JPRS ID: 9542 USSR REPORT ELECTRONICS AND ELECTRICAL ENGINEERING

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• Document Creation Date: November 1, 2016
• Sequence Number: 25
• Content Type: REPORTS

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- JPRS L/9542
11 February 1981
USSR Report
ELECTRONICS AND ELECTRICAL ENGINEERING
(FOUO 2/81)
FBIS FOREICN BROADCAST IIVFORMATION SERV'ICE
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JPRS I,/9542
- 11 February 1981
USSR REPORT
ELECTRONICS PND ELECTRICAL ENGINEERING
(FOUO 2/81)
CONTENTS
CERTAIN ASPECTS OF COMPUTER HARD AND SOFT WARF.: CONTROL,
AUTOMATION, TELEMECF.ANICS, TELEMETERING,MACHINE DESIGNING
AND PLANNING
Image Outlining by a Binary Filter in Pattern
Recognition Systems 1
CERTAIN ASPECTS OF PHOTOGRAPHY, MOTION PICTURES AND TELEVISION
Color Image Filtering in Digital Television Systeme 5
COMMUNICATIONS, COMMUNICATION EQUIPMENT, RECEIVERS AND
TRANSMITTERS,NETWOP.KS, RADIO PHYSICS, DATA TRANSMISSIOh
AND PROCESSING, INFORMATION THEORY
Proceasing Complex Radio Signals by Stroboscopic Methods 11
Averaged Energy Spectra of Pulsed Random Processes Controlled
by an Arbitrary Finite Ergodic Markov Chain 18
Range of the Dead Zone and Maximum Receivable Frequency
for a Horizontally Nonhomogeneoua Ionospheric Layer 39
COMPONENTS AND CIRCUIT ELEMENTS, WAVEGUIDES, CAVITY
RESONATORS AND FILTRRS
Requirements on Methods of Synthesizing Digital Filters
Used for Flaw Detection of Antenna Systema 34
Pasaband Losses of Surface Sound Wave Filters 38
A GaAs Dielectric Waveguide for the Millimeter Band 44
Frequency Synthesizer Based on an Astatic Analog-to-Digital
Phase Automatic Frequency Control System 47
- a- [ITT - USSR - 21E S&T FOUOj
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F,tECTROMAGNETIC WAVE PROPAGATION, ELECTRODYNAMICS
Penetration of an Electric Field Beyond the Shielda
in a Nonsteady Conducting Medium 51
ENERGY SOURCES
I'ifteen Years of Experience in Uperating the Novovoronezhsk
Nuclear Electric Plant Commemorating the Fiftieth
Annivereary of the USSR 58
INSTRUMENTS, MASURING DEVICES AND TESTERS, METHODS OF
MEASURING, GENERAL EXPERIMENTAL TECHNIQUES
Displacement Threshold as a Characteristic of the Operating 67
Quality of the Mechanical Works of Optical Instruments
OPTOELECTRONICS, QUASIOPTICAL DEVICES
Quasioptical Phase Frequency Shifters for the Millimeter Band 72
Choosing the Load Resistance of a Photodiode in Pulaed
OpCoelectronic Sqstema 76
Light Valve Systems With Laser Light 3ource 80
PUBLICATIONS, INCLUDING COLLECTIONS OF ABSTRACTS
Calculating Production Tolerances of Microwave Devices 84
Hydroacoustic Transducers and Antennas 87
Integrated F.lectronics in Measuring Instrum.znts 89
Measuring Instability of the Speed of aRecording Medium 92
Panoramic Receivers and Spectrum Analyzers 94
Piezoelectric Motors 96
Digital Data Transmission in Radio Communications 9$
Liquid Crystal Displays 102
Fundamentals of the Theory and Design of Information Syatems 104
Televiaion Tranamitting Stationa 108
Waveguide Dielectric Filters 111
- b -
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- CERTAIN ASPECTS OF COMPUTER HARD AND SOFT WARE: CONTR.OL, AUTCIMATION,
TELEMECHANICS, TELEMETERING, MACIiINE LESIGNING AND PLANNING
UDC 621.373.826
IMAGE OUTLINING BY A BINARY FILTER IN PATTERN RECOGNITION SYSTEMS
Moscow RADIOTEKHNIKA I ELEKTRONIKA in Russian Vol 25, No 10, Oct 80 pp 2261-2263
manuscript rec:ived 16 Jul 79
[Article by I. I. Sal'nikov]
_ [Text] Pattern recognition with respect to nonorthogonal features freqtiently makes
. use of initial image preprocessing techniques [Ref. 1], one such method being out-
- lining by a binary filter. This method is extensively used because of the simplici-
ty of its realization since the binary filter is nothing more than an opaque screen
of radius r placed in the frequency plane [Ref. 2]. In the literature [Ref. 3] it
haR been shown that preliminary outlining reduces the coefficient of mut:ual corre-
lation between different classes of images to be recognized, which shouid lead to
an improvement in the effectiveness of recognition. However, if consideration is
taken of the noise background of the initial images, the improvement in recognition
effectiveness with outlining ia not so apparent since one should observe a reduc-
tion in signal-to-noise ratio in addition to the reduced matual correlation coef-
ficienC.
Let us determine the conditions under which a reduction is observed in the coef-
- ficient of mutual correlation between functions that describe images to be recog-
nized, and also the change in signal-to-noise ratio after outlining by a binary
i filter.
To simplify the analysis, we will consider the one-dimensional case, and the images
to be recognized will be taken as certain signals sk(x) and sj(x) with band of the
spatial energy spectrum 2S2k and 29i respectively, with S2k < S2j. Moreover, we shall
restrict ourselves to consideration of simple signals for which the product of the
duration multiplied by the band of the spectrum is close to unity (24,3)(20k,j)/27r
=1. Let us express the mutual correlation function of sk(x) and sj(x) after binary
filtration with zero space shift in terms of the mutual energy spectrum G~~)(w)
with band 2SZkj [Ref. 4
(i) B f`)(0)= ~ f GA)(~)dcaaB,i(0)- ~c J Gij (W) dw'
- m 4 - Of
where 252j is the elimination bandwidth of the binary filter. Considering the non-
negative nature of energy spectra, and also the r.elation [Ref. 5] Gkj(w) - (0);;r 84j (0) 11 -4n J [G~((#)Gj(w)lxd4)/~ f Ghi(w)~~.
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. . .
We will assume that Stk �_Qk for S2k wmT - 104-106 for the nanosecond range of durations) by substftuting
T,-.T, ti, -z, 1x-1(T), eT,-aT
we reduce (5) to a Fourier integral for a complex function ~
-t).Co(t)exp{-jwo( N -t)}dt,
(s) y ~Tt S h N

_m
represented on the interval T E[O,NT]. With consideration of the imposed con-
straints, (6) defines the analytical form of the output signal of the stroboscopic
processing system, this signal being an asymptotically narrow-band process with
carrier frequency St = wp - wc �
Practical utilization of the derived relations presupposes specific assignment of
the corresponding functions or their approximation. Of considerable interest is
rhe possibility of using the same type of circuit for shaping the probing and ref-
erence radio pulses [A(t) -X(t)J, which will ensure matched filtration in a strobo-
scopic system of complex signals for any coefficient of spectral transformation N.
71.G
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As an example, let us consider the case of stroboscopic location of objects whose
PTC permits a narrow-band approximation (for example waveguide filters, resonant
commutators based on p-n elements and so on):
h(t) =H(t),cos [w,t+W(t) ]=Re $(t)ej'�`.
In this case, expression (6) can be rewritten in simplified form
Ot r
(7) (i) - 2T .1 a( N -t).*o(t)dt
and treated as ageneralization of the envelope method of Ref. 7 to stroboscopic
processing systems. The influence that the duration of the correlation function of
the reference signals has on reproduction of the envelope and phase structure of
narrow-band PTCs is shown in Fig. 3. Calculctions were done for the models of Xo(t)
-3 -2 -1 0 1 2 3 r/N
N(r) yXl ey
60' ~cq r2,2'
6
~ .ey(e~-o7
47.
~
-3 -1 -1 0 1 2. riN
6 ey=17, 8'
\By
D'
-3 -2 =1 . 0 1 2 3
Fig. 2. Models of investigated
PTC and complex envelope of the
mutual correlation function of
signals x(t) andat(t)w t1(t)-If(t)emui;
J~o(t)- R(t)e�(,)
Fig. 3. Evolution of output sig-
nal y(T) with expansion of the
aperture of the stroboscopic pro-
cessing system: a--Tk = 0.5; 6--
Tk = 1. 0; a--Tk = 2.0
and the complex envelope of the PTC that are shown in Fig. 2. The proposed model
of the correlation function corresponds to even reference signals, which are char-
acteristic when using semiconductor microwave modulators. Fig. 3 also shows the
values of the mean-square error of reproduction of the phase structure of the PTC:
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-2 -1 0 1 1 t

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� V\\ V\ � -11V VUV Vl\Ll
~
r M(r) 18~~~-~1 NdT
~p
(8)
-
f M{T) dt .
-e
where M(T) is the envelope of the output signal
are the mean-s.luare values of the corresponding functions:
a
f M e, (i) d-`
_m
ecp
fm (T) dT
_p -
m
~ H(T)q) (T)dT
_m
(PCy = .
4
~ H (.T) di
~m
As can be seen from the figure, expansion of the aperture of the processing system
leads to an increase in the error. It should be noted that phase resolution can be
considerably improved by reducing the level of phase modulation in the correlation
function (Fig. 36, A~-*-0) by raising the requirements for the phase-amplitude re-
sponses and identity of the reference signal shapers.
The author thanks B. V. Kagalenko and V. A. Korneyev for support and interest in
ttie work.
REFERENCES
1. Blau, "Introduction to the Theory of Partial Coherence in Radar," ZARUBEZHNAYA
RADIOELEKTRONIKA, Izd. Sovetskoye radio, No 5, 1967, p 15.
2. B. A. Varentsov, N. P. Krasyuk, "On Using Methods of Linear Electronics Co Cal-
culate a Scattered Electromagnetic Field," in "Prikladnyye zadachi rasseyaniya
i difraktsii radiolokatsionnykh signalov" [Applied Problems of Scattering and
Diffraction of Radar Signals], Northwest Polytechnical Correspondence Institute,
Leningrad, No 3, 1974, p 2.
3. Kenno, Moffat, "Approximation of Transfer and Pulse Trans�er Characteristics,"
TIIER, Vol 53, 1965, p 8.
4. G. V. Glebovich, "Determination of Parameters of Wide-Band and Narrow-Band Dis-
tributed Systems by Pulse Methods. Up-to -Date Methods and Equipment for Measur-
ing the Parameters of Radio Circuits," Reports of the All-Union Symposium, Si-
berian Scientific Research Institute of Metrology, Novosibirsk, Vol 127, 1974.
5. A. I. Naydenov, "Transformatsiya spektra nanosekundnykh impul'sov"! [Transforma-
tion of a Nanosecond Pulse Spectrum], Izd. Sovetskoye radio, 1973.
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6. A. I. Naydenov, B. A. Chelnokov, "Problems of Electronics," RADIOIZMERITEL'NAYA
TEKHNIECA, Vol 4, 1973.
7. I. S. Gonorovskiy, "Radiotekhnicheskiye tsepi i signaly" [Electronic Circuits
and Signals], Izd. Sovetskoye radio, 1977.
8. V. U. Zakharchenko, IZVESTIYA WZov: PRIBOROSTROYENIYE, No 10, 1976, p 5.
COPYRIGHT: Izdatel'stvo "Nauka", "Radiotekhnika i elektronika", 1980
- [$1-6610]
6610
CSO: 1860
17
Uno nccri-r . r r rcr, nw,t v
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['VK l.: ~~.lHL IJJG V1rLl
UDC 621.391.2:519.217.2
AVEt2AGED ENERGY SPECTRA OF PULSID RANDOM PROCESSES CONTROLLED BY AN ARBITRARY
FINITE ERGODIC MAT:F:OV CHAIN
Moscow RADIOTEKHNIKA I ELEKTRONIKA in Russian Vol 25, No 10, Oct 80 pp 2115-2125
manuscript received 12 Mar 79
[Article by S. D. Eydel'man, T. G. Pletneva and G. N. ltozorinov]
[Text] A solution is found for the problem of calculating the
averaged energy spectrum of a pulsed random process controlled
by a finite ergodic Markov chain. The procedure of generalized
functions is used to substantiate the computational formulas.
The effectiveness of the method is illustrated by exa.mples of
finding the spectra of signals used in digital magnetic recording.
Introduction
- The present investigation arose in finding the energy spectra of highly informative
digital magnetic recording signals. In this study it was found that the recommen-
dations of Ref. 1, 2 and the article of Ref. 3 need to be made specific, while the
results of Ref. 4; 5 need to be made much more general. Methods of calculating the
averaged energy spectra of a broad class of signals, especially electrical communi-
cation signals, are given in the book of Ref. 6, and also in the articles of Ref.
7 and 8.
This paper deals with complete solution of the problem of calculating the averaged
energy spectrum of a pulsed random process controlled by an arbitrary ergodic Markov
chain. Considerable use is made of facts of the theory of finite Markov chains as
presented in the book of Ref. 9. Mathematical substantiation of all passages to
the limit is based on the theory of generalized functions. The presentation is
accompanied by cases in which calculation of the averaged energy spectrum can be =
substantiated within the framework of classical analysis.
The resultant formulas can be used for fairly efficient calculation of averaged
signal spectra.
An information sequence to be transmitted over a communications channel is usually
transformed by encoders and modulators (Ref. 151 in such a way that the resultant
signal has certain predetermined properties such as high interference immunity. In
the most extensively used binary systems the encoder is a synchronous sequential
finite Mili automaton, and modulation is accomplished by the action of binary infor-
mation symbols on any of.the parameters that characterize the carrier waveform (a
18
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time function assigned on segment (O,T)). Digital data transmission systems use a
square-wave carrier, and therefore the signal in such a system is a sequence of
square pulses regardless of which of the parameters of the carrier wave is modu-
lated. In this case the clock interval can be taken as deterministic, and the in-
formation signal can be described by pulse "bursts" that alternate in a specific
pattern. Then it is natural to consider the relations between different pulse
bursts as Mgrkovian. If it is necessary to consider the correlation of bursts that
are rather far apart with respect to time of arrival, then the duration of the
initial set of bursts can be increased. Such a Markov model is readily calculable,
and while it cannot be considered exact, it can nevertheless be used as a fairly
satisfac[ory approximate description of a real process.
1. Mathematical Model
The given random process C(t) is a set of square pulses with amplitudes C1, C2,...
Cp that lasts for time T. The amplitude changes or remains the same at times
kT, k = 0, 1, . . .
Hypotheses that describe the process &(t):
1.1. There exists an integer r such that only certain bursts E1(t), ~2(0,..., ~q(t)
can appear on the half-open intervals [(k - 1)rT, krT), k= 1, 2,... Each burst Ej(t)
is a predetermined set of square pulses �j (t) of duration rT; 0 (t) =ejV for
t E[v - 1)T, vT], v= 1, 2,..,, r, where ejv takes on some value irom the sequence
C1, C1,..., CP.
1.2. The process &(t) can be put into one-to-one correspondence with a finite
Markov chain n(T) with discrete time T=O, rT, 2rT,... and states S1, S2,..., Sq
such that:
a) if n(krT) is in state Sj, this means that C(t) =Ej (t) for tE [krT, (k+l)rT);
b) n (z) is an ergodic Markov chain [Ref. 9] with given matrix P=(pij), i, j= l,
2,..., q of transitional probabilities.
1.3. The mattiematical expectation M{~(t)} of process E(t) is equal to zero.
'1'hus &(t) is a random process with deterministic clock intervals that is specified
by the following quantities: pulse duration T, amplitudes C1, C2,..., CP, number
of bursts q, their "size" r, the matrix of the form of the bursts and
ttie matrix of transitional probab ilities P.
The considerations given below are also applicable in those cases where the wave-
shape of the carrier of the process E(t) is arbitrary and not square.
- 2. Some Notation
Let us denote by A=(A1, A2,..., Aq) the steady-state distribution of a finite
ergodic Markov chain with matrix of transitional probabilities P. In the case of a
cyclic chain
H lim = A, H d> i,
r-_ n
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such that 3 ni~m pdn = A0, where elements of Ap with indices i and j are equal to zero,
if Si and Sj do not belong to the same cyclic clas_~ and are obtained by renormali-
zation from the components of steady-state vector A that belong to the correspond-
ing cyclic class, if Si and Sj belong to the same cyclic class [Ref. 9].
In addition, we introduce the following notation: eu= (elu, e2u,��', EQu)~
pS S pdS _ A0, S = 1, 2, . . . ; PO = I is the identity matrix; A = (Aidij ) i, q;
dij is the Kronecker delta; Aev _(Alelv, A2e2v,..., AqEqv);
Fspve� , Aev - m�s- v)-, AoPYe� � Ae� = m�~ ~
Aoe� � Ae� = m�,),; eN � Ae� = m�v; eA � Ae� = m; m�v' = m�v ~
~a=(1~1+�� �,1)~
-~-9
rT r
Q e;Wr dT ; Q = e-WTi Vi a Y. 6IV'1v-I +
u V�1
ir is the vector of initial probabilties of the chain n(T).
3. Ca.lculation of the Averaged Energy Spectrum
The averaged energy spectrum P(w) of process &(t) is defined by the following
= formula [Ref. 4, 6]:
(1) P((0)=1imP(n,(w),
where x_m Nrr ~Z~ P~~ ) N 2 rT M (
~ I J ~ ~t) e-idtdt
0
On the basis of hypotheses 1.1-1.3, P(N)(w) is represented by the formula
(3) p(") (w) = 21rTa1ZIEs(w)+E:N' (W)
where
N
q A~1 r
(4) E'N' (w) _ ~ 1V Y,
v,V~t
7-t
r N-! q ~
(5) E;"' (m) =2{ 7V / X
P,-t s_s i_1
N-s
E (nP"-'1 ~
k-f
X _ N-S - A' (PbeN) lEt, cos (Sr-k-�-v) w T +
,
~ ) PeeM�~Ie.cos(Sr--�-v)~T ~ j= 2IE:1 `N'((V)~"En
~
yr~l 6..f
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Using the notation of �2 and passing to the limit in (4), we get
.
(6) E, (w) - lim E; "l (o))= ~ m.. cos(�-'v) (oT.
N-m

The following is important for the subsequent presentation:
a) 3b < 1 [Ref. 9] such that
n
4~1
- A, S cb", t/n;
:n
b) if the function ~(w) E D, then its Fourier transform ~(cs) satisfies the inequali-
Cies [Ref. lO]
~(a) 1~Cj vi.
Consider E2N)(w) in formula (5). We will treat this function as a regular general-
ized function of D' [Ref. 101, and understand its limit as N-- in the sense of D'.
Let us take any fundamental function o(w) E D and consider the sequence
~
aN=(Eur;(P)a f E;O'((#)(p (w)dw~ .
_m
(7) .
x-B
~nP4-`)
. x_, ,
i- ~
A-l
u
N ~ N-S
s
-Af Re~EirT(BrtM-v)Qil~~TlW~do)�
l
� _m '
In virtue of points a) and b) (at j=2) and the fact that a2(W)�(w)ED, we get
N N/= N
(8) I uN I< cEb"-es ='c (Eb1-1S:-'+ E b"-es-') `
8-1 8-1 S-N12}1
< c ~ vN/3 \ ' S_1 WE b8 I _.y 0.
~ s-o x..M
Let us go on to f ind the limit of the function E~2~ (c~) . We will assume that N= dn.
We can readily see that the limit of E22) (W) is the same when N - in an arbitrary
way.
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. . .
where
.
(9) En'"' (w)-G,("'((o)+G:" (co) - ~ ep�AErCO$(j1-v)wT,
u,.-1
~ .
(10) G'(M) F. 1 1 drz71 X
M,~~1 T~0 B~0 X (Pd�-Ae)PTe,,�Ae.cosl (dS-1-y)r+js-v]u)T,
. a-i .-I
(11) � E EV 1 r d ~ Agp'e�.
N,v-i T-o a..o Ae,,cos [(dS-I-7 ) r-I-�-v j wT.
Since the norm of matrix (PdS -Ap) has order bS/d, b 1.
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Subttituting the values found in formula (16), wp get
sin 2wTt _
5 4a~T, 8c~TT
P(w) = g~=T! ( 80-40 cos 5- 30 cos s--
+i4 cos i25 T:+ Z cosis5T*- 3 cos 4wT,+ Z cosM 5T*1
l5.2. Among self-synchronized signals that increase recording density is the narrow-
band phase-modulated signal (npm) [Ref. 12]. To improve reliability of the process
of recording and playback, the shape of the npm signal is considerably modified
T
1H__F 9 Fl-,(- 17U_Z 25 LF--L_
? (Z._(Z )OZ--F 18LF--,r 26J-.-_
3(---I_ 11-~- 19 L___r- 27_r---
4F--L-J- 12ZJZ 2X--f1_ 28 f1,J'
5 F11_Z 13 (~1..JL 21 LF1__F- 29 FLJ--
6 F-L.,f 141.F-_ 22L_F-L JO_FL_J-
7 n,1- 15 -IJ-L_ 23L_F-L_ 31 J-Lf-
6 F-VL, 16-Lr-..r 24L,.nj- 32-Fli-Z
is- 47L-:
a
2 rT
1
2 fULJ s LfLJU loLl1!74 nJ'-1f1
3 r-UU 7 rl_!-l ,n LJUn 15ls-lJ .
4rInm D IlLfl 12L,(11U1 16 (Zj`"'Z,j
-.UT
b
TT
1 f-1 3 I�' U
c
t T(~...rl 4 L..l-ZI
Mwa
Fig. 2
(Fig. lb) even before recording on the magnetic medium (i. e. it is predistorted
pd). The npmpd signal can be represented as 16 bursts (Fig. 2b). The duration of
the bursts is equal to 8T (T = TT/4) ; q=16; r= 8.
e,=(Fif-F,), Fj-=(i i 1 i i--4 1-4);
es=(F2i -F=), F,a(i i 1 1 1 i 1 1);
e,=(F,, -F3),'F,-(1 -i i -i -1 -1 -1-1);
ea=(F,, -F.), F,=(1111--1-i -1-1);
es=(F,, -Fe) Ff-(-1-!-!4-1 -1 --1�-1-=1);
e6-(F6, -Fg), F6= (-1-11 1 --9 -i --t -1);
e:=(F,, -F;), F;=(-t -i -9 1 1 1 1 j;
e6-(Fe, -F'i), F'e=(-1
/ ' * T r y ~.1
p = 4 i G); G=iBigzgagi8ib'aBs)+
~
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where ~1= (10100000); g2 = (00000000); gg= (01011010); G*T = (9494939394949292),
where 84= (00000101). .
'fhis process as well t cont~rolled by a regular chain with doubly stochastic
Cranaition matrix P: 1/16& 16; A� 1/16I; mp =1.
In the given example, the formula for calculating P(w) is theoretically no longer
finite, but numerical calculation shows that for the npmpd signal we can limit
ourselves to terms S= 0, 1,..., 5. Further refinements do not exceed one percent.
TABLE 2
PR)) sin~;~ (16, 6, B, -8, -16, -l, -i8, 2, 0, 2, 10, 2, 4. 0, -2)
- p(a) sin' (i T/2) (16, 4, 8, -8, -16, -4, -16, 2, 0, 4, 12, 2, 8, =2. -r-4,.
cw) 20T
-3, -8, 0, -2, 2, 4, 1, 4, -1/2, 0, -i, =3, -1/2, -2, 1/2, 3/4, 2, 0+
1/2, -1/2, -i, -1/4, -i, 118, 0, 118, 5/8, 1/8, 1/4, 0, -1/8)
The results of calculations of P(w) for the npmpd signal are summarized in Table 2.
In tlie formulas of P(w) (Table 2) the coefficients of cos kwT9 k= 0, 1, 2,... are
given in parentheses.
Also in the category of self-synchronized signals is the frequency-modulated signal
with aquare-wave carrier (fms) shown in Fig. lc. An interesting feature of this
signal is that an odd number of high-frequency half-periods fits in the clock inter-
val. The forms of bursts for the fms signal are shown in Fig. 2c. In this case,
T'T=3T; q=4; r=3; e1=e3=(11-1-1), e2=(1-1-11);
1 GIG# 0 j0 ! i
~ 2( G* ~G G- (0 0)' G* (i i)
Here
pZm _ 1 G* ~ G l p2M+1 _ P. .
2(G;G*
Hence we see that the given process is controlled by a cyclic Markov chain for
whicli d= 2. In this case Ap = P2; A= 1/4I; _
101 10i -40-i
m �V = 0 1 0 , na�y = 0 0 0 , m�v = 0 0 0,
(101 40! -10-1
t~'n� B' =U, d y, S> 1.
Then in the first summand of formula (15) we have non-zero terms at y= 0, S= 0:
3+ 2 cos 2wT - 2- 2 cos 2wT = 1. The second summand : -1/2(3 + 2 cos 2wT) . The only
components in the singular summand are those at y= 0: 1+ cos 2wT. Passages to the
limit are treated in the sense of D'. Substituting the resultant values in formula
(15), we find P(w) for the fms signal: �
_ 8 sin2 (c~T/2) ( 1+ Sn cos= coT sin' 3wT S nh1l
p~~~- 3~2T ~ 3T � 2~ ~ w - 3T/
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p(ui) 7r'/zr,
i7f - 1
N ~
r,{ / J~Jnp~.pd
r
o qa
Fig. 3
5.4. The resultant formulas were used for plotting
graphs of the averaged energy spectra of the given
I ~ signals (Fig. 3), where the values of P(w) multi-
4- =-r-plied by the coefficient n2/2TT are laid out along
Che axis of ordinates, while the values of the
normalized frequency w/w.r are laid out along the
axis of abscissas.
~--i
A comparison was made between the results of cal-
culations and experiment. In the experiment the
� _ ~ information signal was simulated by a generator of
pseudorandom pulse sequences. The duration of a
~ sequence was taken as equal to 1023 clock cycles
1 r.~~~~r and the clock frequency was 1 MHz. Appropriate
modulators were used to produce npmpd and fms
signals, which were studied on a wide-band spec-
trum analyzer type 54-25. Photographs on Fig. 4 and 5[not included in the trans-
lation] show the amplitude spectra of these signals taken from the CRT screen of
ttie analyzer in the same scale. A special detector was used to isolate only the
envelope of the amplitude spectrum. The error of ineasurement of the components of
the spectrum did not exceed tl dB.
The somewhat different shapes of the theoretical and experimental spectra, in par-
ticular the slightly higher level of high-frequency components in the theoretical
spectra, can be attributed to the fact that in the calculations the rise and fall
times were taken as infinitely short, and also to experimental error. However, on
the whole the theoretical and experimental spectra correspond fairly satisfactorily.
It can be seen from an examination of the graphs of spectra of the nwrz and npmpd
signals that most of the energy of these signals is concentrated in the low-frequency
region. Considerable use is made of this fact in optimum matching of signal param-
eters and the recording-playback channel. The use of signals with the described
forms of spectra in digital magnetic recording equipment has made it possible to
increase the information density of recording by a factor of 1.5-1.6 without sacri-
ficing high interference imnunity [Ref. 13, 14].
The spectrum of ttie fms signal clearly shows two discrete components corresponding
to the zero-level and one-level information digits, which facilitates symbol detec-
tion by frequency separation.
REFIItENCES
1. B. R. Levin, "Teoreticheskiye osnavy statisticheskoy radiotekhniki" ~Theoretical
Principles of Statistical Radio Engineering], Book 1, Sovetskoye radio, 1974,
p 552.
2. V. I. Tikhonov, M. A. Mironov, "Markovskiye protsessy" [Markov Processes],
Sovetskoye radio, 1977, p 488.
3. L. M. Polyak, RADIOTEKHNIKA I ELEKTRONIKA, Vol 17, No 3, 1972, p 626.
27
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4. A. L. Knoll, "Spectral Analysis of Signals Used in Digital Magnetic Recording"
in: "Problemy magnitnoy zapisi" [Problems of Magnetic Recording], edited by
V. G. Korol'kov, Energiya, 1975, pp 79-91
5. M. Khekt, A. Guida, "Delay Modulation," Trudy Instituta inzhenerov po elektro-
tekhnike i radioelektronike [Proceedings of the Institute of Electrical and
Electronics Engineers], Vol 57, No 7, 1969, p 161.
6. G. V. Konovalov, Ye. M. Tarasenko, "Impul'snyye sluchaynyye protsessy v elek-
trosvyazi" [Pulsed Random Processes in Electrical Communications], Svyaz',
19�, p 304.
7. Ye. M. Tarasenko, RADIOTEKHNIKA I ELEKTRONIKA, Vol 21, No 2, 1976, p 400.
8. G. L. Cariolaro, G. P. Tronca, IEEE TRANS. COMMUNS, 1974, COM-22, 10, Oct 1955.
9. J. Kemeny, J. Snell, "Konechnyye tsepi Markova" [Finite Markov Chains], Nauka,
1971, p 512.
10. V. S. Vladimirov, "Uravneniya matematicheskoy fiziki" [Equations of Mathematical
Physics], Nauka, 1971, p 512.
11. I. M. Gel'fand, G. Ye. Shilov, "Obobshchennyye funktsii i deystviya nad nimi"
[Generalized Functions and Operations on Them], GIFML, 1959, p 470.
12. T. G. Pletneva, 0. V. Poritskiy, G. N. Rozorinov, S. D. Eydel'man, "Determina-
tion of Energy Spectra of Complex Digital Signals by the Method of Associated
Markov Chains." OTBOR I PEREDACHA INFORMATSII, No 56, 1979, Naukova dumka,
pp 48-59.
13.0. V. Poritskiy, G. N. Rozorinov, S. K. Kachanovskiy, "Magnetic Recording and -
Playback of ni4iral Tnformation on a Di_sk Using Narrow-Band Phase Modulation,"
VESTNIK KIYEVSKOGO POLITEKHNICHESKOGO INSTIT'JTA, ELEKTROAKUSTIKA i"LWKUTEKHNIKA
No 1, 1977, pp 45-49.
14. 0. V. Poritskiy, G. N. Rozorinov, V. D. Svyachennyy, "High-Voltage Digital
Magnetic Recording and Playback of a Continuous Stream of Information," VESTTIIK
KIYEVSKOGO POLITEKHNICHESKOGO INSTITUTA, ELEKTROAKUSTIKA I ZWKOTEKHNIKA, No 2,
1918, pp 13-17.
15. M. V. Gitlits, "Magnitnaya zapis' v sistemakh peredachi informatsii" [Magnetic
Recording in Data Transmission Systems], Svyaz', 1978, p 304.
COPYRIGHT: Izdatel'stvo "Nauka", "Radiotekhnika i elektronika", 1980
[81-661 0]
6610
CSO: 1860
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uDC 62i.371
RANGE OF THE DEAD ZONE AND MAXIMUM RECEIVABLE FREQUENCY FOR A HORIZONTALLY NONHOMO-
CENLOUS IONOSPHERIC LAYER
Moscow P,ADIOTEKHNIKA in Russian Vol 35, No 10, oct 8o pp 63-66 manuscript received
2f3 Jan 80 ~
[Article by M. V. Tinin]
[Text] Among the most important characteristics of a shortwave transmission path
is the range of the dead zone (i. e. the distance at which the caustic intersects
the aurface of the earth) at a given frequency, and also the maximum receivable
frequency for a given distance between ground-based communicating parties. Deter-
minntion of these characteristics involves finding the minimum range of a single
}io;, For bearns whose trajectories in the general case of a horizontally nonhomo-
Ncrjeou 5 ionosphere are found by numerical integration of a system of nonlinear
ordinary differential equations. In cases where the equations of the beam have an
anfLlytical solution, the problem reduces to solution of a rather complex transcen-
dental equation. In this paper, approximate formulas are derived for the range of
the dead aone and the maximum receivable frequency in both horizontally homogeneous
and hnrizontally inhomogeneous ionospheric layers with consideration of the small-
:.ess in difference between the angle of departure and the critical angle for a beam
arriving at the boundary of the dead zone. For the sake of simplicity and clarity
of the calculations, we will restrict ourselves to a flat earth and close to flat-
layered ionosphere with permittivity assigned as
1' ym
c (t'. x~) 9m ~
whe.re C = fp/fc is the ratio of the working frequency to the critical frequency; ym
is the half-thickness of the layer. The presence of horizontal inhomogeneity in
ttie ioc.:)sphere is accounted for by the slow dependence of parameters E and ym on x'
and by the inclination a= arctan dh/dx of the base of the layer (Fig. 1).
Consider first the case of a horizontally homogeneous ionosphere
cOn3t, y�f - COnS', a- 0, z- Z', X- X', (2)
where hp = h, ~p =~1, Zp = Z1, D' = D, and for the range of a hop of a reflected beam
we have [Ref. l, 2]
D 2hs (3)
~/Z-s` t.
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-
ha
Fig. 1
whcre 1+ E 1~1- s'
S - YmSE 1~ (4)
1 -EI/ 1-s' .
is the range of a hop inside the layer; h is the altitude of the base of the layer;
s= siti ~p is the sine of the angle of incidence of the beam on the layer.
'I'he range of the dead zone is determined by substituting in (3) the solution of the
transcendental equation
~(s,n) - 0. (5)
l:t i:~ known [ReF. 2] that the angle of incidence ~pm= aresin sm of the beam arriv-
.i.ng n.t the boundary of the dead zone is not equal to the critical angle. However,
a:.� can be seen from distance vs., angle curves D(~p) [Ref. 1-31 this angle is often
quitF: c1ose to critical. With consideration of this fact, we can solve (3) approxi-
mately with respect to s(T):
.
s(s)-sin~,iz-~1-E''+ 2
E E' e f~~i � (6)

Substituting (6) in (3), We get an approximatP equa.tion for the range of the hop:
,
+ 2 � r., y= - `
D _ 2h ' y. t 2h llE'- l { 1 E,~~ ~ e yo E~-~ }  ~ (7;
~
4e yp yE+_1 e ta y~
E
Expression (5) reduces to the equation
SNI
dD (t~n) 4hE' e y~ /(-I)
di ' - Y.a (E' --1)
From (8) and (6) we get
. sm c lrl-E-' {1 +
Now, substituting (9) in (3)-(4), we get for the range of the dead zone Dm
{ y-"' ~ I -F - 1  ~1 - 2)'m (1
Ym In

, _
V 1- 2ym (I 1-`' 1- 2ym lI
(10)
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wliere f)R~ = I)1n/; h, Yrn - YmI; h.
With consideration of (8), a transition to the second equality of (7) can be made
when
Ynr < I.
(11)
But when condition (11) is met, expression (10) is simplified, becoming
:
_ D.,-~Yo(l+in~ 1). (12)
~ _ In order to find the ratio of the maximum receivable frequency to the critical fre-
- quency (M-factor), it is necessary for a given range D to solve equation (12) with
respect to C _~m. Assuming a low value of `ym in(1 let us solve (12) by a
metYiod of succes sive approximations:
+
_ Em =  D' 11 + Y~ 1 + ln . (13)
Y ~
v
A more exact expression for the M-factor can be obtained by solving (10):
,
Em 1 i- ' + DI + ym In (14)
I~
where
2y. �
(15)
D-'
Comparison with the er.act numerical values of ~m and Dm has shown that the error of
formulas (10) ,(14) for ym = 0. 25, 1.4 l, Moscow, Nauka, 1980.
CU['YRTGHT: "Radiotekhnika", 1980
[ad-661oI
6Gio
cso: 1860
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COMPONENTS AND CIRCUIT EI.EMENTS, WAVEGUIDES,
CAVITY RESONATORS AND FILTERS
YJDC 621.372.54
RF.QUIREMENTS ON METHODS OF SYNTHESIZING DIGITAL FILTERS USED FOR FLAW DETECTION
OF ANTENNA SY5TEMS
Moscow RADIOTEKHNIKA in Russian No 9, 1980 pp 56-59
[Article by V. R. Kryuchok, G. P. Lichko]
(Text] One of the basic methods of flaw detection of antenna systems by the
results of holographic measurement of the amplitude-pfiase distribution of the
field in the near zone is the method of inverse diffraction [1]. The success in
implementing th is method depends to a great extent on the level of ineasurement
noise such as the error of the measuring eqnipment, the nonideal nature of the
characteristics of the probes, the disturbance of the conditions of quantifica-
tion of the me asured amplitude-phase distribution (APD) and also the degree of
isolation of the variation of the APD caused by the defects in the measurement
plane. The given difficulties can be partially surmounted using digital.filters
having frequency characteristics close to the required characteristics.
Let us define the requirements imposed on the methods of synthesizing digital
�ilters used for flaw detection of antenna systems with the help of general-use
digital compute rs.
The solution of the problem of flaw detection of flat antennas by the measurements
of the APD in the near zone and the value of the sealed phase distribution for
detection and 1 ocation of defects require the app li cation of digital filters with
two-dimensional frequency characteristic with zero or linear phase characteristic.
The small quantification step used for flaw detection by comparison with the
mpasurement of the APD for other purposes and the la rge measurement areas lead to
an increase in the processed files and the volume of the ready-access memory of
the computer us ed, thus complicating the recursive realization of the digital
filters. Unde r the indicated requirements, considering the stability of the
realization of digital filters,the digitgl filters with restriction by the pulse
response (KIKh filters) with nonrecursive realizatton given by a relation of the
following type are the most prospective for application in antenna system flaw
detection:
K L
Y(+n, P) = J L,h(k, l)x(m-k, P-h, ~1)
!=-K !=-L
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where h(k, R) is the pulse response of length (2K+1) (2L+1) ; x(m, p) , y(m, p)
are the input and output �iles, respectively.
Reitlizat.ion af (1) is possible directly or by means of fast Fourier tranaf.ormations
(FFT). 'Ihe choice of the method of realization dependa both on the ratio of the
length of the pulse response of the used filter to the magnitude of the processed
- �ile of ineasurement results and the capacity of the ready-access memory of the
computer. For a file not contained in the ready-access memory, the filtration
time increases significantly as a result of multipZe reference to the external
memory. For example, the time of realization of the fast Fourier transformation
of a 1204x1024 file using the program by the authors realizing the algorithm pre-
sented in [2], increases by SO times by comparison with the time required for
the r'FT of the 128x128 file in the ready-access memory using the YeS-1022 com-
puter with ready-access memory of 512 kbytes and a magnetic disc storage with a
capacity of 29 Mbytes. As a result of the predominant application of digital
filters �or filtering the results of ineasuring the APD entered on the inter-
mediate information carrier (punch tape, magnetic tape), on input to the com-
puter it is preferable to use a direct calculation (1) or sectional reduction
with the help of the FFT with the knawn length of the pulse response of the used
KIKh-f.ilter. With the possibility of realizing the FFT of the processed file
without using the external memory the linear reduction (1) is comparable with
respect to speed to the circular reduction for the KIKh-filters with symmetric
pulse response up to 24x24 long [3]. Thus, in all of the enumerated cases for
predominant use of linear reduction the pulse response length must be minimal.
~ The presence of symmetry has important significance, for if the selected method -
- of AynthesizinA the KIKh-filter insures symmetry not only of the pulse response,
but also symmetry of the frequency characteristic, the time for synthesis and
reali2ation of the filter decreases significantly. Restricting the length of
the pulse response of the KIKh-filter leads to worsening of the forms of the
frequency characteristics obtained with an increas e in filtration noise when solv-
ing (1). Therefore the choice of the method of synthesizing the KIKh-filter must
be matched both to the length of the pulse response and to the characteristics of
the measuring equipment such as the dynamic range, the errors in measuring the
phase and amplitude. Converting these errors to errors in calculating the APD
spectrum, including the radiation pattern (RP) of the antenna system, it is
possible to define the initial data for synthesis of the filter in the form of
the maximum level of pulsations in the passband D1 and the elimination band D2,
the width of the in termediate b and dF.
As an example of synthesis of the KIKh-filter and its application for flaw detec-
tion of antenna systems let us consider the follawing problem. Let it be
necessary to detect and locate the variation of APD caused by a defect in the
form of violation of the current distribution in 40 elements of a slotted wave-
guide array consisting of 20x30 elements. A file of 64x64 sam-p? es of APD v
measured with a step of a/2 using equipment with dynamic range and measurement
error of APD using a probe providing �or the calculation of the radiation pattern
under the experimental conditions with an error of 5 decibels for a dynamic range
of 40 decibels for
Ia,IS0,3h, Iw,l T, there is a probability of "skipping" through the zone of sharp viewing of
tRe object, and at the same time, skipping it (see Figure 2,a). Ir the speed of
relative displacement of the subject point of the objective odi the object is
appreciably lesa than the speed of the sensamotor tracking [6], then the condition
< 2 T ~1)
guarantees absence of skipping the point object (see Figure 2,b). Here, for the
case of A z (1/2)T the subject point of the objective can be in the zone T 1-3
times durYng a single one-way pas's (considering some small indeterminacy of the
physical boundaries of the depth of focus [71). In the given phase of developmen.t
of the concepts of the role of the mecha.nism in the focusing process the expression
A. C 2 Tmln.. _
(2)
where Tmin is the least of the depths of foctis �or the objectives used in the micro-
ecope set, and it can serve as the limiting condition of insuring focusing on the
part of the mechanism used.
1The latter fact is decis{ve in a number of experiments, aad it indicates the func-
tional suitability of the instrument.
2 This representation of the object permits us to obtain a margin of accuracy when
estimating the admissible thr.eshold displacements.
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For the inveatigated cases of use of inechanisms in control circuits, the trreshold
displacement at the input of the mechanism cannot serve aa an independent operating
characteriatic, but it is of interest for research purposes [1].
LeC us consider the peculiarities of the functioning of m-nchanisms in measuring cir-
cuits, and let us discover Che role of the displacement threaholds for this case.
In the measuring circuits (Figure 3) the mechanisms are used for conversion, as a
rule, of a small "signal" displacement to a large one at the output, in accordance
with the gear rat io of the mechanism which, in the general case, is a variable. iiere
- the accuracy of r ealizing the prescribed relation between the displacement at the
input and the displacement at the output, that is, the accuracy of realizing the
gear ratio, is important. As is lcnown, the values of the gear ratio are calculated
without considering friction, the terminal rigidity of the circuit, clearances and
dynamic factors which lea.ai to the threshold limit of realizable displacements at the
input and output of the mechanism. The displacement thresholds f* the mechanisms
.s
Figure 3. Structural diagram of a measuring circuit; 1-- signal;
2-- sens itive element of the measurement circuit; 3-- measurement
circuit elements; 4 indicator.
' increase the general sensitivity threshold of the measuring instrument which,
accord ing to [2], is def ined metrologically as a value equal to the zera error, and
the relative measurement error in this case is accardingly equal to 100%. There-
fore the comparative estimates of the displacement +th:.esholds far different types of
mechan isms could aerve as the basis when seYecting the optimal mechanism for insur-
ing the required operating precision of the measuring circuit of the optical instru-
ment. In the op inion of the author, the displacement thresholds should not have
independent significance for production quality control of the mechanisms of ineasur-
ing circuits.
At the same Cime it is necessary to note that in many optical instruments the
mechan iams simultaneously perform the control f unction and the measurement function
(for example, Che precision focusing mechanism of a measuring microscope). For
such mechanisms it is important to control both~the accuracy of realizing the
transf er function and the threshold displacement determining the quality of the
mechanism for positioning control.
When subatantiating the expediency of using the threshold characteristic for in-
vestigation and control of the mechanical works of optical instrument control cir-
- cuits, the meCro logical aspects of rating them are not touched on, for this must
be the aubject of a separate investigation for each case of use of inechanisms
depending on the peculiarities of the operating conditions and requirements.
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BIBLIOGRAPIiY
1. V. V. Kulagin, S. M. Latyyev,"Tizreshold Sensitivity of the Movemeut of Precision
Mechaniams with Manual Control," OPTIKO-MEKHANICHESICAYA PROMYSHLENNOST'
- (Optical-Mechanical Industry), No 5, 1973, pp 16, 17.
2. P. V. Novitskiy, OSNOVY INFORMATSIONI10Y TEORII IZMERITEL'NYKH USTROYSTV (Funda-
- mentsls of the Information Theory of Measuring Devices), Leningrad, Energiya,
1968, p 107.
3. L. A. Ostrovskiy, OSNOVY OBSHCHEY TEORII ELEKTROIZMERITEL'NYKH USTROYSTV (Funda-
mentals of the General Theory of Electrometering Devices), Leningrad, Energiya,
p 101.
4. M. M. Miroshnikov, TEORETICHESKIYE OSNOVY OPTIKO-ELEKTFZONNYKH PRIBOROV (Theore-
tical Principles of Optico-Electronic Instrtments), Leningrad, Mashinostroyeniye,
1977, p 19.
5. S. A. Sukhoparov, V. A. Dmitriyev, "Designing Optical Instruments with the Help
of Spatial Gear Ratios," TR./I,ENINGBADSRIY INSTITUT TOCHNOY MEKHANIKI I
OPTIKI (Works of the Leningrad Institute of Precision Mechanics and Optics),
No 84, 1976, p 18.
- 6. B. F. Lomov, CHELOVEK I TEKHIJIKA (Man aad Machine), Moscow, Sov. radio, 1966,
_ p 46.
7. A. N. Zakhar'yevskiy, KONTROL' OPTICHESRIKH SISTEM I PRIBOROV [KONSPEKT LEECTSIY]
(Optical System and Instrument Control [Lecture Synopsis]), No 2, izd. LITMO,
1946.
Recommended by Optical Instrument Design Manuscript received 28 Feb 1979
ar.d Production Department
COPYRIGHT: "Izvestiya vuzov SSSR - Priborostroyeniye", 1980
[A144/0258-10845]
10845
C50: 8144/0258
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'Vl% Vl'l'l\.IAL VUL'+ Vl\Lt
OPTOELECTRANICS, QUASIOPTICAZ DEVICES
Unc 621..372.852.1:621.376.42
QUASIOPTICAL PHASE FREQUENCY SHIFTERS FOR THE MILLIMETER BAND
Moscow RADIOTEHIiNIKA in Russian Vol 35, No 10, Oct 80 pp 76-78 manuscript received
11 Jan SO
[Article by B. N. Knyaz'kQV, Ye. M. Kul�shov and M. S. Yanovskiy]
[Text] A frequency or frequency spectrum can be shifted by some small amount by
using continuous linear phase shifters that produce a time-uniform change of phase
displacement. In quasioptical phase shifters for the submillimeter band the fre-
quency displacement is accomplished upon reflection of a circularly polarized wave
from a rotating half-wave differential phase section located between reflecting
rjuarter-wave sections, one of which is for linear-to-circular polarization, while
the other is for circular-to-linear polarization [Ref. 11.
In the case of oblique incidence of the electromagnetic wave on a rotating half-
wf-tve phase section formed by a wire grid backed with a flat reflector, a spectrum
Qf npurious components appears at the output of the device due to spurious phase
- modulation [Ref. 2]. In this connection, it has been
suggested that a 90-degree dihedral co~�ner reflector
6 be used as the half-wave section [Ref. 31, which
~p f1 enables time-linear phase shift of the electromagnetic
, 9 1 ff wave that is reflected.
IF ~;2--F-3
Fig. 1 shows just such a phase frequency shifter
� ~4 based on a hollow dielectric beam guide [Ref. 41.
B y Placed in a bend of the beam guide is a reflecting
wtZQ t~ . quarter wave phase section made up of wire grid 3 and
stationary flat reflector 4. The grid is made up of
Fig. 1 parallel wires with a recurrence period much shorter
than the wavelength X. The beam guide is closed by
90-degree dihedral reflector 5 fastened to the shaft of motor 6 with electromag-
netic double rotation frequency sensor 11. At the output are two polarization beam
splitters with wire grids 1 and 2 in the diagonal pla.nes; the wires of these grids
are at an angle of 45� to each other. A wave polarized perpendicularly to the
- wires of grid 1 enters at input 7. This wai*e is the flanda.mental mode of the hollow
die].ectric beam guide EH11 with plane front and axisyIInnetric amplitude distribution
that has a ma.ximum on the axis and fa11s off toward the periphery of the beam guide
in accordance with Bessel law. The wave passes freely through grid l, and is split
on grid 2: half the energy is tapped off to fla.nge 9 s.nd may be sent to the
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reference channel of a measurement circuit, while half of the energy passes through
grid 2 and enters section 3-4 that produces a quarter-wave path difference between
orthogonal components. Produced at the output of the section is a circulaxly pola-
rized wave that is then incident on corner reflector 5. The phase of the reflected
ci rcularly polarized wave is now related to its angle of turn about the axis of
~ the beam guide: rotation of the reflector through angle * displaces the phase of
trie reflected wave by angle 2ii,, and consequently uniform rotation at frequency S2
produces a frequency shift of 2S2 in the reflected signal. When the circularly
polarized wave is reflected from the quarter-wave section, it is once more trans-
formed to linear palarization. It passes freely through grid 2, and is split on
grid 1: half the power (1/4 the power of the input signal) goes to output flange 8
from which it can be directed to the measurement channel of the circuit.
Tmprecision in tuning section 3-4 to the quarter-wave differential phase shift, or
frequency dependence of the phase shift.for fixed tuning of the section leads to a
spurious component in the spectrum of the output signal. When the phase shif"t
deviates from the nominal (n/2) by an amount d, an elliptically polarized wave
appears at the output of the quarter-wave section the.t can be represented as two
companents with orthogonal circular polarization. Upon reflection from the rotat-
ing corner reflector the useful component is shifted in frequency by (f)252, and the
spurious component acquires a"mirror" displacement by (+)252. After secondary re-
flection from the phase section and splitting by grid 1, we get a useful signal at
the output (flange 8) of the form 2 cos' 2 sin(m(�)24)t and a spurious signal on the
"mirror" frequency ~ rin. 2 sin(w(~)2i2)t. In addition, a signal sin d cos 2SZt sin wt is
rPflected from grid 2 to flange 10 that contains components with frequency w+ 20
and w-?Q. A signal on the difference frequency 411 is induced at the output of a
detector connected to this flange. Fine adjustment of the phase section to the
qua.rter-wave phase shift in the working device can be conveniently done with re-
spect to the minimum of this signal, or with respect to the minimum of the detected
si.qnal on frequency 411 at the output 8.
In essence, this device is a phase shifter of the frequency of the reflected wave
in which a system
of polarization splitters isolates 1/4 of the power on the dis-
placed frequency.
If a circulator had been included, it would have been possible
to convert all the
power to the signal on the shifted frequency. However, there
are no circulators
for tYie submillimeter band, and therefore the phase frequency
shifter was based
on rotating corner reflectors. This device converts all the
power that reaches
it to signal power on the shifted frequency, i. e. it is a phase
shifter of the tra
nsmitted wave frequency [Ref. 51 (Fig. 2). In pola.rization beam
.
splitters 6 and 7 the grid wires form an angle of
45� to one another. The two ad,jacent arms of
splitter 7, lying to either side of the grid, are
closed by 90-degree dihedral corner reflectors 3 and
4 placed on the ends of the one-piece shaft of motor
5 and turned through 90� relative to one another.
In arms I and II are 1+5-degree beam guide bends with
movabl P reflectors in front of whicr are wire grids
that form quarter-wave differential phase sections
1 a.nd 2.
Fig. 2
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cvA vrraa.ana. vua: v,....
E Einw ET;,,
out
Eout
w�p~
EIoui ;73~~7
Fig. 3
Direction of
wires of grid 7
Grid 6
Tnput electromagnetic wave Ein (Fig. 3) passes through grid 6 without attenuation,
and is split by grid 7 equally between the two arms of the splitter EIin and EIIin�
'I'he orientation of grids of sections 1 and 2 is chosen so that if a wave witYi-
left-hand circular polarization is excited on the output of section l, a wave with
right-hand polarization is excited at the output oY section 2, or vice versa. In
this event the waves reflected from corner reflectors 3 and 4 acquire a frequency
shift of the same sign (-252 or +251), depending on whether the directions of circu-
lar polaxization and rotation of the corner reflectors do or do not coincide. As a
result, two waveforms with orthogonal linear polarization on the displaced fre-
quency show up on the section of beam guide between grids 7 and 6. Waveform Elout
that is produced in arm I is polarized paxallel to the wires of grid 7, while Ellout
that is formed in axm II is polarized perpendicular to these wires. Since corner
reflectors 3 and 4 are turned through 90� relative to one another, one of these
waveforms acquires an additional 180-degree phase shift, a.nd the resultant wave
Eout is polarized parallel to the wires of grid 6, and is reflected by this grid
to output flange 9� Thus a transmission frequency shifter circuit can be made
by using a rotating system of two reflecting dihedral co�rner reflectors without the
aid of a circulator.
Let us denote deviations of the differential phase shift in sections 1 and 2 from
7r/2 by dl and 62 respectively. Then in output channel 9 we get useful sigr.al
Ec _ 2(I.}. ~s a' 26' coa b' ~ a') sin (m~ ~f 22) ~
and spurious signal on the "mirror" frequency
a
2- Cps a' 2 a' cpy b' Z') sin 24) t.
When 6, = 82 = b, the a.mplitudes of these signals will
be cos 2 and sin22 respec-
tively, and the level of the waveform on the "mirror" frequency with respect to the
useful signal on the shifted frequency will be tan 2. In auxiliaxy channel 10 we
p;et components: polarized perpendicult3x to the wires of grid 7 El -gin8,cos20tsincnt
and para11e1 to these wires E u-sin b, cos 29t sin dl. By adding a detector to arm 10 that
receives one of the polarized signals, we can carry out separate tuning of sections
1 and 2 to the quarter-wave differential phase shift with respect to the minimum on
frequency 4S2 � �
The described frequency shifters were made on the basis of a hollow dielectric bea.m
guide 20 mm in diameter; wire grids were used with a period of 30 um and wire 8 um
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in diameter. Frequency shifters with tunable phase sections operated in a wave
band of 0.5-2.2 mm. With fixed tuning of the phase sections, the level of the
spurious component of the output signal spectrum relative to the useful signal on
the shifted Prequency was less than -40 dB in the range of �15% of the tunEd fre-
quency of the sections. The speed of rotation of the corner reflectors reached
9000 rpm, where the frequency shift was 300 Hz. Attenuation in the beam guide
eystem of the device was about 1 dB on a 0.5 mm wave, and increased to 3 dB toward
ttie long-wave section of the band.
REFERENCES
1. M. S. Yanovskiy, B. N. Knyaz'kov, IZV. WZov: RADIOELEKTROIJIKA, Vol 13, No 10,
1970.
2. B. N. Kriyazkov, M. S. Yanovskiy, RADIOTEIgiNIKA, Vol 27, No 9, 1972�
3. R. N. Knyaz'kov, Ye. M. Kuleshov, M. S. Yanovskiy, "A Quasioptical Phase
5hifter," USSR Patent No 439866. ,
4. A. I. Goroshko, Ye. M. Kuleshov, in: "Radiotekhnika" [Radio Ehgineering, a
Collection of Papers], Khar'kov, Khar'kov State Univ., No 21, 1972�
5. M. S. Yanovskiy, B. N. Knyaz'kov, "A Modulator of the Plane of Polaxization,"
USSR Patent No 508895.
CUl'YRIGHZ': "Radiotekhnika", 1980
( 86-661.0 ]
6610
cso: z86o
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UDC 621.383.98
CfiUUSING THE LOAD RESISTANCE OF A PHOTODIODE IN PULSED OPTOELECTRONIC SYSTEMS
Moscow RADIOTEKHNIKA in Russian Vol 35, No 10, Oct 80 pp 72-74 manuscript received
10 Apr 80
[Article by F. I. Khaytun and I. Ye. Zamanska,ya]
[Text] The ever increasing use of high-resistance photodiodes in pulsed lidar and
optical communication systems combined with the current trend toward shortening
transmitted signals (to tens of nanoseconds and less) makes it necessary to account
f'ar the influence that time lag of the photodetector circuit has on the character-
istics of systems, and to use care in choosing the parameters of the photodetector
circixit for different signal processing requirements in the reception channel.
Thus the problem arises of rational choice of the load resist&nce RH of the photo-
diode not only for optimum reception [Ref. l, 21, but also under conditions where
the passband of the channel is maintained constant (preset), and may differ con-
siderably from the optimum when RH = var.
Principal Relationa. Notation on the block diagram of the reception channel (Fig.
1): Oc(t)--signal flux on the photodetector; E--current sensitivity of the photo-
diode; ic(t), S(iw)--signal photocurrent and spec-
141 trum; G1 = 2eI0 + 1+kTO/RH--spectral noise density of
octv the photodetector circuit; Ip--constant component of
photodiode current; e--charge of the electron; k--
Bj ~t Boltzmann's constant; T�--absolute temperature;
G2 = e2/,.RH--equivalent spectral noise density of the
Fig. 1 ampliKer (with respect to current); K1(iw)=(l+iwT)-1
--transfer function of the photodetector circuit;
T= RHC; C--overall capacitance of the input circuit; K2(iw)--transfer function of
the aznplifier.
The transfer function of the channel, which differs from the optimum in scaling can-
version, takes the form [Ref. 31
aS' (1me-iu.t.In
K(~m) - Ko~ (idln) ~ Q~t Q~il ~(wln) I'i
and signal-to-noise ratio u for symmetric input pulses takes the form
t
2 2 ('~1S(f r)) IS (i'�jn)jd"
(xG, ) J 1.} ne mT' *'1n2
6
P ~
(1 + -F ~7'' I S (~..!n} dd
1c �
3 (1 ni t mT'e'in'r'
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where m = m(RH) = G2/G1.
Functions n(RH) at amT = const with other parameters of the reception system prede-
termined can be calculated by using an expression for the effective noise passband
of the channel:
�
~ IK 0ts))' d.
0 + ne)' ~ IS (t~./n) 1' dr
emr- K, (0) ~ S+ (p) ~ (1 m =T� *�/fi+y �
Next let us consider a gaussian signal ic(t) =AEe'n(t/;)2, where A is the amplitude
of radiant power on the photodetector; t is duration of the signal pulse on a level
of zo.5max.
After rather lengthy integration and a number of transformations, we can get from
expression (1)
2 y'Y M, `12
Ac 1~s 1 + n./ H (P~1
~ ce, P{H (p) 11 -2p'+n' (I t21')l + -y U - n')}~~~ .
where
a - P(Rr) - T Kt -F m0nmI '12 - (z! /Fx;, c) (2.l, + 4Kr/R, + y /R.2)'12 . (3)
ro
n' + 1 112 2
CT--) , H(x) - x[ I- eri (x)] eX,, eri (x) --y-77, e X' dz.
With optimum filtration (n = 1) we get from (2)
4
~14f - A� [T+N (A)] 112lVltg Cir P.
The degree of relative reduction in signal-to-noise ratio due to departure from the
optimum filtration conditions ca.n be characterized by the expression
� 2In!(1 + n)'1"' H (a,)
H'12 (p) { H (p) [f - 2P' + n' (I + 2p')l + -1f.- (I - n')
Thus at a given value of n# 1 the quantity a depends only on the para.meter S that
gives a generalized characterization of the influence that the time lag of the
photodetector circuit has on conditions of signal detection. Having determined
function n(S), we can find u(~), a(S) and for other predetermined parameters with
consideration of (3), we can find relations u(RH) and a(RH).
For the width of the passband of the channel we can write the expression [Ref. 41
2 V2 sn I N (p) (1 - 24') -F ~P' I
(4)
n= 1, formula (4) defines the optimum width oP the channel passband. Let us
At
assume that the quantity AwT must be fixed from the condition
Aeez " OMc/b - 'X v'f/tb. (5)
where Awc is the effective width of the signal spectrum, b=const. Then from (4)
and (5) we find thc required value of the coefficient of relative widening of the
passband:
7?
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n - ~H (a)cl - 2a~ + Y2,~ a~ .
Resulta of Calculations. Calculations were done as applied to the following initial -
parameters of the system:
T=20 ns (Afc =Awc/2n=17.7 Mf?z), I0 =10-7 A, C=10 pF,
ey = 2.45 �10'9 V/Hzh , b=1, 2, 3(of-r = eWT/2,r =17.7 MHz, 8.85 MHz, 5�9 MHz) .
a
T
J 5/7; T J 6 A7'r t 3 S AS 2 J RN, 0
Fig. 2 Fig. 3
Shown in Fig. 2 are curves for u(RH) for the three assumed values of AfT, a.nd also
the curve for M(RH) corresponding to optimization of the channel passband for each
_ value of RH (broken curve).
If the fixed passband of the cha.nnel is wide enough, curve u(RH) may have an ex-
tremum (curve 1), in which case an increase of RH beyond some limit (here about
104 SZ) result s in some reduction of signal-to-noise ratio. Even if the maximum of -
u(RH) is faint or nearly absent (curves 2, 3), the Iimits of effective increase in
RH at aPT = co nst may be considerably displaced as compared with optimum filtration.
For example at AfT = 8.85 MHz (curve 2) the limit of practically feasible increase
- in RH does not excee3 (2-3)�104 SI, whereas with optimum filtration this limit is
approximately 107 S2.
'Phe resultant data also show the price paid for expansion of the channel passband
from the stan3point of conditions of signal detection. For example increasing
- AfT from 5�9 MHz to 17.7 MHz reduces u by a factor of approximately 2.2 (with the
most favorable choice of RH) .
The loss in [a] as compared with optimum filtration is even greater, as shown by
curves for a(RH) in Fig. 3� .
~
The results may be of use in development of pulsed lidar and optical communication
systems with photodiode receivers.
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REFERENCES
- 1. G. V. Voyshvill.q A. M. Romanov, Y e. G. Lebed' ko , RADIOTEKHNIKA, Vol 25, No 10,
197o.
P. V. A. Markln, UPTIKO-MPKHANICHESKAYA PROMYSHLENNOST', No 12, 1973.
3. F. 1. Kha,ytun, Ye. G. Lebed'ko, OPT IKO -MEKHANI CHESKAYA PROMYSHLENNOST' , No 11,
- 1970 .
4. R. B. Shemshedinov, F. I. Khaytun, Ye. G. Lebed' ko , OPTIKO-MEKHANICHESKAYA
- PROMYSHLENNOST' , No l, 1978. ,
COPYRIGIiT: "Radiotekhnika", 1980
[86-66.io]
6610
cso: 186a
J
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UDC 535.8
LIGHT VALVE SYSTEMS WITH LASER LIGIiT SOURCE
Leningrad PRIBOROSTROYENIYE in Russia.n Vol 23, No 9, Sen 80 pp 77-80
[Article by V. V. Khvalovskiy, S. N. Natarovskiy, Yu. V. Fedorov, Leningrad Insti-
tute oF Precision Mechanics and Optics]
[Text] A study is made of the special operating characteristics of a
light valve system with a coherent light source. Various versions of
the construction of the optical system are investigated.
In modern light valve inetruments most frequently powerful and superpowerful thertnal
sources, Yor example, superhigh pressure xenon tubea, are used as the light source
- for displaying non.absorbing objects (for exaruple, of the thermoplastic recording
type). Thia arises, on the one hand, from the small admissible size of the source
(resCricted by the minimum angle of diffraction on the object) and, on the other
hand, by the neceesity for obtaining quite high illumination of the image.
The application of the indicated sources makes the heat balance of the instrument
appreciablq worse. In order to reduce the heating, the circuitry and the structural
design of the instrument are complicated by in!;roducing heat filters, thermal insu-
lation and f orced ventilation. In addition, tte presence of a continuous radiation
apectrum in the visible and infrared ranges of this type of source leads to the
fact that the contrast transmission function of the projection objective on all
epatial frequencies, in addition to zero, is less than one, that is, the image con-
trast of the fine details of the object is lowered [1]. All of this has a negative
effect on the operating and technological characteristics of the instruments.
The use of a laser [2] with focusing lena of the light source in a light valve sys-
tem permits the thermal heating characteriatic of thermal sources and the reduction
_ in image contrast to be avoided, but the grainy structure of the inage in this case
lowers its quality which is exhibited especially sharply in visual type instrumente.
Then the image coneista of so-called aventurine dota. This def iciency is controlled
- by illuminating the object with the scattered laser 1Lght beam [3]. Frosted glass
or liquid 'media with randomly moving particles (foz example, a milk solution in
waCer or liquid crystals) are used as the dispersing agent. However, these disper-
eion techn.iques lead to losa of coherent illumination and, consequently,to loss of
image contrast of the small details of the object [4]. In addition, they have
little advantage energywiae.
The graininess of the image can be reduced signif icantly by installing a lens raster
in the light valve projector system, The optical syst~.n, can be built, as is shown
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in Figure 1. It operates as follows: laser 1 emits a monochromatic light beam of
essentially parallel rays which are scattered by the lens raster 2 in the volume of
space limited by the raster aperture. The light bea.ms completely fill the input
aperture of the condenser 4 by means of the collector 3. Af ter passage through the
condenser, the light beams illuminate the nonabsorbing object S and reach the pro-
,jection objective 6. The light beams which have passed through the object without
refraction (diffraction) on its relief are screened out by the blank 7 and do not
- participate in Che structure of the image. The light rays which undergo refraction
(diffraction) on the object are not screened out by the blank 7 and construct the
image of the viewed object on the screen 8.
Figure 1.
In this system the viewing diaphragm (or blank) 7 is installed in the rear equiva�
lent f ocal plane of Lhe entire optical system including the condenser and the pro-
jection objective i,n. itself, and t::p le*.s raster is installed in theplane con3ugate
to the entrance pupil of the illuminating part of the system. The installation of
the lens raster in the indicated plane permits the interference conditions on the
microunevennesses of the object to be altered in such a way that the graink- struc-
ture of the image is decreased to limits such that its influence becomes insignifi-
cant (it goea beyond the limits oz resolution of the projection objective). Other
veraions of execution of this system can be used (see Figures 2, 3).

k'igure 2.
The operation of the optical system shnwn in Figure 2 is analogous to the operation
of the preceding one. The advantage of this optical system is that the lens raster
3 installed between the collector 2 and the condenser 4 operates in a wider light
beam and, consequently, a larger number of lens elements of ths raster 3 participate
in the scattering of the light. Therefore, damage to one or several elements of
the raster in practice does not disturb its properties 8s a light dispersing medium.
Thus, it ts possible to lower the technological requiretnents on manufacturing the
lens raster. '
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.3 4 S 6 `7
- - - - 1.
_ j.' ~ � . ~
ow -
~l � ' ` I_ J 1
Figure 3.
The operation of the system presented in Figure 3 is also analogous to the one in-
vestigated above. A characteristic feature of this system ia the fact that the lens
raster 2 plays the role of a collector in addition to the role of the light beam
dieperaing medium. This simplifies the optical sys[em (the total number of optical
surfaces decreases), and it increases its physical lens speed, for the transmission
coefficient of the system is increased somewhat.
The application ;f a laser as the light source insures coherence of the illumina-
tion for which the normalized contrast transmission function of the projection ob-
jective and all the reuiaining optical elements is constant with respect to the en-
tire frequency pass band of the optical system, and it is equal to or.e. Thus, the
image contrast of the viewed nonabsorbing ob3ect is undistorted (:,:z_th small residual
aberrations of the projection objective), and maximal with/respect to magnitude.
In addition, it is expedient to use a lens raster in the system which permits redis-
tribution of the light beam energy to be obtained without '.oss of degree of coher--
ence, for which the graininess of the image is significantly reduced, and the mode
structure is entirely absent. In practice complete absence of heating of the ele-
me;ts of the optical system permits us not to use the hest protection means, which
significantly simplifies the structural design of the light valve projector. In
Figure 4,a [not reproduced], a photogZaph of the image of a phased test object is
presented which was obtained on a mockup of a Schli.eren projector constructed by
the diagram in Figure 2, and an image of the same object illuminated directly by a la-
ser lightbeam from which the lens raster has been taken out is presented for compari-
_ son in Figure 4,b [not reproduced].
BIBLIOGRAPHY
- 1. J. Goodman, VVEDENIYE V FUR'YE-OPTIKU (Intrnduction to Faurier Optics), Moscow,
Mir, 1970.
- 2. V. M. Vaksman, G. V. Mikhay].lk, "Mapping of Phased Images in a Schlieren Pro-
jector with a',Coherent Light Source," ZHURNAL NAUCFVOY I PRIKLADNOY FOTOGRAFIZ
I KItIEMATOGRAFII (Journal of Scientif ic and Applied Photography and Kinemato-
graphy), Vol 22, No 6, 1977.
3. L. M. Soroko,.OSNOVY GOLOGRAFII I KOGERENTNOY OPTIKI (Fundamentals of Holography
and Coherent Optics), Moscow, Nauka, 1971.
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4. A. S. Toporets, "Interrelation of the Degree of Coherence of Diffusely Scattered
Ligh[ Uaiag the One Slit Method," OPTIKO--MEKHANICHESKAYA PROMYSHI.ENNOST'
(Optical-Mechanical Industry), No 11, 1975.
Recommended by the Department of Optical Manuscript received 11 Apri.l 1979
Devices Theory
COPYRIGHT: "Izvestiya vuzov SSSR - Priborostroyeniye' 1980
- [8144/0258-10845]
10845
CSO: 8144/0258
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' 83
= FOR OFFICIAL USE ONLY
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PUBI,ICATIONS, INCLUDING COLZECTIONS OF ABSTRACTS
UDC 621.396.029.64:621.753.001.24
CALCULATING FRODUCTION TOLERANCES OF MICROWAVE DEVICES
Leningrad RASCHET PROIZVODSTVENNYKH DOPUSKOV USTROYSTV SVCh in Russian 1980 signed
to press 14 Jan $0 pp 2, 145-147
[Annotation and table of contents from book "Calculating Production Tolerances of
Microwave Devices" , by Yevgeny Aleksandrovich Vorob'yev, Izdatel'sCvo "Sudostroyeniye",
3700 copiea, 148 pages]
[Text] The book examines methods of calculation and rational designation of pro-
duction tolerances for microwave components, microwave assemblies and standard
microwave devices niost extensively used at the present time ii: gr.ound-based, ship-
borne an,d airborne radar and radionavigation facilities as well as in microwave
monif~nring and measurement instrumentation.
The main thrust of the book is to present up-to-date methods of calculating pro-
duction tolerances and studying the most successful engineering design decisions
Chat ensure high tEChnical quality of electronic equipment in the microwave band.
The book is intended for radio engineers and technologists working in the area of
developing and producing microwave devices, and also for instructors, graduates and
undergraduate students in the electronics departments of colleges and universities.
Contents
_
3
Preface
Chapter 1. Particulars of Calculating the Production Tolerances of Struc-
5
tural Elements of Microwave Devices
5
1.1. Introductory remarks on methods of calculating production tolerances
_
1,2, Principal definitions
1.3. Statistical and analytical computation methods of determining the
9
influence of production errors
10
1.4. Differential methods
12
1.5, The method of conformal transformations
14
1.6. The method of small perturbations
16
1.7. The method of the auxiliary coordinate system
ction Tolerances for Roughness of the Conductive
d
P
u
ro
Chapter 2. Calculating
17
and Dielectric Surfaces of Microwave Structures
roblem of the influence that roughness of
th
i
e p
ng
2.1. Formulating and soZv
ductive anci dielectric surfaces has on radio engineering parameters
con
and characteristics of microwave structural elements
17
84
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2.2. Tolerances for roughness of conductive (metal) surfaces of microwave
structural elements
2.3. 2olerances for surfacea of dielectric (radiotransparent) components of
mi,,rowave structural elements
2.4. Examples of cal cuiation of production tolerances for roughness of the
working surfaces of microwave devices
Chapter 3. Calculat ing Production Tolerances for Manufacture and Assembly
of the Co nnecting Elements of Waveguide Channels
3.1. Initial premises
3.2. Technological d esign characteristics of connections
3.3. Calculation of production tolerances for manufacture and assembly of
waveguide connections
3.4. Electric strength of waveguide connections as a function of errors in
manufacture and assembly
3.5. Optimizing assembly of waveguide channels with respect to criteria of
minimum reflectivity and minimum losses
Chapter 4. Calculat ion of Production Tolerances of Microwave Cavities
4.1. Functional and design particulars of microwave cavities
4.2. Relation betw een the parameter.s of oscillatory systems and technological
errors in their manufacture
- 4.3. Principles of exact analysis of structural elements of microwave cavities
4.4. Calculation of production tolerances of structural elements of microwave
cavities 4.5. Problema of optimizing the structural elements of microwave cavities
4.6. Calculation of production tolerances for an echo chamber structure
Chaprer 5. Calculat ion of Production Tolerances of Functional Components
of Microwave Systems
_ 5.1. Purpose and par ticulars of designing functional components
5.2. Relation between the parameters of functional microwave components and
technological errors of structural elements
5.3. Equations or pro duction errors of the functional microwave components
5.4. Calculation of production tolerances of the structural elements of
functional microwave components
5.5. Optimizing the structural elements of functional microwave components
Chapter 6. Calculation of Production Tolerances of Microwave Antennas
6.1. Calculation of production tolerances of reflective microwave antennas
6.2. Calculation of p roduction tolerances of lens antennas
6.3. Calculation of production tolerances of the structural elements of
antenna arrays
Chapter 7. Calculation of Production Tolerances of Antenna Housings
7.1. Classif ication and technological design characteristics of antenna
housings
7-.2. Calculation of production tolerances of flat, cylindrical and spherical
encloaures
7.3. Calculation of production tolerances of pointed housings
Chapter 8. Calculation of Production Tolerances of Microminiature Microwave
Devices
8.1. Brief description of microminiature microwave devices
8.2. Calculation of s tripline production tolerances
8.3. Calculation of production tolerances of resonant elements based on
striplines
85
FOR OFFICIAL USE ONLY
18
25
27
32
32
32
37
42
45
55
55
56
59
63
65
67
70
70
72
78
79
83
86
86
89
97
103
103
106
113
123
123
124
135
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8.4. Calculation of production tolerances of the simplest elements of microwave
microcircuits 137
141
Conclusion
142
References
COPYRIGHT: Izdatel'atvo "Sudoatroyeniye", 1980
[91-6610J
_ 6610
cso: 1860
's
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86
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vnc 681.883.67(075�3)
HYDROACO?JSTIC TRANSDUCERS AND ANTENNAS
Leningrad GIDROAKUSTICHESKIYE PREOBRAZOVATELI I ANTENNY in Russian 1980 signed to
press 24 Apr 80 pp 228-230
[Annotation and table of contents from book "Hydroacouatic Transducers and Antennas",
by Gregoriy Mikhaylovich Sverdlin, Izdatel'stvo " Sudoatroyeniye", 3800 copiea,
232 pagesl
[Text] This is a textbook for intermediate special academic institutions in
specialty No 0649. It outlines the principles of operation of hydroacoustic trans-
ducers of the types most extensively used in tiydroacoustic ant.ennas, the theory of
directionalzty and the theory of calculating and designing hydroacoustic tra.ns-
ducers.
Met}iods of ::alculating and constructing hydroacoustic transducers and antennas are
presented.
'Z'he book contains examples of calculation of typical Y~ydroacoustic tra.nsducers and
antennas, and data in the form of rePerence tables and graphs.
The book is intended for students of technical schools and may be of use to those
attending colleges an d universities with major in applied hydroacoustics, as well as
to engineers working in this field.
Contents
Preface 3
Tntroduction 4
Chapter 1. Characteris tics of Hydroacoustic Transducers 7
1.1. Classification and major parameters of hydroacoustic transducers 7
1.2. Electromechanical and electroacoustic conversion 13
1.3. Characteristics of the emitter 18
1.4. Characteristics of the receiver 22
1.5� Requirements for hydroacoustic transducers 27
Chapter 2. Directional ity of Hydroacoustic Transducers and Antennas 29
2.1. Nature and evalua.tion of directional.ity 30
e.2. Directionality of solid antennas 36
2.3. Directionality of linear discr,-fte antennas 51
2.4. Radiation power of dir.ectional antenna . 62
87
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Chapter 3. F:lectrodynamic Transducers
3.1. The electrodynamic rsdiator
3.2. `Phe electrod}mamic receiver
Chapter 4. 1'ie2oelectric Transducers
4.1. The piezoelectric effect and its use Por hydroacoustic tra.nsducers
4.2. Piezoelectric bar transducers
4.3. The cylindricxl piezoceramic transducer
4.4. The spherical piezoceramic transducer
Chapter 5� Magnetostrictive Transducers
5.1. Magneto strict ion and its use for hydroacoustic transducers
5.2. Magneto strict ive bar transducers
5�3� The cylindrical magnetostrictive transducer
Chapter 6. Ca1cul.ating and Designing Hydroacoustic Tra.nsducers
6.1. Initial design data
6.2. Selecting the type of antenna transducer
6.3. Calculation of piezocera.mic transducers
Bar transducers
Cylindrical piezoceramic transducers
Segmented cylinder 6.4. Structural elements of transducers and antennas 'Piezoceramic transducers and antennas
Magnetostriction transducers
6.5. Calculating magnetostriction transducers
Bar transducer
C,ylindrical transducer
Chapter 7. Examples of Calculat ion of Hydroacoustic TransducerE
7.1. Flat multielement piezoceramic antenna.
7.2. Cylindr3cal piezoceramic antenna
7.3� Flat magnetostriction antenna
7.4. Measurement hydrophone
References
COPYRICHT: Izdatel'stvo "Sudostroyeniye", 1980
[88-6610]
E 6io
cso: i86o
88
FOR OFFICiAL USE ONLY
and Antennas
and Antennas
69
70
76
80
81
90
105
115
118
119
128
135
140
141
1.49
158
158
165
170
170
171
179
183
183
.192
195
195
207
214
221
227
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UDC 621.3.049.77:681.518.3
INTEGRATED ELECTRONICS IN MEASURING INSTRiJMENTS
Leningrad INTEGRAL'NAYA ELIICTROIVIKA V IZMERITEL'NYKH USTROYSTVAHIi in Russian 1980
signed to press 22 Apr 80 pp 2, 246-247
[Annotation and table of contents from book "Integrated ElectroniGa in Meseuring
- Inetruments", by Valentin Sergeyevich Gutnikov, Izdatel'stvo "Energiya", 40,000
copies, 248 pagesJ
(Text] The book deals with the use of series-produced analog and logic ICs for
making standard functional units of ineasurement devices. Particular att ention is
given to methods of designing various measurement transducers (including precision
amplifiers) based on integrated opa.mps. An examination is made of the particulars
of using integrated switches, multipliers, comparators and so on. Varieties of
- logic ICs are described as well as their use for realizing logic funetions, making
registers, counters, code-to-frequency converters and the like. The presentation
of the material is accompanied by a condensed theoretical a.nalysis. The examples
that are given are based on up-to-date Soviet ICs.
The book is intended for a wide class of specialists and studnets engaged in the
development and invest7gation of electronic measurement equipment.
Contents
I'reface
3
Chapter l. General Tnforma.tion on Analog ICs
5
1-1. Varieties of analog ICs
5
1-2. Integrated analog switches
7
Chapter 2. Integrated Opa.mps
14
2-1. General information on opamps
14
2-2. Equivalent circuit and parameters of the opamp
16
2-3. Opamp auxiliary circuits
24
2-4. Improvement of opamp parameters
29
2-5. Calculation of circuits tha.t contain opamps using directed graphs
34
Chapter 3. Amplifiers with Negative Feedback Based on Opamps
39
3-1. Inverting amplifier
39
3-2. Noninverting amplifier
6
3-3. Differential amplifiers
58
3-4. Current aiid charge amplifiers
59
3-5� Amplifiers with galvanically decoupled supply circuits
62
89
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C1iapter 4. Precision Measurement Amplifiers
6~
4-1. fteduction of multiplicative amplifier errors
69
4-2. Amplifiers with periodic drift correction
72
4-3. Amplifiers with signal modulation and demodulation
76
4-4 , '!'w^-channel amplifiers
83
4-5. Galvanic isolr~tion in measurement amplifiers
92
4-6. Noises of ineasurement amplifiers
Amplifiers with Current Output and Resistance-to-Voltage
bilizers
St
,
e.
Chapter 5.
107
Converters
107
5-1. Voltage stabilizers
5-2. Current stabilizers and amplifiers with current output
111
117
5-3. Resistance-to-voltage converters
123
5.-1~. Bridge type resistance-to-voltage converters
128
Chapter 6. Using Opamps with Lineax Frequency-Dependent Feedback
128
6-1. Principles of designing operational converters
132
6-2. Integrating operational converters
140
6-3. Active filters
'1~7
6-4. Resistance converters
149
6-5. Sine-wave signal generators
CYiaptzr 7. Using Opamps with Nonlinear and Controllable Feedback
15~
150
7-1. Average-value rectifiers
15~+
7-2, Pet~k-to-peak rectifiers
i56
7-3. Switching devices and phase-sensitive demodulators
160
7-4. Devices for sampling and storing a.n analag slgna7- .
161
7-5. Functional converters
165
Chapter 8. Using Opamps in Pulse Devices
165
p-L. Limiters and square-wave voltage shapers
169
8-2. Relaxation oscillators based on opamps
d controllable oscillators based on opamps
171
$-3. Kipp oscillators an
177
ChaX?ter 9. Special Types of Opa.mps �
177
9_1, ppe,Inps with current inputs
179
Q-2. Arialog signal multipliers
181
9-3. Comparators
182
Criapter 10. Integrated Logic Circuits
182
10-1. Basic prinriples of logic algebra
185
10-2. Varieties of logic ICs
188
10-3� Parameters of logic ICs
191
Chapter 11. Combination Logic Circuits
191
11-1. Minimization of logic functions
19~+
11-2. Synthesis of comb ination circuits
ly6
~.1-3. Examples of typic al combination circuits
199
Chapi:er 12. Flip-Flops
Varieties of flip-flops in the integrated modification
1?
199
202
.
12.2. Principles of des igning integrated flip-flops
205
12.3. Interference-itrmYUne flip-flops
206
Chapter 13� Registers and Ring Counters
206
13-1. Memory registers
207
13-2. Shift registers
209
13-3. Ring counters
Chapter 14. Binary Counters, and Counters Based on Binary Counters
212
212
14-1. Binary counters
215
14-2. $inary-decimal counters
90
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14-3. Counters with various non binary scaling factors
14-4. Reversible counters
14-5:. Synthesiz3.ng counters
Chapter 15� Using Logic ICs in Pulse Shapers and Pulse Generators
15-1. Pulse shapers
l5-2. Pul:+e genexators
Chaptcr i6. Special Components of Measurement Devices Based on Logic ICs
16-1. Synchronizing devi.ces
16-2. Frequency subtractors
16-3. Code-to-frequency converters
16-4. Using microprocessors in measurement devices
References
COPYRIGHT: "Energiya", 1980
[90-6610]
6610
cso: 1860
91
FOR OFF'ICIAL USE ONLY
221
223
226
229
2z9, .
234
235
235
237
238
241
243
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'A
uDC 681.84.083.8:534�14
MLASURING INSTABILITY OF THE SPEID OF A RECORDING MEDIUM
Moscow IZMEREPdIYE NESTA.BIL'NOSTI SKOROSTI NOSITELYA ZAPISI in Russian 1980 signed
to press 12 May SO pp 2, 102-103
[Annotation and table of contents from book "Measuring Instability of the Speed of
a
Recording Medium", by Mark Vladimirovich Laufer, Izdatel'atvo "Svyaz"; 2450 copies
104 pageal
[Te xt] An analysis is made of the instability of the speed of a recording medium

- based on the time scale function. An examination is made of the influence that
ttiis instability has on recording-playback processes for different kinds of data.
Me-thods and devices are given for measurements of speed instability in the record-
p].ayback mode.
`I'Yie book is intended for engineering and technica.l workers engaged in the develop-
ment arld aprlication of various devices for information recording and playback.
Contents
3
,
� intr.oduction
5
No-tation
6
Chapter 1. Analysis of Speed Instability
6
1 . _L . Time scale function
Rules of application of the time scale function in analyzing signals to
2
1
.
.
9
be reproduced
10
1.3. Time distortions
Time scale function and time distortions in a system of repeated elec-
4
1
.
.
10
trical transcription
play-
Analysis of the influence of periodic oscillations on recording and play-
1
5

.
back of harmonic and holographic signals
Analysis of the influence of speed instability in recording and playback
6
1
12
.
.
of a frequency-modulated signal
19
2~
1.7. Analysis of random speed fluctue.tions
play-
Lvaluation of the influence of s peed instability in recording and play-
8
1
.
.
28
back of audio signals
Influence of speed instability on recording and playback of pulsed and
1
9
.
�
29
video signals
Ctiapter 2. Methods of Measuring Speed Instability i.n the Recording Mo de
33
2.1. Measurements in photographic recording equipment by the method of visual
33
registration of sections of waveforms
92
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2.2.
Measurement in recording equipment by the phase method
37
2.3.
Measurement in ar~y kind of recording equipment by the frequency method
42
Chapter 3. Methods of Measuring Speed Instability in the Playback Mode
49
3.1.
Principles of ineasurement
49
3.2�
Influence of spurious amplitude modulation on measurement of speed
flUCt,Uf1tiQT1S
50
3.3.
lnfl.uencc of naise at the input of the speed instability meter
53
3�1+.
Principles of designing speed instability meters
57
3.5�
Factors that influence the error of FM and PFM signal conversion
62
3.6.
Methods of ineasurement in the playback mode
66
3.7.
Improving the resolution of speed fluctuation meters
68
3.8.
Principles of designing facilities for certification of speed fluctuation
meters
69
3.9.
Parameters of the display equipment used for measuring speed fluctuations
73
Chapter 4. Measurement of Average Speed
74
4.1.
Methods of ineasuring average speed
74
4.2.
Methods of ineasuring velocity drift
76
4.3.
Yroduction of a measurement waveform with consta.nt wavelength on a strip
_
chart
77
- 4.4.
Measurement waveform of any type with constant wavelength
78
Ctiapter 5. Devices for Measuring Speed Instability
80
5.1.
The IND-6 and IND-7 instrwr,ents for measurement by the phase method in
the recording mode
80
5.2.
7'he UIKS universal instrument for measurements in the recording and
playback mode
82
5.3.
The 41 arid G3-103 instruments for measuring speed fluctuations in the
plE,ybrlck mode
84
5.4.
'!'he IKS and AKS instruments for measurement and analysis of the speed
fluctuation spectrum in the playback mode
86
5.5.
The PI instrument for checking speed instability meters
89
- 5.6.
Comparative data of Soviet and non-Soviet ins+,ruments for measuring
speed instability
95
- Conclusion
95
Refe
rences
96
Sub,S
ect index
100
COPYRIGHT: Izdatel'stvo "Svyaz'", 1980
[89-E61o]
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cso: i86o
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FOR OFFICtAL USE ONLY
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UDC 621.396.62:[623.61:455.40]+621.317.757
PANORAMIC RECEIVERS AND SPECTRUM ANALYZERS
Moscow YANORAMNYYE PRIYIIKNIKI I ANALIZATORY SPEKTRA in Russian 1980 signed to press
15 Dec 79 pp 2> 348-350
[Annotation and table of
Analyzers'; by Valentin
Izdatel'stvo "Sovetskoye
352 pagea]
contents from book "Panoramic Receivers and Spectrum
Alekseyevich Martynov and Yuriy Ivanovich Selikhov,
radio", second revised and enlarged edition, 10,000 copies,
[Text] An examination is made of the principal methods of spectral analy5is and
t he flundamentals of design of panoramic receivers and spectrum analyzers. The pur-
pose and areas of application of panoramic devices are defined, and the requirements
a.re formi.il.ated .for their major characteristics. An analysis is made of physical
pxocesses in the main channels of these devices, and recommendations are given on
aptimizing their design under realistic operating conditions. Block diagrams of
pt111p2'ai(11C devices are considered as well as desi-gn variations and problems of dis-
playing, recording and processing the results of analysis. Descriptions are given
of some panoramic receivers and spectrum analyzers presently being used (the first
edition was published in 1964).
The book is intended for specialists working on development of the pertinent
equip-
men�t or using it to analyze radio emissions. It may be of use to instructors
and
- students in colleges and universities specializing in appropriate fields.
Contents
f'.r e fac e
3
4
Int.roduction
CtYapter 1. Yrinciples of Panoramic Radio Reception and Analysis of the
Spectra of Radio Emissions
8
1.1. Basic principles of frequency analysis
8
1.2. Parallel frequency analysis
16
1.3. Sequential frequency analysis
19
1.4. Combined f:equency analysis
22
- 1.5. Major qualitative indices of panoramic devices
24
Chapter 2. General Problems of Panora.mic Reception and Spectrum Analysis
32
1. Interrelation between ma.jor parameters of panoramic devices
2
32
.
2,2. Probability of signal detection and resolution
34
2,3. Spurious reception cY.annels and combination interference in panoramic
receivers. Selection of intermediate frequencies
53
94
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2.4.
Nonlinear distortions in the panora.mic receiver
5$
2.5.
Sensitivity and dynamic range oP the pannramic receiver
72
Chapter 3. Wide-Band Channel oP Panoramic Devices
79
3.1.
Purpose and ma,jor requirements of tlae wide-band channel .
79
3.2.
Optimum distribution of amplification in the wide-band channel
81
3.3.
Structure of wide-band channel
89
3.4.
Continuoua and discrete tuning of the wide band channel and panoramic
heterodyne
99
3.5.
Circuitr;y modifications of electronic tuning
106
- 3.6.
Circuitry particulars of stages of the wide-band channel
113
Chapter 1+. A:zalyzing Channel of Panoramic Sequential Analysis Devices
122
' 4.1.
Generr,,l information and formulation of the problem
122
4.2.
Transient processes in the resonant amplifier
124
I 4.3,
Possibilities of practical realization of a bell-shaped curve of the
narrow-band channel
135
4.4,
Use oF integrators in the narrow-band channel
145
Chapter 5. Methods of Improving the Indices of Panoramic Devices for Sequen-
tial Analysis
157
5.1.
Formulation of the problem
157
5.2.
Method of variable speed of analysis
159
5�3.
Damping oscillations in the circuits of the nrirrow-band channel
177
5.4.
Automatic Gain Control and Logaxithnic Amplifiers
182
5.5.
Using double differentiation of signals in the narrow band channel
190
5.6.
Sequential analysis with time compression of signals
198
Chapter 6. Pa,noramic Devices for Parallel and Combined Analysis
206
6.1.
Block diagrams of devices for para11e1 and combined analysis
206
6.2,
Transient processes in the narrow band channel
219
6.3.
Narrow-band channel of a panoramic device for para11e1 analysis
225
6.4.
MetYaods of forming the characteristics of a narrow-band channel
235
Chapter 7. Promising Methods of Spectral Analysis
239
'j.l.
Dispersion-time devices for spectral analysis
239
7.2.
Spectrum analyzers of recirculation type
244
7�3.
Acoustico-optical methods of spectral analysis
251
7.4.
Digital methods of spectral analysis
255
Chapter 8. Displa,ying, Recording and Processing the Results of Analysis
271
8.1.
Requirements for display devices
271
8.2.
CRT displays
275
8.3.
Displays of other types. Recording devices
293
8.4.
Scale devices
301
$.5.
Some questions of processing the results of analysis
308
Chaptcr 9� Practical circuits of Panoramic Receivers and Spectrum Analyzers
314
9.1.
General information
314
9.2.
Panoramic receivers for the long, medium a.nd short wave bands
317
9�3.
F'anoramic receivers for the microwave band
323
9�4.
Spectrum analyzers for para11e1 analysis
329
9�5.
Spectrum analyzers for sequential analysis
337
References
341
Sub,ject index
345
COPYRIGHT: Izdatel'stvo "Sovetskoye radio", 1980
[87-66io]
66io
cso: i86o
95
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UDC 621.313.13:537.228.1
PT.C7.OELECTRIC MOTORS
Moscow P'YEZOELEKTRICHESKIYE DVIGATELI in Russian 1980 signed to press 12 Mar 80
pp 2, 109-110
(Annotation and table of contents from book "Piezoelectric r;otors", by Vyacheslav
Vasi.t'yevich Lavrinenko, Igor' Aleksandrovich Kartashev and Vladimir Sergeyevich
Vislnevskiy, Izdatel'stvo "F.ne.rgiya", 7000 copies, 112 pages]
[Text] A 4tudy is made of the structural designs and the mechanism of the opera-
tion of variou.g piezoelectric motors; their specifications are presented.
Recommendations are made with respect to the engineering-design of the indicated
motors. The problems connected with the development of power supply for piezo-
- el.ectric motors and also the problems of the manufacturing technology for such
motcir.s ancl the problems of ineasuring their characteristics are investigated.
'1'he book is designed for engineers working in the field of building and using
e.lectric motors and also for engineering-technical workers involved with the design
of radioelectronic equipment.
Contents
Foreworcl
Page
3
Chapter 1. Physical Principles of the Operatic:i of Piezoelectric Motors
, 5
1.
liistorical information
5
2.
Paddle principle
8
3.
Fiezoelectric effect
10
4.
Resonance in a piezoelectric plate
10
5.
Transverse force
12
6.
Trajectory af motion of the end of a piezoelement at the point of
7.
contact with the rotor �
Eslements of the piezoelectric motor and a description of its operation
13
15
8.
Selection of oscillator dimensions
18
9.
Trajectory of motion of the contact point
19
10.
Jamming. Angular rotation rate of piezoelectric motor
23
11.
Fastening and clamping the oscillator
26
12.
Efficiency
29
13.
Wear-resistant spacers. Piezoelectric motor life
32
96
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Clinpter 2. Influence of Accompanying Electromechanical E�fects on the
Psr.ameters of Piezoelectric Motors 34
14. Bendiug vibrations with respect to the width of the oscillator.
Contact spot 34
1.5. Spurious rotor vibration modes 35
Ib, Acoustic noise of piezoelectric motors 37
17. Rotor material. Input impedance of a piezoelectric motor 39
(:hapter 3. Structural Designs of Piezoelectric Motors .
43
18.
Nonreversib.te piezoelectric motors with excitatian of compression,
tensile and bending deforroation
43
1.9.
Piezoelectric motors with passive rotor and excitation of shearing
vibrations
45
20.
Piezoelectric.motors with passive rotor and excitation of torsional
vibrations. Piezoelectric motor with passive stator
47
21.
Piezoelectric motors with prot;:uding spacers
50
22.
Reversible piezoelectric motor with active rotor and stator
52
23.
Reversible piezoelectric motors with electrical excitation of
longitudinal and bending vibrations
56
24.
Reversible piezoelectric motor with monomorphic oscillator and
using the jamming effect
59
25.
Piezoelectric motor with excitation of longitudinal and transverse
-
vibrations
61
_ 26.
Contrvl of tile speed of a piezoelectric motor. Motors with mechanical
reverse
64
27.
Methods of i.ncreasing the power of piezoelectric motors
67
28.
reed voltage of piezoelectric motors
70
Chapter 4. Equivalent Plagrams of PiezoeJ_ectric motors 74
Equivalent diagrams of the piezoelement of a piezoelectric motor
with longitudinal and bending vibrations 74
30. Principles of constructing the equivalent diagrams of piezoelectric
motors with passive rotor 76
31. I:qtiivalent diagram of a piezoelectric motor with zero contact angle 77
32. Force direction transformer 79
Chapter 5. Measuri.ng the Parameters of Piezoelectric Motors and Their
Power Supply. Application of Piezoelectric Motors 81
33. MeaGUring the parameters of piezoelectric motors 81
34. Power supplies of piezoelectric motors 83
35. VoltaKe converter with current feedback 85
36. Voltafie converter with master oscillator 87
37. Application of piezoelectric motors 90
Iiihliography 106
COPYRIGFIT: Izdatel'stvo "Energiya", 1980
(57-10845]
10845
CSO: 1860
97
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UDC 621.391.037.372
DICITAL DATA TRANSMISSION IN RADIO COMMUNICATIONS
Moscow TSZFROVAYA PEREDACHA INFORMATSII V RADIOSVYA7.I: in Russian 1980 signed to
press 6 reb 80 pp 2, 254-255
[Annotati.on and table of contents.from book "Digital Data Transmission in Radio
Communications", by Mikhail Semenovich Nemirovskiy, Izdatel'stvo "Svyaz
6500 copies, 256 pages]
['i'ext] This book contains a brief discussion of the problems of constructing
digftal data transmission systems. The paper consists of several parts, each Qf
wh ich is devoted to a group of closely related problems and devices.
'fh e first part of the book discusses the problems of analog-to-digital and digital-
to-anal.og conversions during data transmission. Admissible accuracies of conver-
sl on of analog data to digital form with PCM modulation and 0-conversions, means
oF optimizing the parameters of the corresponding devices, methods of achieving
- coirversion accuracies close to the potentially possible accuracies are analyzed.
A ciescr.ipt:[on is also presented of inethods of converting digital data to an
nn alog signal designed for transmission over communication channels with restricted
, pZSS band.
1'lie second part of the book discusses the prob lems of demodulation of digital
radio s.ignals in the presence of interference. 1fie noiseproofness of the basic
keying methods is defined considering signal distortions in the filter sections
of the receiver. A description is given of the structure of the corresponding
rec:eivers, and the noiseproofness losses caused by nonidealness of individual
ser.tions of the structure are estimated. '
Tn the th ird part of the book a Gtudy is made of the problems pertaining to the
notse-proof encoding of digital data. The structure of block and super-precise
codes and the principles of constructing economica'1 decoders are described. The
efCectiveness of the various codes is estimated as a functioii of the keying
mechod used in the rad.io line, the amount of instability of the carrier frequency
and other parameters.
'I'he f.ourtli part of the book is devoted to the study of the noiseproofness of
aiitomatic frequency control systems and Gadence synchronization systems widely used
in the receivers of digital commvnication lines. Recommendations are made with
respect to optimizing the parameters of these systems.
98
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~
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In the fifth part of the book a description is preaented of the basic methods
of time multlp.texl.ng and sharinR of digital signal; known methods of asynchronous
.tnpuC are nnalyzed; the characteristics insured by them and the efficient areas
nF use of each o� these methods are defined.
Tlie sixth part of the book is on the specific problem of multistation access
occurring when building prospective comanunication lines with the radio relay on
fln artificial earth satellite. The basic methods of multistation access are
described, and their energy efficiency is defined.
Tlius, the book material fanu liarizes the reader with the basic ideas of the car.responding areas of engineering, the results achieved and the prospects for
further development. The discussion is carried to the calculation relations
suitable for usP in engineering practice and includes a number af original results.
The book is intended for scientific workers involved with the development of
communications equipment, �
There are 99 illustrations, 15 tables and 67 references.
Contents Page
~ Foreward . 3
! PAJZT I. Analog-to-Digit Conversions 7
Cliapter 1. Discretization of Analog Signals 7
1.1. General information about analog-to-digital conversione 7
1.2. Kotel'nikov theorem 9
1.3. Frrors of discretization 15
Chnpter 2. PCM Conversion 18
2.1. Quantization of random variables lg
2.2. Errors and optimization of PCM conversion parameters 21
2.3. Ef.fect of errors that occur in the comnunications channel 25
f:hapter 3. 0-Conversion 27
3.1. Errors and optimization of the parameters of classical
A-conversion 27
3.2. Effect of communications channel noise on the classical
0-conversion error 35
3.3. Ver.sions of the A-conversion algorithms 37
Ctiapter 4. Data Transmission over Analog Channels 41
, 4.1. Selecting the shape of signals 41
4.2. Methods of signal shaping and reception 45
99
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PART II.
NOISE IMMZINITY
OF DIGITAL DATA TRANSMISSION OVER RADIO
CHANNELS
WITH CONSTANT PARAMETERS
51
Chapter
S. Transmission
of Di.gital Signals through Linear Elements of
Ctie ReceivinK Ghannel
51
5.1.
Tr.ansmission of
video signals through low-frequency filters
51
5.2.
Transmission of
keyed signals through band filters
54
Ch1pter 6. Transmission of Signal and Noise Through Standard Nonlinear
rlement5 57
h.l.. Amplitude detection 57
6.2. Frequency detection 59
6.3. Distortions of telegraph video pulses by f luctuation noise 71
Chapter
7. General Characteristic of the Methods of Transmitting
Digita
l Data in Radio Communications and Noise Itmnunity of Amplitude
Keying
75
7.1.
Methods of transmitting and receiving digital data
75
7,2.
Noise immunity of amplitude keying
78
Chapter
8. Phase and Relative Phase Keying
82
8.1.
Phase keying
82
8.2.
Relative phase keying
88
Chapter.
Immunity of Digital Data Transmission by the FYequency-
9. Noise
Shift
_
Keying Method
92
9.1.
Multiposition transmission during reception to a filter discriminator
92
9.2.
i)ouble frequency-shift keying. Filter discriminator
98
9.3.
Doub le frequency-shift keying. Linear frequency detector
102
9.4 Mul.tichannel transmission. Frequency modulaCion
105
I'ART III. NOISE IMMi1NE CODING OF DIGITAL DATA
108
Chzpter
1.0. General Information and Simplest Codes
108
10.1.
Genera]. information about noise imanune coding
108
10.2.
Structure of cyclic cocles
112
117
10.3.
Multicycle linear fil:ters and simple decoding algorithms
10.4.
Eff.iciency of block coding
122
CtiaPter 11. Cascade and Convolution Coding 129
11.1. Cascade codes 129
11.2. Convolution coding � 130
11.3. Viterby decoding algorithm 133
11.4. Ser.ies decoding 136
PART IV. AUTOMATED CONTROL SYSTEMS 140
ChApter 12. General Data and Analysis Procedure 140
1.2.1. Use of automated control systems in digital data transmission
systems 140
12.2. Procedure For analyzing the noise,immunity of automated control
systems 142
100
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12.3. Analysis of the transient process and discontinuation of
4 tracking by the methods o� diffusion process theory
Clinpter 7.3. T'requency Automatic Frequency Control Systems
13.1., Initial equations and positions of equilibrium
13.2. Tracking mode and statistical dyriamics
13.3. Brief information about the frequency automatic frequency
control system with delay
Clinpter .1.4. Phase Automatic Frequency Control' Systems
14.1. Initial equations and basic parameters
14.2. Statistical dynamics of the operation of phase autamatic frequency
control systems
Chapter 15. Cadence Synchronization Systems
15.1. Operating algorithms and general relations
15.2. Simplest digital closed cadence synchronization systems
15.3. Cadence synchronization systems with delay
PART V. T1ME MULTIPLEXING OF DIGITAL SIGNALS
' Chapter 16. Simplest Methods of Digital Multiplexing
16.1. General information 16.2. Cyclic synchronization
Chnp[er 17. Asynctironous Input Algorithms
17.1. Algorithms based on digitalization with respect to time
17.2. PIV [insertion information trar.smission] algorithms
17.3. Algorithms based on coding front positions
PART. VI. MUI,TISTATION ACCESS TO THE RADIO RELAY IN COMMUNICATYONS SYSTIIMS
WITH ARTIP'ICIAL EARTH SATELLITES
Chapter 18. Methods of Multistation Access and Their Efficiency
18.1. Classification of inethods
1.8.2. Energy efficiency of multistation acc,,kss methods
Chapter 19. Characteris'_'-a of Basic Multistation Access Methods
_ 19.1. Multistatior access with direct radio relay and separation of
signals by frequency and shape
- 19.2. Multistation access with time separation of signals on the
- satellite-ground station radio link
Bi.b liography
Subject index
_ CQPYRIGHT: Izdatel'stvo "Svyaz"', 1980
_ [55-10845]
10845
CSO: 1860
101
FOR OF'r'ICIAL USE ONLX
145
152
152
155
158
160
160
162
165
165
171
177
184
184
184
189
193
193
199
210
216
216
216
222
232
232
238
249
252
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UDC 621.3.0853:532.783
I.IQUID CRYSTAL DISPLAYS
Mos cow INDIKATORNYYE USTROYSTVA NA ZHIDKIKH KRISTALLAKH in Russian 1980
siqned to press lb Jan 80 pp 2, 239-240
[An notation and table of contents from book "Liquid Cryatal Displays", by
Zen on Yur'yevich Gotra, Fduard Pavlovich Dzisyak, Leonard Kazimipovich Vistin',
Lyubomir Mikhaylovich Smerklo, Valentin Vasi1'yevich Parkhomenko, and Vasiliy
Teodorovich Fechan, Izdatel'stvo "Sovetskoye radio", 10,000 copies, 240 pages]
[TexC] A discussion is presented of the state of the art in the development of
liq ui.d crystal displays. The basic physical properties and electrooptical effects
in liquid crystals are investigated. Process-design recommendations are made with
re s pect to the execution of the displays.
Th e book is designed for a broad class of engineering and technical workers and
st udents involved with the problems of the investigation, development, production
an d application of liquid crystal displays.
Contents Page
Fareword
3
In t roduc
tion
5
Chapter
1. Physical-Chemical Properties of Liquid Crqstals
8
1.1.
(:1lssification of liquid crystals
8.
1.2.
Liquid crystalline compounds for displays
16
1.3.
i'hysical properties of liquid crystals
32
1.4,
Sttidy of the el.ectxophysical characteristics of liquid crystala
42
Ch apter
2. Flectrooptical Effect in Liquid Crystals
48
2.1.
Domains in nematic liquid crystals
48
2.2.
Optical and electrical properties oi domains
61
2.3.
Theory of Electrooptical Effects in Liquid Crystals
68
Ch apter
3. Structural Designs of Liquid Crystal Displays
80
3.1.
Structural design of a liquid crystal display
80
3.2.
Versions of'liquid crystal displays
85
3.3.
Television, cathode-ray and projection screens based on liquid
crystals
93
3.4.
Matrix displays
103
3.5.
Color liquid crystal devices
114
102
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3.6. Electrooptical parameters o� liquid crystal displays 120
3.7. Electronic control of liquid crystal devices 135
Chupter 4. Production Techtiology of Liquid Crystal Displays 153
4.1. Manufacture of electrically conducting films 154
4.2. Methods of creating the film coating configuration in liquid
crystal display technology 167
4.3. Methods of creating directianal orientation 177
4.4. Assembly and seal of liquid crystal displays 184
(:hapter
5. Application of Cholesteric Liquid Crystals
for Displays
199
5.1.
F.ffect of temperature on the spiral steepness in cholesteric
liquid crystals
199
5.2.
Liquid crystal heat indicator technology
207
5.3.
Application of heat indicators
210
5.4.
Effect of inechanical tensile ehear and pressure
on the spiral
steepness of cholesteric liquid crystals and
practical use
of these phenomena
.
219
5.5.
Chemical effects on cholesteric Iiquid crystals
and practical
use of these properties
223
Bib liography
225
Supplementary bib liography
233
Subject
index
237
COPYRZGHT: Izdatel'stvo "Sovetskoye radio", 1980
[59-10845] ,
10845
CSO: 1860
103
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UDC 621. 391.1
RJNDAMENTALS OF THE THEORY AND DESIGN OF INFORMATION SYSTEMS
Moscow OSNOVY TEORII I RASCHETA INFORMATSIONNO-IZMERITEL'NYKH SISTEM in Russ3.an
1980 signed to press 25 Dec 79 pp 2,'278-280
[Annotation and table of contente from book "Fundamentals of the Theory and Design
of Information Syatems", by Oleg Nikolayevich Novoselov and Aleksey Fedorovich Fomin,
Tzdatel'stvo "Mashinostroyeniye", 9000 copies, 280 pages]
(Text] A disciisaion is presented of the fundamentals of the theory and design of
mensurement data gathering, representation and transmission means. The data pro-
cessinfi problems pertaining to the reproduction of continuous transmissions and
improvement of their reliability at the system output are investigated, and
sr.andard examples of the calculations are given.
The book is designed for engineering-technical and scientific workers dealing with
the planning, design, operation and maintenance of information measuring systems
and automated control systems (ASU).
Contents Page
T'oreword 3
Introduction 5
Chapter 1. Information Characteristics of Measurement Transmissions 7
1. Ceneral approach to describing the models of ineasurement
transmissions and the output of the investigated target , 7
2. Models of stationary random processes 9
3. Models of nonstationary measuring processes 15
Isrrc)r index durinR measurements and transmission 16
C.hnptcr 2. Fundamentals of the Theory and Design of the Digital
Rep
resentation of Continuous Processes
18
1.
General information about the methods
of digital representation
of continuous processes
18
2.
Estimation of the error in reproducing
a continuous process during
digital representation of it
20
3.
Optimal digital representation
23
4.
Generalized digitalization with respect
to the Legendre polynomials
24
S,
Reproduction of continuous messages by
algebraic interpolation
polynomials
29
6.
Calculation of interpolation errors and
determination of the cyclic
interrogation frequency
33
104
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7. Optimal interpolation
8. Comparative estimate of various methods of interpolation
9. Representation of continuous messages by regular sampling with
reproduction by the least squares method
1.0. Difference and delta-digital representatians
1~. Cstimation of digital representation error by the uniform approxima-
tion index
12. Calculaeion of extrapolation error
Cfiarter 3. niRita.l.-Quantized Representation of Measurement Transmissions
1. I'orms of digital-quantized representation
2. Calculation of quantization error in various representations with
reproduction by the Lagrange interpolation polynomial
3. Calculation of the quantization error when representing a trans-
mission by the coefficients of an orthogonal series
4. Calculation of optimal ratio of the errors in digital representa-
tion and quantization of it
5. Comparison of the efficieney of diaital-quantized representations
Chapter 4. Adaptive Representation of Data in Information Measuring
5ystem9 (Adaptation to Measurement Transmissions)
1. Statement of the problem and classification of inethods of adaptive
data representation
2. Qua.l.ity indexes of data compression algorithms
3. Data compression algorithms with single-parametric adaptation
4. Dnta compression algorithms with two-parametric adaptation
5. Procedure for comparing the effectiveness of adaptive and regular
representations of nonstationary processes
Chapter S. Theory and Calculation of Devices for Grouping Message Flaws
in Information Measuring Systems
1. Message flaws in information measuring systems and methods of
grouping them
2. Calculation and comparison of n.athods of grouping flaws in
adaptive information measuring systems
3. Comparison of the ef�iciency of adaptive and cyclic data gathering
systems in information measuring systems
37
39
41
45
50
53
55
55
56
58
60
63
73
73
75
77
86
90
97
97
98
105
Chapter 6, Basic Characteristics of Measurement Information Transmission
Systems 114
1. Ceneral definitions 114
2. Basic models and characteristics of signal carriers 115
3. Comparison and optimalness criteria of transmission systems 118
Chapter 7. Fundamentals of the Theory and Calculation of Analog Continuous
Transmission Systems 120
1. General information about analog continuous transmission systems 120
2. Noiseproofness of analog continuous transmission systems in the
presence of weak interference 122
3. Estimation of anomalous errors in the presence of angular modulation
and real reception 131
105
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4. F.stimation of the resultant transmission error at the output of
a real FNI signal transmi.tter
5. Optimal and quasioptimal tracking signal receivers with angular
modulation and estimation of their noisenroofneas
Chapter 8. Fundamentals of the Theory and Calculatiion of Analog Pulsed
Transmission Systems
1. Basic characteristics of analog pulsed transmission systems
2. Basic relations of statistical communication theory and the
optimal reception of analog pulsed signals
3. Noiseproofness of analog pulsed signals during optimal reception
4. Calculation of threshold signals and optimal parameters of analog
pulsed systems during optimal reception
5. Estimation of the noiseproofness of PPM-AM signals during actual
reception
6. Estimation of the noiseproofness of PAM-FM signals during actual
reception
7. Noiseproofness of analog pulsed transmission systems when using
pulsed tracking demodulators
C}iapter 9. Fundamentals of the Theory and Design of Digital Transmission
Sys tems
l. General. informfirian about digital transmission systems
2. BaHic relations of statistical communication theory and optimal
reception of digital signals
3. Noiseproofness of digital signals during optimal reception
4. Noiseproofness of certain digital signals during actual reception
5. Estimatian of the errors introduced by digital systems during the
transmission of continuous processes
6. Calculation of threshold signals and the optimal parameters of
digital transmission systems
Ctiapter 10. Information Characteristics and Comparison of Transmission
Systems
1. Maximum carr.ying capacity of a communication channel
2. Actual carrying capacity of analog transmission systems
3. Maximum threshold relations for analog transmission systems
4. Comparison of various analog transmission systems
Chapter 11. Analysis of the Method of Increasing the Reliability of
Lstimates of Continuous Measurement Transmissions at the Output of an
Information Measuring System
1. Brief characteristic of various methods of improving the reliability
of estimates of continuous processes in inf ormation measuring
systems
2. Basic relations of the statistical synthesis and analysis of filters
and anomalous error detection devices
3. Optimal and actual filtration of anomalous errors during continuous
observation
106
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133
isb
144
144
146
154
164
172
178
179
188
188
190
192
19?
198
206
221
221
222
226
228
234
234
235
244
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4. Optimal filtration of anomalous errors during discrete
observation 5. Filtration of anomalous errors by the method of finite
differnces
6. Filtration of anomalous errors based on the least squares method
7. Filtration of anomalous errors based on interpolation and
extrapolntion by Lagrange polynomials
- 8. Estimation of the effectiveness of re3e cting anomalous e rrors during
dnta processing
Bibliography
Notation
Sub ject Index
COPYRIGHT: Izdatel'stvo "Mashinostroyeniye" , 1980
[58-10845 ]
10845
CSO: 1860
107
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248
250
253
256
260
271
274
276
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UDC 621.397.61
TELEVTSION TRANSMITTING STATIONS
Moscow PERI:DAYUSHCHIYE TELEVIZIONNYYE STANTSII in Russian 1980 signed to press
5 M7r 80 pp 2, 327-328
/Arirj()tation and table of contents fram book "Television Transmitting Stations'l,
b,y A.l.eksandr Mikhaylovich Varbanskiy, Izdatel'stvo"Svyazl", 7000 copies,
328 pageJ
[Text] A study is made of the structure of the televisiai transmitting network
and methods of planning the placement of television transmitting stations. A
- ciescription is given of the equipment of standard television transmitters, tele-
vision relays and antenna-feeder devices. The prob lem.s of the design and
or.ganization of the operation of television transmitting stations are discussed.
'1'lie book is designed for engineering and technical workers involved with the
devel.opment, operation and maintenance of television transmitting stations, and
it can also be useful to students of the higher institutians of learning
specializing in the field of television transmission engineering.
Contents Page
Foreword 3
Introduction 4
Chapter 1. Planning of the Placement of Television Transmitting Stations 7
1.1.. Structure and parameters of the television transtnitting network 7
1.2. Radio wave bands, television systems and their standards used 13
for television broadcasting
1.3. Radio wave propagation for television broadcasting 15
1.4. Calculation of field intensity. Propagation curves 24
1.5. Minimal field intensity 33
1.6. Protective ratios 38
- 1.7. Placement of television transmitting stations 44
ChapCer 2. Television Stations 45
2.1. Construction of television stations 45
2.2. Operation with partially suppressed frequency sideband 53
2.3. Power addition and divi.sion 58
2.4. Separation filters 69
108
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(:hnpter 3. Television Transmitter Video Channel 76
3.1. Parameters and structure of the video channel 76
3.2. High-f requency channel 85"
3.3. Modulation in the video channel 93
3.4. Correcting circuits 101
(:hrepter 4. Drivers
4.1, Parameters and structure
4.2. FM signal drivers
4.3. Combined drivers of tele-
4.4. Drivers for stereophonic
108
of video channel drivers 108
113
vision transmitters 121
radio broadcasting 130
Chapter
5. Equipment of Standard Television
and FM Radio Broadcast
Transmitters
134
5.1.
Classification and parameters of the
equipment of standard
television transmitters
134
5.2.
Television transmitters for operation
in frequency b ands
I and II
139
5.3.
Television transmitters for operation
in frequency band III
152
5.4.
Television transmitters for operation
in frequency bands IV-V
163
5.5,
Radio broadcast transmitters with fre
quency modulation
167
Chapter 6. Television Relays 168
6.1. Parameters and structure of television relay 168
6.2. Television relay stations with demodulation 174
6.3. Television relay stations with spectrum shift 176
6.4. Equipment of standard television relay stations with demodulation 178
G.S. Equipment of standard converter relay stations 186
Cliapter 7. Antenna-Feeder Devices 194
7.1. Requirements on antenna-feeder devices 194
7.2. Antenna elements 199
7.3. Turnstile antennas 202
7.4. Panel antennas 208
7.5. Antennas with radial and V-dipoles 217
7.6, Feeder 219
7.7. Antennas f.or multiprogram broadcasting 222
Chiipter.
8. Monitoring and Measuring the Parameters
of the Video Channel
of fl
Television Transmitter
226
8.1.
Requirements on the monitoring and measuring
system and its
structure
226
8.2.
Demodulator
231
8.3.
Monitoring and measuring with respect to the
television image
233
8.4,
MonitorinR and measuring with respect to the
total television
signal
240
8.5.
Television test signals
242
8.6.
Measurements of the vldeo channel parameters
of a television
transmitter
246
8.7.
Measuring channel parameters in the transition process
260
109
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Chlpter 9. Problems of Organizing the Construction, Operation and
Maintenance of Television Trarismitting Stations 263
9.1. Design of transmitting television stations 263
9.2. Organization of operation and maintenance 267
CfiriPter 10. ilgr of Arti{'icial Earth Satellitea in the Television
'I'r.nnqmittinA Network 271
10.1. Classification of space television broadcast services 271
10.2. Used satellite orbits 273
10.3. Peculiarities of radio wave propagation 278
10.4. Admissib le signal levels 280
10.5. Parameters and structure of the receiving station 282
Appendix 1. Terminology Used to Designate Signals and Equipment in
Televi5ion Cngineering 286
Appendix 2. Nomenclature of Frequency and Wave Bands Used for Radio
Communications (Item 112 of the Radio Communications Regulations) 287
Appendix 3. Basic Parameters of Black and White Television Systems Used
for Broadcasting 288
Appendix 4. Width
of Radio Channel and
Emitted Radio Signal Spectra in
Uiffer.cnt Systems
292
Appcndtx 5. Tel.evision Standards
.
292
Appendix 6. Basic
Parameters of Black
and White and Color Television
Systems F,stablished by All-Union State
Standard 7845-79
295
Appendix 7. Rated
Values of Frequency
Bands atid Video Carriers in
Various Television
Broadcast Channels i
n the Meter Wave Range
299
Appecidix 8. Rated Values of Frequency Bands and Video Car.riers in
Various Television Broadcast Channels in the Decimeter Wave Range - 302
Appendix
9.
Conver.sion Table of Voltage (Current) and Pawer Ratios to
Decibels
303
Appendix
10.
Provisional Graphical Notation Used in Diagrams
305
ApPendix
11.
Basic Parameters of the Stereophonic Radio Broadcast System
LstAblished by All-Union State Standard 18633-73
308
Appendix
12.
Basic Parameters of Powerful Radio Tubes Used in Television
Sets
,
309
Appendix
13.
Radiation Patterns of Some Television Antennas
316
Bibliography
323
COPYRIGHT: Izdatel'stvo "Svyaz 1980
[60-10845]
10845
CSO: 1860
110
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~ FOR OFFICIAL USE ONLY
i
UDC 621.372.8
WAVI:GUIDE DIELECTRIC FILTERS
Moscow VOLNOVODNYYE DIELEKTRICHESKIYE FILTRY in Russian 1980 signed to press
20 Mar 80 pp 2, inside back cover
~ [Annotation and table of contents from book "Waveguide Dielectric Filters", by
i Boris Yulianovich Kapilevich, Izdatel'stvo "Svyaz 3400 copies, 136 pages]
i [Text] A study is made of the problems of the calculation and design of small
microwave filters based on waveguide-dielectric structures with evanescent
. couplings. Examples of the practical realization of multisection filters are
; presented. FORTRAN-IV programs for analyzing the frequency characteristics of
~ evanescent resonators and filters are described in the appendices.
The book is designed for engineering and technical workers involved with the
c.llculation, design and construction of micrawave equipment, and it can also be
u.4efu1 to poetgraduate students and 'students in the advanced courses at the
institutions of higher learning.
Contents Page
T'oreword . 3
From the author 5
Tntroduction 6
Chapter 1. Evanescent Dielectric Waveguide Resonator with Plane Layer 10
1.1. Dispersion matrix of a plane dielectric layer in an evanescent
rectangular waveguide 10
1.2, Frequency characteristics of the elements of the dispersion matrix
and the resonance condition 19
1.3. Field sCructure 25
1.4. Loaded and characteristic Q-factor of a resonator 27
~ Cliepter 2. Cvanescent Resonator with Dielectric Nonuniformity of
~ Cylindrical Shape 34
; 2.1. Electromagnetic fields and wave equations in a longitudinally
; nonuniform medium 35
~ 2.2. Dispersion matrix of a segment of the transmission line with
~ longitudinal-nonuniform medium 38
~ 2.3. Dispersion matrix of a resonator with dielectric nonuniformity of
, cylindrical shape 39
111
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2.4. Results of calculati.ng the transmission coefficient and
resonance frequencies 46
2.5. Natural Q-factor 53
(;hupter 3. Calculation of Dielectric Waveguide Filters with Evanescent
Cauplin gFi 59
3.1. Calculated model of an evanescent waveguide-dielectric filter 60
3.2. Peculiarities of the frequency characteristics of evanescent
dielectric waveguide filters 63
3.3. Machine synthesis of dielectric waveguide filters with evanescent
couplings 72
3.4. Equivalent diagram of a dielectric waveguide filter with
evanescent coupling 79
Chapter 4. Practical Realization of Evanescent Dielectric Waveguide
87
Filters
87
4.1. Realization of the prototype of a band filter
4.2. Stability of the frequency characteristic of an evanescent
dielectric waveguide filter
92
4.3. Examples of the practical realization of dielectric waveguide
�ilters with evanescent couplings
95
4.4. Coupling of a dielectric-waveguide structure to a regular
transmission line
103
Appendix 1. Program for Calculating the Elements of the Dispersion
Matrix of a Plane Dielectric Layer in a Rectangular Waveguide
119
Appendix 2. Program for Calculating the Dispersion Matrix Elements of a
Die.tectr.ic Cylinder in a Rectangular Waveguide
123
Appendix 3. Program for Analyzing a Multisection Evanescenti Dielectric
127
Waveguide Filter
Appendix 4. Calculation Relations for Prototype Filters with Parallel.or
Series Resonator at the Input
130
131
Ribliofiraphy
COPYRIGHT: Izdatel'stvo "Svyaz'", 1980
[56-10845]
10845
CSO: 1860 ~D
112
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