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JPRS ID: 9489 USSR REPORT ELECTRONICS AND ELECTRICAL ENGINEERING

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APPROVED FOR RELEASE: 2047102108: CIA-RDP82-00850R000300070024-5 FOR OFFIC[AL USE ONLY _ . JPRS L/9489 15 January 1981 ~ USSR Re ort p ELECTR4NICS AND EIECTRICAI ENGINEERING CFOUO 1 /81) FB~$ FOR~:IC;N BRQAa~AST INFORMATiON SERVICE FOR OFFICIAL USE ON~.Y APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2047102108: CIA-RDP82-00850R000300070024-5 NOTE JPRS publications contain information primaril.y from foreign newspapers, periodicals and books, but al~o from news agency _ transmissions and broadcasts. Materials from foreign-language sources are txanslated; those from English-language sources are transcribed or reprin.ted, with the original phrasing and , other characteristics retained. Headlines, editorial reports, and material enclosed in brackets [J are supplied by JPRS. Processing indicators such as [Text] _ or [Excerpt~ in the first line of each item, or following the - last line of a brief, indicate how the original informa.tion was processed. Where no processing indicator is given, the infor- mation was summarized or extracted. Unfamiliar names rendered phonetically or transliterated are enclosed in parentheses. Words or names preceded by a ques- _ _ tion mark and enclosed in parentheses were not clear in the original but have been supplied a, appropriate in context. ' Gther unattributed parenthetical notes within the body of an it~m originate with the source. Times within items are as given by source. _ The contents of this publication in no way represent the poli- cies, views or attitudes of the U.S. Government. - ~ . COPYRIGHT LAWS AND REGULATIONS GOVERNING OWNERSHIP OF r MATERIALS REPRODUCED HEREIN REQUIRE THAT DISSEMINATION OF THIS PUBLICATION BE RESTRICTED FOR OFFICIAL USE ODTLY. APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2047102108: CIA-RDP82-00850R000300070024-5 FOR OFFICIAL USE ONLY JPRS L/9489 � 15 January 1981 USSR REPORT ~ ELECTRONICS AND EL~CTRICAL ENGINEERING - (FOUO 1/81) CONTENTS COMMUNICATIONS, COMMUNICATION EQUIPMENT, RECEIVERS AND TP,ANSMITTERS, NETWORKS, RADIO PHYSICS, DATA TRANSMISSIO?J AND PROCESSING, INFQF.MATION THEORY , Quasi-Optimal Filtering of Trapezoidal Signals With Varying Rise and Fall Times 1 Optimal Word Selection for Digital Coherently Weighted Signal Processing Systems 5 Study of Bas= 4 Fast Fourier Transformation Algorithms With Constat~t Structure 11 Effect of the Form of Sea Waves on the Scattered Radiation Characteristics 22 A Comparison of the Noise Immunity of ~o Detectors Which Operate Using the Method of Bilateral Spatial Contrasts........ 28 The Sequential Detection of an Incoherent Signal 36 COMPONENTS EiND CIRCUIT ELEMENTS, WAVEGUIDES, CA~IITY RESONATORS AND FILTERS Quadrature Filters Using Integra~ed Circuits for Analog _ Signal Multiplexers , 42 PUBLICATIONS, INCLUDING COLLECTIGNS OF ABSTRACTS Antenna Synthesis Methods: Phased Antenna Arrays and Continuous-Aperture Antennas 54 ~ Autocompensation of Drifts of Power Gyrostabilizers 58 1 _ Digital Radio Navigational Systems 60 - a- [I~I - USSR - 21E S&T FOUO~ ~(1R f1FF'r('iAi TiCF (11Ii,Y APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000300070024-5 - Electroc}~emical Processing in the Technology of Electronic Equip~aent Production 64 Mobile 4?ommunicstions Center 66 Piezomdgnetic Ceramics 76 Resolu~ion of Magnetic Recording Systems 79 E RADARS, RADIONAVIGATION AIDS, llIRECTIdN FINDING, GYROS Characteristics o' the Sea Wave Image in Side-Looking, S~nthetic-Aperture RAdar 81 Frequency Scanning in ~[tadiovision 93 ~ , ~ ~ , _ ; i ; . ! ~ - b - FOR OFFICIAL USE ONLY ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02108: CIA-RDP82-00850R000300070024-5 FOR OFFICIAL USE ONLY � COMMUNICATIONS, COMMUNICATION EQUIPMENT, RECRIVERS AND , TRANSMITTERS, NETWORKS, RADIO PHYSICS, DATA TRANSMISSION AND PROCESSING, INFORMATION THFORY = UDC 521.391.266 QUASI-OPTIMAL FILTERING OF TRAPEZOIDAL SIGNALS WITH VARYING RISE AND FAI:L TIMES Kiev IViJZ RADIOELEKTRONIKA in Russian Vol 23,No 8,Aug 80 pp 85-86 manuscript received 15 Feb 79,after revision 31 Jan 80 - [Paper by P.V. Gavrish] [Text] The optimization of the electronic channel of a LIDAR polar coordinate meter reduces to the choice of the pXOCedure for discriminat- 1 ing the detected signal in the receiver noise against the signal and interference background, referenced to the input of the time filter. The received realization u(t) = s(t-T, + n(t) consists of additive noise ntt) and the signal s(t-T, S), which is a determinate function of time, and some parameter S, which characterizes the law governing the ~ image analysis; T is the signal delay time. The reception condition~ are such that we consider the statistics of the photoelectric current to be normal while n(t) is a steady-state normal uncorrelated process. In such situations, the reception of intensity modulated signal~ (with the exclusion of the constant compon- ent) is accomplished just as in the case of radar. The sounding range is equal to [R1, RZ] for any distance R [R1, R2] and uniformly distributed in [R1, RZ], the detected signal represents - a symmetrical trapezoidal video pulse [1] with a width at the 0.5 level relative to the maximum value A of T~ = const. and a width of the leading and trailing edges of T~ ti 1/R. In this case, T~ is uniformly - distributed in th.e segment ~T~2, T~l] (0, TS), where T~1 ti 1/R1 and T~2 ti 1/R2. [de shall take T~ as B. We then derive the Iike~ihood function p(u/z) ' which for a given nature of the signal and noise defines the structure 1 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2047102108: CIA-RDP82-00850R000300070024-5 ~ va. iVi~li1 ~.~u vara.~ ~ of the optimal receiving system, by means of statistically averaging the likelihood function p(u/T, T~) with respect to the minor parameter T~. The practical realization of such an optimal receiver is complicated. If the signal is considered to be a determtnate function, the problem posed here can be solved by the method of optimal filtering (OF). However, since T~ ti 1/R, the synthesis of a filter which is optimal for the set of signals encompassing [R1, RZ], is not feasib~le in practice. In such situations,quasi-opti.mal filters (KVOF) are used [2] which are matched to the signal in a portion of its spectrum~"selected in a specified manner. It is proposed that an ideal low pass filter with a passband ~f be used _ as the KVOF, where the filter is designed to maximize the ~ignal-to- noise ratio for the worst~c3se situations which occur in the specified � sounding band. � We shall 3esignate the maximum valae of the voltage signal-to-noise ratio at the output of the KVOF to the signal to noise ratio at the output of an opti.-nal filter as p[2J : ~ . ` S (J~) K (J~) e~~'td~ f = , . ~ a , i~z ~1) ~ I S(i~) I' d~ ~ I K ~~u) I= d~ I , where S(jc~) = 4A sin 0,5 u~T~ sin 0,5 ~r~/c~~t~ ~2~ is the spectrum of the received signal, while ~ X~1~) = ke imt,. ~ w ( 3) - is the transfer function of the proposed KVOF. We define tp as the point in time when the signal is observed at the output of the KVOF; k is a constant factor. After substituting (2) and (3) in (1), we obtain: (1- T~ ) S~ ~nef (T~ - Tm)~ -I- (1 ) si [nA/ (7~ -F z~)l - 2 - n~1~T~ sin nAfT~ sin nA/i~ D = ' ~4) n y~i3e f ~sT~ - . where si(z) is the ~ntegral sine. - 2 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02108: CIA-RDP82-00850R000300070024-5 1 ~ FOR OFFICIAL USE ONLY ~ i I = P ~ The reduction in the signal-to-noise ratio 0,9 - at the output of a K~'OF f or various values 1 . of the normalized rise time of the pulses, f ~6 computed on a camputer using formula (4), is ~ ahown in Figure 1. I UI ! The quantity p, for a specified [R1, R2] ca.n ; . 06 be consid~red a function of two variables: i ~ 0,2 0,4 0,6 G,'8 at-30 dB, weighted processing in a ChPK2-~7AT quasi-optimal system has a poor efficiency and the weighted store degenerates into an equi- - librium store, A similar situation is a7.so observ~d in a ChPKl-VN quasi-optimal system when a>-20 dB. Thus, the analysis performed here and the proposed procedure for the optim ization of the bit capacity of digital devices using the criterion ' of a miniun~ conditional equipment.cost can be useful for the technical � economic substantiation of the choice of the structure of digital - quasi-optimal systems. The results obtained show that the requisite - number of A/D converter bits is determined by the quasi-optimal system efficiency and for actual noise/interference ratio, depends little on ` - its structure. The presence of a rejection filter in the quasi-optimal = system reduces the requirements placed on the bit capacity of the weight- ing coeff icients and the multip7iers of bandpass filters to a greater _ extent, the higher the efficiency of the re~ection filter. - BIBLIOGRAPHY � - 1. Popov D.I., Koshelev V.I., ~'Opta.mizatsiya ts~~rovay kogeXentno~yesovoy radiolokatsionnykh signalov" ("The Optimizat;[on of the Digital _ Goherently Weighted Processing of Radar Signals~'], TZV. VIIZOV - - - RADIOELEKTRONIKA [PROCEEDINGS OF THE HTGHER EDUCATEONA'P, ~NSTI7,'UT~S ^ RADIOELECTRONICS], 1979, 22, No 8, p 9Q. 9 FOR OFFICIAL USE ONLY i APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 FOR, OFFICIAL USE ONLY - 2. Gray G.A., Zeoli G.W., "Quantization and Saturation No3se due to _ Analog-Digital Conversion", TEEE TRANS., 1971, AES-7, N~~ 1. 3. Kh~im~el'blau D., "Prikladnoye nelineynoye programmirovaniye" ["Applied Nonlinear Progra~ing"], Moscow, Mir Publlahers, 1975. COPYRIGHT: "Izvestiya vuzov SSSR - Radioelektronika~~, 1980. - ~ [11-8225] 8225 - CSO: 1860 I I 10 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2047102108: CIA-RDP82-00850R000300070024-5 FOR OFFICIAL USE ONLY vnc 6zi.391.a STUDY OF BASE 4 FAST FOURIER TRANSFORMATION ALGORITI~iS WITH CONSTANT STRUCTURE , Moscow RADIOTEKHNIKA I ELEKTRONIKA in Russian Vol 25, No 8, Aug 80 pp 1639-1647 _ manuscript received 5 Jan 79 [Article by A. A. Belyys Ye. I. Bovbel', V. I. Mikulovich] [Text] A study is made of base-4 fast Eourier transformation ' algorithms with constant structure under their properties. The pre- sented results permit determination of the limiting possibilities of the systems containing no more than one arithmetic circuit operating in real time. The results of the studies are used to create algorithms with counterstructure which, in turn, permits the creation of deficient systems for simultaneous proc~ssing af two complex si~nals. Introduction Fast Four.ier transformation algorithms (BPF algorithms) have had a great influence on the development of digital signal.processing. They are widely used in determin- - ing the mutual spectral power density [1-3], the coherence function [4, 5J, the mutual correlation function [1, 2, 6j, and the indeterminacy function [2, 12]. The operation data play a def ining role when solving various problems which arise, for example, in radar and also when processing the results of acoustic and vibration measurements. A characteristic feature when performing the given operations is simultaneous obtaining of the spectrum of two signals. The given signals are com- - plex, for by assumption, the analytical model of a real signal is used [7, 8, 10]. The possibility of using BPF algorithms with substitution in the device realizin~ ~ these operations has been investigated in detail in references [1, 9, 11]. The app~ication of BPF algorithms with constant~structure for the solution of a given problem ha.s not in practice been investigated. Tlie purpose of this paper is the investigation of BPF algorithms with constant structure and the possibility of using the given algorithms in a specialized device _ designed for simultaneous obtaining of the spectra of two complex signals. - The limiting characteristics of the device operating in real time will depend on the speed of execution of the base operation of the BPF and the selected method of realizing the BPF. It is known that the execution of the BPF algorithm can be - realized [lJ by the methods of series, parallel and f low processing using bases 2, 4 and 8. Con~cidering these methods, it i~ possible to draw the conclusion tha.t - from the point of view of equipment expenditures with ~imely development of an _ ]1. FOR QFFICIAL USE ONL~f APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 element base it is possiUle to discuss the series method of executing the base 4 - BPF algorithm when all of the base operations of the algorithm are performed in series by one arithmetic circuit. l. Base 4 BPF Algorithm 'The discrete Fourier transformation for samples of the ti~,~e function si given at N . discrete points is written in the form x-i , An= ~ W"'s~, k=0,1, . . . , N-1, ~1~ r_. where W= exp (-j 2~r/N) , N is an integer. If we introduce the N x 1 matrices Ilsll~col(s,, s,, sx-~); IIAll=col(A,,~Al, AR-~) xxt xxi and define the iV x N matrix W , the coefficie~ts of which are ~ w~,,=egp [ -j N (ik) mod N . expression (1} assumes the form ' - - IIAl1=1IR'llllsil. ~ ~2~ NXt XXH NXt I - In the case where the matrix ~~W~~ is multiplied from the left by the permutation matrix ~~II~~, the newly obtained matrix can be represented in the form of the product of rare:ied matrices. As the permutation matri.x it is possible to use the digital - inversion matrix ~~III~ _ ~IQ~~� Tn the case where an_1, an_2, al, a~) are n ; - digits of the base 4 representation of the row number of the matrix ~~W~~, then n digits (a0, al, an__2~ an_1) define a new number of the given row in the matr.ix ~~T~I- Let us also note that if an operation of the type ~an-1' ar.-2' an-3' a2' I al~ a~) ~ ta~, an-1, an-2, a3, a2, al) is performed, thPa the matrix IIPII is defined, and if the operation of ths type ~an-1' n-2' an-3' a2' a1' a0~ ~ - ~an-3' an-3' an-4' al' a0' an-1~ is valid, the matrix ~~M~~ is defined. ~ Using the digital inversion matrix, expression (2) can be reduced to the f orm ' IIA11=11QiI IITII ilsll, (3> rrxi rrxx xxx xx~ where . IITII=IIQII IIwII. (4) Kxx xxx xx~ Entering the row number p of the matrix I~T~~ in the f orm 12 ' FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 FOR OFFICIAL USE ONLY - w-t P=~ d~4`~ d~=0, i, 2, 3, . ,~..o ~S~ in equality (4), it is possible to aote that the same row in the matrix ~~W~~ will have the number r~ cP) a~4^-'-~. ~6~ ~ In this case the elements of the matrix ~~T~~ will be _ tpQ'-w~R(P)a-B1CF) ~-j2n T�~P)4 ~ . _ ~7) N Let us brea.k down the matrix I~T~~ into blocks Aoo ~ Aoi ~ Ao2 ~~b3 ' A~o ~ A� ~ Ai2 Aia II T II = Azo I qzi ~ Asx j Az9 ' ~8) i Aao I As~ ~ A9s ~ As3 where the matrices ' has dimensions of 4n-lx4n-1. IIA ~ Il, i=0, 1, 2, 3; k=0, i, 2, 3, The elements of the matrix ~~Aik~~ .are equal to: - rR - apq -t{.�~ ~+D- ~+Qf, P=q=O, 1, 4*''-1; i=k=0, 1, 2, 3. ~9~ - If we consider the equality (7), expressi~n (9) assinnes the form j T.~i�4"-'+P) ~k�4"-'+4) aD9 -V%r~(D)o-~p 1 )~.JL l !}n ~ Since for i= 0, 1, 2, 3; p= 0, 1, 4n-1 - 1 the equality ?'n ( ~ � 4n-~+PI -4Tn-1 ~P) ~'i~ is valid, then ' r ~ �;;=exp{-j2n 4 }exp{-j2~t 44 }exp j-j2n Tr4*P)91. t ~ (10) - Considering expression (10), the equality (8) can be raritten as ,-n-1--~---7-"-1 ,-"-~---I Tn-~ T n-~ 1'n-1 1 T n-1 Ln-i I-!Tn-~ Ln-1' I ~T n-1 L++-7 \ -r-~-------- --------I------- ' ~Is x~ II = T~_1 L~_1 i T n-i Ln-i ~ Tn-i Ln-i i Tn-i Ln-i . _I_Y ~ I I . ' Tn-~ Ln-~ I 1 T n- Ln- I- i l' Lg ~T L$-- 1 1 I n-1 n-i I a-1 n-1 T�-1 ~ 0 I 0~ 0 I� .I 0 I ~ . - ' n_1 0 0 In-1 ~ jn-1 ~~n-~ ~ In-1 ~ - 0 I Tn-1 ~ 0~ 0 0 ~ L ~ 0 ~ 0 I T I- jl il - jl ' _ -~----~----I ~-1 I--- ri-1 ~ n-1~ n-1 j n-1 0 I p T ~ a I x I il ~--I il ' -~----I- n-1 ( ~ ~ ~ d j'~Ln-1 ~ ~ n_i I n-1~ n-1 ~ n-1 ~ ~ ~ ~ ~ ~ ~ T"'1 ~ I ~ I ~ I ~'n-a. ~n-i~~ln-1 ~ - lln-~ ~ - ~~n-1 13 ~ FOR OFFICIAL USE ONLk APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 ~ where . IIL"`11=diag~1,exp(-j ~ i�m},...,ezp[-j N (4"-'-1)mll+' ~ ln-1 i~ ~ unit matrix; le~ us also note that here the abbreviated notation for the 4n-lx4n-1 matrix ~~A~~ in the form I~A~~ ~ An-1 is used for convenience. If we introduce the notation ; s .a . Dn = quasi- diag (1�-,, Ln-,, Ln-s, L~-s) an.d use tl~e symbolic notation for the direct matrix product [11], then equality (11) , . assumes the form ~ TR=(T~-~~It)Dn(I.-,~T~), ~ ~la) where ~ is the direct product symbol. If we express the matrix Tn_1 in terms of the matrix Tn_2 and this process is then } I _ repeated until the matrix Tn is fully exprQSSed i.n terms of the matrix T1, we obtain i the base 4 BPF algorithm wliich considering equalities (2) and (3) is written in the ~ form Wn=Qn(T~~1�=t) ~D=~In-:) ~I,~T~~I�_=) . (Dk~l�_R)(T~_~~T,~In_R) ...D�(In_t~T~), , ~13) where _ Dn-1 - Quasi-diag (In-r-~~ L~-c-s, ~n{ t-t, Ln~ t-i~, ' ~ Lm = diag I0, ra�4`, m�2�4', m(4"-'-'-1) �4`l, 1 1 1 i ~ ~ 1-j-1 -j . ' , Tl- 1 -1 1 -1 ' . 1 j -1 -j k= 3, 4, n-1; i= 0, 1, n-2; m= 1, 2, 3. ~ The symbolic notation m is used in place of W'� to designate the elements of the ; matrix L. 2. i3PE Algorithm with.~onstant Structure By analogy with what has been stated above, it is possible to obtain a clas~ of BPF ~ algorithms permitting the use of a set of structural diagrams for their equipment : executi~n. Erom this class of algorithms we isolate the BPF algorithms with con- ' stant structure which are considered below. ' ~ 1.1.~ ~ FOR OFFII;IAL USE ONLY _ , ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000300070024-5 FOR OFFICIAL USE ONLY APN Algorithms. If we isolate the matrix sn=1n-~~T,, in the equality (13) , ~re obtain the BPF algorithm which is written in the for~a W~=Q�P�SRPA(1�-=~D=)S~ . . . P~(I*_.~Dk) S~ . . . P�D�5,,. (14) ~ Example: for N= 64 expressian (14) aesumes the form _ ~ w~=QsP~S~P~~I~~D:)S~P~D,S,, - where �D, = diag ~0, 0, 0, 0, 0, 0, 0, 0. 0, 0, 0, 0, 0, 0, o, o, 0, i, 2, 3, 4, 5, 6, 7, 8, 9, 10 li, 12, 13, 14, !5, 0, Z, 4, 6, 8, i0. 12, 14, 16, i8, 20, 22, 24, 26, 28, 30, 0, 3, 6, 9. 12, 15. 18, 2~, 24, 27, 30, 33, 36, 39, 42, 45), _ '(Il ~ D:) diag ~(0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0. ~ 0, - 0, 0, 0, 0, 4, 4, 4, 4. 8, 8, 8, 8, 12, 12, 12, 12, 0, 0. 0, 0, 8, 8, 8, 8, 16, f6,' i6, ~i6, 24, 24, 24, 24, 0, 0, 0, 0, 12, i?, !'2, f2, 24, 24, 24, 24,. 36, 36, 36, 36). The block diagram of the device executing.the given algorithm is presented in Figure 1 and consists of one arithmetic circuit (AU), the input and output storage elements (ZU1 and ZU2 respectively) and permaaent memory (P7.U). (b) i~si i - I p~...P.rs R~�..Aa~ AaY..p~ A~e...Ara ~ ~g~i~3Y------�------- i~ -----i o ~6 u o!~ ao o rz u ~ c ae ~r o t~ te o u K I r-- ~ ~ 0 J6 ! 0 N 16 0 IS W ~ I R91 ' 0 JE 76 0 I~ 0 !1 !f ~ ' 0 h ~J 0 li if 0 6 71 ~ ' ~ 0 ?i ~p 0 !6 10 C E q ~ ~ 0 1+ t7 0 iF /A 0 A 9 ~ ~ 0 1~ l~ U W I6 0 E 8 ~ ~ ~ 0 1f fi 0 d N ? { ~ f ~ o r ra o e ~r o� r ~ ~ I o it rs a a a o� s I ~ ~ o u i o� o ~ �o o~ ~ I Z Z Z I i o c o o~ a c ~ 1 I ~ ~ 0 0 0 0 0 0 0 0 ~ ~ x ~ ~ X ~ - L - - - J x I - - ~ a ~y1------------=------- ' CC~ I Aa ��pu A%...Nn qu"'~a Aw...~p ~ I L - - - - - - - - - - - - - - - - - - - - - _ J Figure 1. Block diagram of the device executing the APN algoritUm. Key: a. PZU b. ZU1 c. ZU2 The APS algorithm Wn=~npnsn{Pw~ln-~~//t~~w} ~15~ . . . PTL~'~ {P~ (Ia-R~DA)Mp} . . . PAS� {P�D�M*}P�5,,, 15 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 tb ,;ay~- ~ ~ Ao...A~ A~...R,u R...A~r ~~e...pu F . . ----...h ---------------""I ' ~a~ jn39 ' ~ - I - I x A91 I~ ~s o i~ aa o u t~ o u s o - ~ 06 Ii. 0 1ti JO 0 ~L tE 0 0 6 0 ~ X ~ ~ u as o r+ n o ~t u o o a o ~ z I Jf J6 0 t~ ? 0 if 1S 0 0 0 0 ~ X ~ ~p 0 16 ~7 0 D 0 0 f 0 1 ~ S~ tE D 16 tC 0 E O 0 ~ 0 I ~ , t~ t6 0 16 ~a 0 L 10 0 0 f 0 I r~ r~ o +s ~s o � a e a o 0 0 ~ ~ I , ~ i~ u o s n a o o~ o I I I r u o e w o � c o 0 o I ~ iZ t3 0 E 9 Y � J 0 0. 1 0 i i ~ 1I i! 0 6 L 0 ~ ~ 0 0 0 0 ~ ' 0 0 0 0 0 0' 0 0'0 0 0 D I I 0 0 0 0 0 0 D 0 0 B 0 0 i ~ ~ 0 0 0 0 0 ~ 0 S 0 0 0 0 I I ' ' ~ ~ F ~ l- - - - - - 'J - - (c) ~yt---- , . , . A~ . ~q~ 1 ~ qe... Ars AK... Aai ~t...Au 1e... ~ - ' ~ Figure 2. Block diagram of the device executing the BPS algorithm , Key: a. PZU b. ZU1 c. ZU2 ; ~ The BPN algorithm ~ IIn=Un~n{rnLQn\~i~j*-i/Qr~t~nJa7~... - . ~ I {Pn ~ ~Qn~DR~ln-~~'~C*~~w_!}Ua~A... ~],~j~ I ~..{Pn-'~KnDn`ln~`~~ !/u�`~^i�~ . The BPS algox7,tl~t _ . - . . I - Wn=Sn {Q� ~D:~Iw-=) QA1 M� . . . (17) , . . . S, {Pn-= ~ Qn (~k~ln-~) Qn ) Mr-= }M,, . . . ...S~{P�-=[Q�D�Q~]M� =}M�S�M�Qn. . Example: ~or N~ 64 ex~ressi.on (17~ assuraes th,e foxm ! ' W~=S, {Q~ (D:~I,) Q:} M~S, {F~ I Q,D~Q~ ~ M~}M~S,M,Q,, . whare ~ [QaDsQal M, = di,ag ~o, 0, 0, 0, 0, 2, 3, 0, 2, 4, 6, 0, 3, 6, 9, , � 0, 0, 0, 0, 4, 5, 6, 7, 8, 10, i2, !4, i2, i5, 18, 2f, ; 0, 0, 0, 0, 8, 9, 10, ii, 16, i8, 20, 22, ; 0, 0, 0, 0, 12~ 13, 14, i5, 24, 26, 28, 30, 36, 39,� 42, 45). ; Q3 (~s ~ ti) Qo;= dia$ (0, 0, 0, 0, 0, 0, 0, 0, U, Q, 0, 0, 0, 0, 0, 0, 0~ 0, 0, 0, 4, 4, 4, 4, 8, 8, 8, i2, i2, i2, i2. ; 0, 0, 0, 0, 8, 8, 8, 8, 16, !B, 16, i6, 24, 24, 24~ 24, ' 0, 0, 0, 0, 12, 12, 12, 12, 24, 24, 24, 24, 36, 36, 36,36). The block d3~a.gram o~ th~e hardware execution of the given algorithm is presented in ~ Fi.gure 2 ~ ' ~ . ; ~ 16 FOR OFFICIAL USE ONL~ , APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02108: CIA-RDP82-00850R000300070024-5 FOR OFFICIAL USE ONLY SPN algorithm _ Wn SnDnMn . . . Sn ~In-k~Dh~ Mn . . . Un ~In_=~D=~ ~~a7n/~~Q~, ~ZB~ SPS algorithm ~ wn =snll[n{rn~rMn}sn~rrn... ~19~ {Pn~rn_.~Dh~!?r~}s~~n... {Fn~rn_=~D,~M~}snMn. DPS algoritt~ ~ - R'�=Q�P�SrPn{P� '[Q�D~Q~]MR-=}S*... ...P*(P* '~~~~D?~~In-.)~~�~.Mn-'}Sn... (20) . . . P� {Q* ~D~~In-:) Q*} 5,,. ~ DPN algorithm - ~*=^nnn~n rn*-ir�n~n^n~~~-!} ~l ~ t~ l~l ~l . . ...P~Jn{Pn-f ~Q~~DR~In-A~Qn~IILn 1} ~Ll~ - . P�S~ {P� ~ Q~ ~D:~I�-Z) Qn l Mn} P~s~� From the above-presented formulas it is obvious tha.t each of the algr~rithms is exec ted in n= log4N steps. For each of the above-investigated algorithms thE following basic property is satisf ied: its structure is constant in all steps. The given structure permits the use of a memory with series access. The organi.zation of the input or output memories can be parallel or series. 'the arithmetic circuit can be asyu~etric (Figure 1) or sy~etric (Figure 2). For convenience of use the basic distinguishing features of the given algorithms are presented in Table 1. The processing in real time usually requires that the spectrum calculation tiime be equal to the signal duration T, that is, for the given algorithms the following equality must be satisfied p Tp=T 4 log~ N, (22) where is the time in seconds required for the performance of the basic base 4 operation including the memory access time and the operating time of the arithmetic circuit. Since the equality FB = N/2T is valid, where FB is the Kotel'nikov ~re- P quency, the expression (22) assumed the foxm I/ 4 7' _ 2l sFB lo�~ ~FB P (23) +Jhen using the equality (23), the graphs presented in Figure 3 were constructed which indicate the limiting possibilities of the systems, that is, they determine the minimum resolution or the admissible execution time for the given Kotel'nikov - frequency. For comparison a curve is also presented for the base 4 BPF algorithm with substitution. The graphs were constructed Ymder the coudition that the memory access time is on the order of 1 microsecond, and tlxe operating time of the aritlbna~ic circuit is 2 microseconds. The values of FB for th~ most widespread values of N are presented in Table 2. ~ 17 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 % FQ, Kry ~a~ ; 200 ~ ~ . ; !60 i IZO 4 6 ' g0 3 ; ' S ~ Z y0 ~ . , -4 -Z 0 tig Tp i Figure 3. Ratio of the upper frequency and length of the realization ; during operation of a system for fast Fourier transformation in real ~ time: 1-- curve for the algorithm with substitution; 2-- curves for ~he APN and the DPN algorithms; 3-- curve for the BPN and SPN algo--.~. - rithms; 4-- curve for the APS and DPS algorithms; 5-- curve for the i~ BPS and SPS algorithms; 6-- curve for the algorithm with counter~.:~s ~ structure. ~ - ; Key: a. FB, kilohertz The abo~ve-investigated properties of the BPF algorithms with constant structure per- ' mit the development of algorithms that are more adaptable for simultaneous process- , ing of two complax signals. ~ _ 3. BPF Algorithms with Counterstructure ~ Let us propose that it is necessary to obtain the spectra of two complex signals in i real.~times simultaneously. If we use the BPF algorithms with substitution for;~the ; given ~ievice, then from Table 2 and Figure 3 it is possible to deter~ine the limit- ; ing characteristics of this system. The f ollowing belong t~ the basic equipment expenditures required f or execution of the given system: two arithmetic circuits and a memory with a capacity of 2x2x~Txk bits, where N is the signal length, and k is the number o~ binary bits required for representation of the inp:~* and intermediate values. The application of BPF algorithms with constant structure, as is obvious from Table ; 2 and FigLre 3 leads to expansion of the values of the limiting parameters and simpli- � fication of the hardware (the control circuit is simplif ied). It is necessary to note that these values are achieved as a result of increasing the memory size from 4xNxk~�bits to 2x4xNxk bits. ~ If am,ong the algorithms wiCh constant structure we isolate the algorithms which have ! a def ined order of reading and writing data, then ip tt ~.is'.possible to~. ~onstruct~ ~a ; 18 FOR OFFICIAL USE ONL'~ ~ . i APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 FOR OFFICIAL USE ONLY Table 1. BPF algorithms with constant structure Algorithms APN APS BPti BPS SPN SPS DPN DPS Read from Series + + + + - mean~ry Parallel + + + + - ~nter in Series + + + + - memory Parallel + + + + Arithmetic Symmetric + + + + circuit Asy~e~tric + + + + Order of Multiplicatio + + + + execution of Addition + + + + + + + + operation Multiplicatio + + + + Table 2 Upper boundary frequency, kilohertz N Algorithm ith sub- ~ APN APS BPN BpS pptim~l stitution DPN DPS SPN SPS 64 81 108 114 126 135 185 - 256 61 81 86 94 102 138 1024 49 65 69 75 81 111 4096 41 54 57 63 68 92 - a system havi.ng def ined advantages. The block diagram of such a device using the APN and BPS is presented in Figure 4. Thesignal sl written in the memory ZU1 is rhe input signal for the algorithm APN, and the signal s2 written in the ZU2 memory is the input signal for the BPS algorithm. For example, for iV = 64, 0, 15, 31 and 47 samples of the signal sl arrived at the input of the arithmetic circuit of the APN algorithm, and 0, 1, 2 and 3 samples of the sigr_al s2 arrive simultaneously at the input of the arithmetic circuit of the BPS algoritFim.~ Af ter performan~e of the calculations at the output of the arithmetic ~circuit of the APiJ algorithm, da.ta a.ppear which are entered in the cells of the ZU2 memory where previously there were ~ 0, 1, 2 and 3 samples of the signal s2, and the data from the output of the arith- metic circuit of the BPS algorithm are entered in the corresponding cells of the ZU1 memory. From the performed analysis it is obvious that the use of the BPF algorithms with constant structure and defined order of reading and writing (let us call the given algorithms BFF algorithms with counterstructure) permits the memory size to be cut in half . The above-presented choice of BPF algorithms with counterstructure (APN and BPS) does not permit the organization of an optimal system, that is, a system in which the arithmetic circuit and memory operat without a pause. However, if we are limited to the algorithms, for example, SPN and DPN, for which a defined order of execution of the operations is f ixed in each step, then in the block diagram presented in Figure 19 . FOR OFFICIAL U'SE ONL~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000300070024-5 � 4, one arithmetic circuit will be excess. Accordingly, it is possible to create an optimal system (let us propose that for this purpose in the arithmatic circuit there are special buffer registers available), which will be capable of procesaing two complex signals with minimum equipment expenditures: one arithmetic circuit, a 4XI1xk bit memory and control circuit. The limiting parameters of the given system can be determined from Table 2 and Figur e 3. 1'He algorithms APN and BPN; APS and BPS; SPN and DPN; SPS and DPS which differ from - each other by the type of arithmetic cir cuit and the ordex of execution of the operationcan be used asBPF algorithms with counterstructure. The given algorithms permits the developer to manif est defined flexibility when constructing systems _ designed f or simultaneous processing of two complex signals. _ - (a) ~3yt ( I ~ _ J L------ - i Z � f E i f- ~ ~ F E ~ ; x " /13y ~b) fl3y x x , AliN ~e~ _ 6AC x � . , x ~ ~ i , _ Cd~S!2------------ Figure 4. Block diagram of the device executing the BPF algorithm with counter structure. _ I:ey: a. ZU1 memory b. PZU c. BPS d. ZU2 memory e. APN Thus, the performed studies of the properties of the BPE algorit.hms with constant structure permitted determination of the algorithms wi.th co~,iaterstructure which can be used for the creation of optimal devices that are efficient with respect to ~ equipment expenditures designed f or real time processing of two complex signals. _ 20 FOR OFFIC" ~I, USE ONLX ~ ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 FOR OFFICIAL USE ONLY BIBLIOGRAPHY 1. L. Rabiner, B. Gould, TEORIYA I PRD~IF.NENIYE TSIFROVOY ORPABOTKI SIGNALOV (Theory and Application of Digital Processing of Signals), Izd. Mir, 1978. 2. CINQUIEME COLLOQUE rlATIONAL SUR LE TRAITEMENT DU SIGNAL ET SES APPLI~ATIONS, "tlice, 1975. 3. ASPECTS SIGNAL PROCESS, Part II, Proc. NATO Adv. Study Inst., Portovenere, La Spezia, 1976. 4. W. G. Halvorsen, I. S. Bendat, SOUND AND VIBR., Vol 9, No 8, 1975, p 18. 5. V. A. Benignus, IEEE TRA~VS., AU-17, 1969, No 2, p 145. 6. B. I. Trampe, BRUEL AND KJAER TECHN. REV., No 4, 1970, p 3. 7. D. Ye.Bakman, RADIOTEKI~JIKA I ELEKTRONIKA (Radio Engineering and Electronics), Vol 21, No 6, 1976, p 1275. 8. D. Ye. Bal~an, L~ A. Vaynshteyn, USPEKHI FIZ. N. (Progress in the Phy.sical ~ Sciences), Vol 123, ho 4, 1977, p 657. 9. V.. M. Yefanov, I1. I, Korshever, V. M. Lobastov, G. G. Mashutkirx, AVTOMETRIYA (Autometry), No 3, 1973, p 3. ~ 10. C. Berthomier, N. Corniliea~Wehrlin, ANN. TELECOMMUNS, Vol 30, No 7-8, 1977, p 224. _ 11. H. Sloate, IEEE TRANS. CIRCUITS Aiv~ SYSIE:I, Vol 21, No 1,�1974, p 109. - 12. E. I. Bovbel' , V. V. Izokh, I. Yu. Shmidov, RADIOTEKI~IIiZA I ELEKTRONIKA, Vol 18, No 11, 1973, p 2311. COPYRIGHT: Izdatel'stvo "Naukaf', "Radiotekhnika i Elektronik~', 1980 [45-10845J _ 10845 CSO: 1860 21 'FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02108: CIA-RDP82-00850R000300070024-5 ; UDC 621.391.2 EFFECT OF ~HE FORM OF SEA WAVES 0:1 TIiE SCATTERED RADIATION CHARACTERISTICS Moscow RADIOTEIaiNIKA I ELEKTROidIKA in Russian Vol 25, No 8, Aug 8Q pp 1770-1774 . ma_n_~iscript received 28 Mar 79 ~ [Article by I. F. Shishkin] ' [Text] In recent decades, in the broad oceanographic literature a detai.led study has ~ been made of the relation of the characteristics of radiation scattered by the sea to the condition of the water surface. The dependence of the scattered signal pa- - rameters on the form of the sea waves constitutes an exception. This is explaine.d I by L-he inadequacy of the widely accepted two-scale model'of the sea surface to the I mechanisms present during scattering by waves of finite steepness. i ~ Graphic results are obtained when investigating the diffraction of acoustic or elec- tromagnetic waves on a trochoidal profil.e. The expressions proposed in [1] for the angular factor determining the scattering i.ndicatrix of a field incident on a segment of the surface with the simplest types - of large-scale unevennesses are easily generalized to the case of symmetric periodic : unevennesses of arbitrary form. For a reflection coefficient modulus equal to one, , the dependence of thP angular factor modulus of the form of the unevennesses, the angle of irradiation of the surf ace a0 and the direction of the diffraction lobe ; - peaks am has the form ~ a ~ i 1-COS~Q+n-lXO~ ~1 ~1 ~_~~m-t-2D-...-(n-t)tJt~f~... ~1~ t (ac~,) _ ~ L L ~ sin ac,,,-sin ao ~ e--~ o--~ t--�� ...1p~S~~17~S2~Im_2I-7p-...-nl~sl~ ( ~ where the arguments s of the Bessel functions of different order are expressed in , terms of the coefficients o.f expansion of the surface profite i*: ~ I'ourier series _ an by the formula ~ ; s�=ka~ (sia ac,~.-sin ao) ~2~ (k is the emission wave number). For proFiles defi.ned by the parametric equations ~ _ i s=8--a sin 9, { y=a ~os e 1 ~ ; 22 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000300070024-5 FOR OFFICIAL USE ONLY f00 BO ,~a 60 , ~u� . r ~2~ Q a. o ~o ~ ~ d . ~ ~ - P H - ,~b ?.00 160 /10 d0 UO 0 40 BO >20 160 YOOq6 ~1) a ~1~ ~po eo . . , 1~D 6O . u~ , \ ~ ~2~ = a N O ~ d ~ n P ' . H .Q62D0 ~60 120 BO 40 0 ~t0 BO IZO 160 Z00,�6 ~1) ~ ' ~1~ . 100 a0 1ti0 60 _ \u~ N / n ` ~ ~ O ~G~ O - ~OO N d 0 ~ _ Q H _ ~ 1~6 200 '!60 IZO BD 40 0 40 BD 120 160 200 a6~1 ~ c - Figure 1: a-- h/A = 0.05, a=~= 0.157; b-- h/A = O.I, a= R= 0.314; - ~--h/I1=0.1, a=0.65, 5=0.314. Key: 1. decibels 2. angles in degrees ~ 2~ _ - FOR OFFICIAL US~ ONLY - APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 roo av ~ ~ ~ ,~0 ~o , 7 . - 1 a ~ 00 ~ p d ~ ~ a H ,q6200 160 /20 BD /!0 0 u0 BO /20 160 200,~6 (1) a C1) 100 Bo ~ . ; ~1 . ~ ~ ,~0 ao i _ 7~~~ Q O~ ~ ~ N ~ . \ O N . \ 1 ~t ' ~I . a6Z00 /60 f10 BO 40 D [!0 BO 1Z0 160 Z00.&6 ~l) b ~l�~ ' - ~00 . � eo . ~ ~ . ~ ~~Q . - ~ (2) ~ ~ _ : a. N Q ~ ~ ~ p> _ fL n P _ H ~t 6 200 !60 110 BD /~0 0 u0 80 110 160 200 ~t 6 (1) c (1) Figure 2. a-- h/Il = 0.05, a=~= 0.157; b-�- h/A = 0.1, a=~= 0.314; c-- h/A = 0.1, a= 0.65, R= 0.314. ; Key: 1. decibels 2. angles in degrees ; i - I i 24 FOR OFFICIAL USE ONLY ~ I . >i APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 I FOR OFFICIAL USE ONLY for n > 1 [2], i _ a�=~[1,~_~(na)+1�+t~Ra)~-a~~~~na)- 2. ~I~n-a~na)+In+:(~)]. (3) ` Thc> calculstion by formula (1) is performed as fpllaws. By the given values of a0, the ~ea wave length !l and the radiation wavelength a from the candition A m = - (cos a,,, - c~~s an) for m= 0, +1, +2, the directions of the diffraction lobe peaks are defined. Then for each direction a by formula (2) all the arguments of the Bessel functions sn are found in (1), aftem which f(am) is calculated. The number of harmonics n depends on the required accuracy of~the calculations. In practice it is insured when using the following approximate expressions in place of (3) ' a~ ~ ~ ( i -0,375�z+ 0,002fxc+--0,000759a�), ~z'~ ~ (O,Sa-0,333a'+O,OG25a'} , ' as~~(0,375a=-0,359a++0,1108a�), ac ~ ~ (0,333a'-0,4a') . ~ a~ _ ~ (~,325~ac'-0,475a6) , ' aa=~0.3375acs, a~ ~~0,3647a�. Since the Bessel functions are negligibly small for the values of the indexes greatly ~ exceeding the magnitude of the argument, in (1) the summation is actually performed within bounded limits. The form of the sea waves is given by the values of a and S. For a=~ the wave ~ _ prof ile is trochoidal, the case a>~ corresponds to the so-called V. V. Shuleykin waves. The steepness of the waves defined as the ratio of their height h to length A increases as the values of a and S increase, and it reaches a ma.xi.mum value of - 0.143 for trochoidal waves with a=~= 0.45, and far the V. V. Shuleykin waves, for a > R < 0.45. - In Figure l,a,b, the scattering indicatrices are calculated by formula (1) for the trochoidal waves of diff erent steepness and A= 30 cm of radiation with 3 cm for vertical (a = 270�) irradiation of a section of the water surface are presented. From the figures it is obvious that the variation in wave steepness leads to notice- able redistribution of the energy ;,alculated in the surrounding space. Iiere a role is played by the variation of the wave height. For example, in the directinn of the bac~ sca~tering the amplitude of the echos as a result of an increase in h decreases - by hundredths of a decibel. In pure form the dependence of the scattering indica- _ trix on the foru? of sea waves is traced on a model of the V. V. Shul~yt~h waves. The = sharpening of the crests of these waves takes place as a result of an increase i.n the ellipticity of the orbits in which the surface particles of the wa~~e move without - variation of h and A. The transforma.tion of the scattering indicatrix is illustra- _ ted in Figure l,b,c. The amplitude of the back-scattered signals does not vary within the limits of accuracy of the calculations. Analogous phenomena occur for sl.ant irradiation of the water surface, which is illus- _ trated by the scattering indicatrices constructed in Figure 2 for the same values of 2~ FOR OFFICIAL USE ONLX APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02108: CIA-RDP82-00850R000300070024-5 !1, ~ and a~ = 300�. The difference is the absence of symmetry of the indicatrices wiCh respect to the direction of mirror reflection. The amplitude of the signals started in mirror direction by trochoidal waves decreases by hundredths of a deci- bel as a result of an increase in their hei.ght. When scattering by V. V. Shuleykin waves, it remains constant. Thus, whatever the angles of irradiation of the water surf ace (wi,`.hin the limits of , applicability of the investigated method [1]), the amplitude of the signals scattered in the direction of the mirror reflection does not depend on the shape of the sea waves.: Its value is determined by the angle and the amplitude of the first harmonic of the spatial spectrum of the surface waves al. The angular factor in the mirror direction is ! -cos (cc,,,-aq) 1 = lo (s!). sin a~,,,-sin ao In practice the signals scattered in the mirror reflection direction are used for vertical sounding of the wave surf ace from aircraft in the combined reception-trans- mission mode. Here, consequently, it is impossible to obtain information about the shape of the sea waves. This fact must be considered when designing means of moni- - toring world ocean pollution by petroleum products based on recording the smoothing i_ of the sea waves by surface-active films. _ ~ _ - - I- f~�`%X~a~ ~a~ " ffa; xJ,,as (a) . ~ a,-i70 . - P00 ppp . 150 !SO ~ ' ' ~ ~ t90' ~pp 100 ! ~ JOG'. sp Z SO 31~' , 3 ~ _ I - 1d0 160 150 Z60 170 1R0 190 300 ao,z~ca ~~lj~ O,P Q4 Q6 Q8 H/ll Figure 3: 1-- a= R= 0.45; 2-- Figure 4: a= S cth 2~r(H/A); ' a=~= 0.314; 3-- a= B= 0.157. 0.314. ~ey: a.. decibels b. degrees Key: a. decibel~ ~ During inclined sounding the amplitude of the back-scattered signals depends on the . shape of the waves. The greater the angle of incidence, the stronger this dependence. Figure 3 shows the case of active location of waves of trochoid~~. r~ofile, and Figure 4 shows V. V. Shuleykin waves with 0.314 and a= S cth 2~t(H/11), where ~ H is the depth of a body of water. ~he presented relations confirm the conclusion ; that was drawn. The cons~deration of the asymmetry of the sea waves can be considered a further de- ' _ velopment of the theory. The author is grateful to I. K. Mileyeva for computer calculations by formula (1). , i i 26 ' FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 ~ FOR OFFICIAL USE ONLY f BIBLIOGRAPHY 1. L. M. Brekhovs~Cikh, ZHETF (Journal of Experimental and Theoretical Physics), Vol 23, No 3(9), 1952, p 275. 2. L. A.~Rorneva, TRUDY KOORDINATSIONNYKIi SOVESHCHANIY PO GIDROT~INIKE (Works of the Coordinating Conferences oa Hydraulic Engineering), Izd. Energiya, 1972, p 36. - COPYRIGHT: Izdatel'stvo "Naulca", "Radiotekhnika i Elektronika", 1980 [45-10845] 10845 CSO: 1860 1 ~ 27 FOR OFFICIAL USE ONLX APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 FOR QFFICIAI. USE ONLY UDC 621.396.669 A COMPARISON OF THE NOISE Il~IUNITY OF TWO DETECTORS WHICH OPERATE USING THE METHOD 0:' BILATERAL SPATIAL CONTRASTS Kiev IWZ RADIOEIsEKTRONIKA in Russian Vo1 23,No 8~Aug 80 pp 32-36 ~ . manuscript received 30 Mar 79,after revision 1 Nov 79 [Paper by V.T. Belinskiy, Yu.L. M.azor and R.M. Tereshchuk] . ~ [Text] The noise immunity of two noise signal detectors which operate using the method of bilateral spatial contrasts is treated, where the detectors � differ in the procedure for the camparis~~ ~r signal and reference voltages. The advdntage o~ ~ detector where the signal voltage is eampared to the average reference voltage over a detector in which . the signal voltage is campared to each-of two , reference voltages i~ d'~o::strated. In noise signal detectors which use the method of bilateral spatial contrasts, various methods are employed to compare the signal and reference voltages. Block diagrams of two detectors are shown in ~igure 1, each of which contains a standard detection channel (TTO) and reference and signal voltage driver (FSON). The TTO consists of the antenna system (AS), the bandpass filter (PF), t1~e detector (D) and a low pass filter (FNCh). The low pass filter storage interval T, is chosen equal to the time for sweeping the antenna system through an angle equal to the width of the main lobe of the directional pattern (DN). The reference and s~~nal voltage driver consis~5 ^f d~lay lines LZ1 and LZ2. The voltage U4 = U4(t) is chosen as the signal voltage, which corresponds to the position of the antenna system directional pattern at the point in time t, while chosen as the reference voltages are U4 = U4(t+T) and U4 = U(t-T), which are shifted in time relative to the signal voltage by �T. 28 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02108: CIA-RDP82-00850R000300070024-5 FOR OFFICIAI. L'SE ONLY The basic distinction between the detectors consists in the method of camparing the signal and reference voltages. In the detector of Figure la, the signal voltage is compared in a threshold gate (PU) with the mean arithmetic value of the reference voltages, where this value is obtained by means of an adder (S) and a voltage divider (Del). The decision that a signal is present is made in the case where the threshold voltage Upor is exceeded by the signal voitage US = U4 > Up~r = = Kd(U4 + U~), where Kd is the transmission factor of the voltage divider (Kd > 0.5). In the detector shown in Figure lb, the signal voltage is compared to each reference voltage. The decision that a signal is present is madQ in the case where the threshold voltage Upor in the threshold gates PU1 and PU2 is simultaneously exceeded by the output voltages of the sub- traction gates W1 and W2 respectively: _ U4-Ua>U~p ~1~ - U4 - U4 > UaoP ~ . Decision (1) is made by a device which performs an AND logic operation. The specified false alarm probability (VLT) is achieved through the choice of the threshold voltage. In the following, the detectors con- sidered are designated in accordance with the operational algorithm as ODKS - a detector with bilateral contrasts with respect to tihe mean value and ODKI - a detector with bilateral contrasts and an AND logic - gate. , The noise immunity of an ODKS was treated in [1] with the following assumptions: the interference voltages corresponding to the adjacent directions of the antenna system directional pattern are independent; PF is an ideal bandpass filter with a banZwith of ~f; D is a linear detector with no inertia; SNCh [low pass filter]~~is an ideal integrator. ' The case where ~fT � 1 which is important in practice was analyzed. We shall estimate the noise i.mmunity of an ODKI, adopting the assumptions made above and ~fT � 1. In this case, it can be assumed that the voltages at the outputs of the reference voltage and signal driver have a gaussian distribution both in the presence and the absence of a signal, mean va7~ues of : a,=K1aZ~ a4 =Kld~ a4 = Kld ~2~ . and mean square deviations of: 29 , FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 FOR OFFICTAL t~SE '-0NLY z ~ a a a ~ h ~ti h ' a v ~ . . ~ ~ � v ~.J ~ $ . � � . , ~i ' � w ' u ~ ~ ~ ~ v .i _ _ ~ b x ~ ~ FI � 0~ e C r-1 d ri - ~ ~ N ~ D ~ ~ ti ~ ~ ~ ~ ~i ~ ~ ~ ~ v ~ . ~ ---j FTr C N e"~ ~ LTt f�~ ~ y~.i N r+ aI r-i ~ Ri I~ O ~1 � w Gl W � ~ ~1 1J 1~ d ~ c~ r--~ ia 1.~ d�^ r"+ Cl N N r-I j~ ~ d~ N r-I S-~ ~ Gl 'C b0 a.~ O ~ i^' N a~ ~ ~ a.~ ti cd 7 h ~ ~ i ~ A ~ 'J~ W m ~ L'. ~'b '+d ~~-I r v I,~ ~ iv, S~-+ ~ Ol t0 ~-I r-1 r~-1 N c) O .C ~ ~f cd tA F+ LL c0 O 00 ~O .C tA i b~ c0 O F D+ td F+ m N tJ 1^+ ~i ~1. 1J 3 0~ tU r~ 01 1~ ~ d ~1 . ~ ~O Cl 'C! U O rl ri i-i Cl ~-1 .G Cl .C ` ~ 1.+ ~ Gl ~-~I m Gl Gl F+ O~.~ 1~ i~ ~ ~ u u u ~ r..+ u u'~ ~ u u ~ u � b a O ~ c~ O~ ~ ,-I ~~-I O HdaA~wacnwA~a~~ . . - �aicicawwc~ac~-+tia~..a~z a ~ 30 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000300070024-5 FOR OFFICIAL L~SE ONLY _ o-~/ o� d- vQ. d._Ka_ (3) ~-/\y zi 4- ~\2 4- z~f where K1 = 1/~ , K2 = 0.2/ fA T, 62, Q2 and 62 are the mean squa~e deviations of the interference voltage at the output of the bandpass filter corresponding to the three adjacent directions of antenna system ~ directional pattern. The probability that the voltages at the outputs of the subtraction gates U5 and U~ will simultaneously exceed the threshold voltage is: p"P - p~Us > U~p~ U6 ~ U~v) = f~~ d d ~ 4) z y~ y~ ~J:� `~mP _ where w2(yl,y2} is the coffibined probability density of the two indP- pendent random quantities U5, U5, formed from the three independent � ones U4, U4 and U4~ ,In accordance with [2]: ~ . ~z ~~Ji~ ya~ _ ~ ~+.~i ~X~ ~i ~i ~x~ dy~� where tul(xl), ~1(x2}, u~l(x3) are the one-dimensional probability densities of the random quantities U4, UJ~, U4; J4 5 is the Jacobian of the transform from the randam quantities U4, U~ and U4 to the random quantities US = U4 - U4, US = U4 - U4 and US = U4. In this case, Jq~S = 1, and therefore: ~ ~ ~ ~ ~ 3~ . . p ~a - yi~ a~= X z i~ y~ e7t (2n) o~Q4a, ) _o a~ (y a~ ~ X p ~ya- ~'l ~ r_ '--~s- l ~J~� 5) - eX ~ 2~a4)~ J e L 2~Q~ J d Following the substitution of (S) in (4) and integrating with respect - to y~, taking (2) and (3) into account, we derive the expression for _ the probability that the threshold voltage will be exceeded simultan- eously in PU1 and PU2 of the ODKI: . _ . C1C2 C1Cs (1-}- Cl -f- C~ r 1 1 X - pnp ~ YCz + C;~ exp Ct ~ CiLZ ~ C2 Jl . i a ~p l.~~l-~-Ci~~~-2KC1~~'1-C'2-CS'{'~'lC'2~z1 v - r r X J J ~ 2(~~ + ~2~~ + ~z) z. X ex 2 C,CZZ,z2 - 2KC2 (Cz - Cl - Ci C~C~ z2 - C2 (1 Ci) ~ I~1~2~ \ � P [ . 2 (C; -f- C;Cs -I- Cz) ~ (b) 31 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02108: CIA-RDP82-00850R000300070024-5 FOR QFFICIAL t~SE ONLY z~ a Upor/o~4 is the normalized threshold value and K= K1/KZ. The false alarm probability PnT and the det.ction probability P~p are ~ defined by the expression: p,~T npH C1= vs/d; Cy � az~az, ~ _ ( 7) ~ p�D when P�~ rt x C-v a~ 1 ' ~8~ P i- 2/ ~ y~ Ca = Qz/QS l~ 1-{- y, where Y= Q~~/o2 is the ratio of the signal power to the interference power at the bandpass filter output. - By using expressions (6) and (7), one can select the value of Zp for which the specified false alarm probability is assurred. Shown in Figure - 2 are the detection characteris~ics computed from formulas (6) and (8) ~ for various kinds of interference field anisotropy and ~fT = 104, where - the value of d~ was established for the worst case nature of the aniso- . tropy (C1 = C2 = 0.95), so that the maximum false alarm probability did ~ not exceed 10-4. i P' In the comparison of an ODKI and ODKS, I no the change in the coefficients which ~g C-, 5 0.95 / j~ /,05 def ine the nature of the interf erence , ~ ~~0,95 / / /,P5 field anisotropy f~' � '~a~P*'' 0,4 directions of the antenna sys~~~n direc- ~05 tional pattern was taken in a range of - 0.95 to 1.05. In the worst case as ~0,/ 0.3 0,5 ~ regards the false alarm flow for the nature of the anisotropy (C1 = C2 = - Figure 2. = 0.95, the values of the transmission ' factor ~of the voltage divider Kd (for _ the ODKS) and the normalized threshold zp (for the OnKI) were determined, for which a specified value of Pf.a.O ~ [false alarm probability) is assurred. Then, the threshold ratios Y0.9~ and the corresponding [detection] probabilities P~o = 0.9 (Table 1) and the values of the false alarm probability (Table 2) were determined - for each detector using formulas [1] (for the ODKS) ,,r (6)-(8) for the ODKI for various kinds of interference field anisotropy. For the ODKI, ~ the values of zp and the threshold ratios ~yp,q were dete~ined on a camputer using numerical integration and searching fui :'~e extremum of a one-dimensional quality function using the method of the golden mean [3]. The indicated calculations were performed for various values of ~fT and PnTO (Tables 1 and 2). ; Then, similar calculations were also performed far both detectors where - _ the initial setting of the threshold zp (the coefficient Kd) was made ~ 32 FOR OFFICIAL USE ONLY ~ i I ~ i APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 FOR OFFICIAL ['SE ONLY assuming that the interference field was isotropic (C1 = C2 = 1). The ,I results of these calculations are shown in Tables 1 and 2. TABLE 1 THRESHOLD RATIOS Y0.9 Iloporoede orxoweHxA Yo,9 ~ (3~ Xapaxrep axasoTponxN nona nowexx . Crpyxry- o ~/T Pa CI=0.95 C1=0,95 C1=1 C1=0,95 C1=1 C1-1.05 _ pY~aTenA C-0,95 I C-1 IC -1 C--1:05 C-1,05 I C-1 ~05 s- s- s- L4~ Ycrasoaxa nopora npx C1=Cs= 1 . O,qKC 0,095 0.15 0,21 0.21 0,2? 0,34 OIIKFI 1,08 1.23 1.31 l,l2 1,46 �.1.54 io-' la o.uxc - - o.osa o,osa o, ~a ~o, i~ OAKN 0,21 0,31 0,34 0,45 0,46 0,47 OAKC 0,13 0,19 0.26 0,26 0,32 0,38 OJ.~KN 1,41 1~57 1,6T 1,80 1,84 1,95 ~0-0 ~a o11KC - - o,os o,os o, ~s o, ~s OAKN 0,28 0.39 0.42 0.53 0,54 0,56 _ ~l YcraHOexa nopora npx C1=.C~=0,95 1~ OAKC 0,21 0.28 0.34 0~34 0.42 0.48 OJ~K1~I 1,29 1~44 1,53 1,66 1,70 1.80 to-' lo, oAKC o,os o.i2 o,ls 0,18 0,24 o,ao OAK~I 0,33 ' 0,45 0.47 0,60 0,62 0~63 10, ~AKC 0,25 0.32 0,39 0,39 0,46 0,53 OAKFI 1,54 1.80 1,92 2,02 2,10 2.22 �~0-6 ~a OAKC 0,08 0,13 0.19 0.19 0,25 0.31 ~AKN 0,41 0,52 0,56 0,66 0~69 0.71 OAI~ ~ Key: l. False alarm probability; 2. The detector structure; 3. The nature of the interference field anisAtropy; 4. The setting of the threshold when C1 = C2 = 1; 5. The setting of the threshold when C1 = C2 = 0.95. A camparison of the threshold ratios for both detectors (Table 1) shows the substantial advantage of the ODKS for both methods of setting the threshold (assimming C1 = C2 = 1 and C1 = C2 = 0.95) and any nature of the interference field anisotropy. In this case, the advantage of the ODKS in the threshold ratios is manifest more when the initial setting of the threshold is made assuming that tfie interference field is 33 _ FOR OFFICIAL USE ONLY _ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000300070024-5 FOR OFFICI~IL. USE ONLY isotropic and increases with a reduction in the product ~fT and the ' probability PnTO� TABLE 2 THE FALSE ALARM PROBABILITIES - � XapaxTep axasarpanxN nonA notrexa_~ nro ~~T PY 1- 95 I C-1 I C-0,95 C1-1.Q P o6 a x~ryitaa C-0 ~ i i ('Z}renA C -0,95 C~=1~ Cs=1,05 Cs= s- (4) Ycraxoexa nopora npa C1=C;-1 1.5�10-~ 10~ �10~ 1,4�10-~ - 10, � AKN 1� 10-3 ~p--4 2� 10-5 7, 8� 10-s ~o-' ~a oAKC t io-' ~o-~ -~i,s . Q~~~ pZ[Ky 2,4�10-z lp-4 4~7�10-6 3.5�10~ _ s i0~ ~DKS ~AKC 2.7�10"2 10-s tp- 40 dB). The deviations of the phase ~shift p~ and the reduction in the amplitude are one of the reference _ voltage c.omponents lead only to a decrease in ~T(wp)~ for the same lev~l . of nonlinear distortion registered with respect to the amplitude of the low frequency beat frequencies at the output. The dynamic range of the quadrature filter circuits studied here amounted to no less than 60 dB, and in a temperature range of -60 to +125 �C, ~T(wO~I � 2Uout = 1.5 - volts. We will note in conclusion that the most acceptable circuit for IC realiz-~ - ation is the symmetrical quadrature filter configuration with high pass f ilters in the channels, in which at the price of a slight drop in the signal suppression coefficient outside the transmittance band, one can - successfully provide for a maximum incr~ase in the temperature stability and the dynamic range, while preserving the bandpass type of amplitude- frequency response. BIBLIOGRAPHY ~ 1. Finkel'shteyn M.I., "Osnovy radiolokatsii" ["Fundamentals of Radar"], Moscow, Sovetskoye Radio Publishers, 1973, pp 89-91, 111-114. 2. Rigby, "Integrated Selective Amplifiers Utilizing the Principle of Frequency Conversion", ZARUBEZHNAYA RADIOELEKTRONIKA jFOREIGN RADIO- _ _ ELECTRONICS], 1967, No 6. 3. Timonteyev V.N., et al., "Proyektirovaniye integral'nykh analogovykh peremnozhiteley signalov" ["The Design of Integrated Analog Signal Multipliers"], "Elektronnaya Tekhnika", "Seriya 3", "Mikroelektronika" ["Electronic Engineering" "Series 3" "Microel.ectronics"], 1977, No 6 (72). 4. Tarasov V.P., "Kvadraturnyy fil'tr" ["A Quadrature Filter"], IZV. WZOV - RADIOELEKTRONIKA [PROCEEDINGS OF THE HIGAER EDUCATIONAL INSTITUTES. RADIOELECTRONICS], 1971, 14, No 12, p 1411. 5. Maslennikov V.V., Isaykin V.A., Tarasov V.P., "Izbiratel'nyye RC-Tsepi (obzor)" ["Selective RC Networks (Review)"], PTE jEXPERIMENTATI~TION INSTRUMENTS AND ENGINEERING], 1974, No 1. 52 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000300070024-5 FOR OFFICIAL USE ONLY 6. Tarasov V.P., "Vozmozhnosti uvelicheniya postoyannoy vremeni RC-tsepey v kanalakh integriruyemykh kvadraturnykh fil'trov" ["The Possibilities of an Increase of the Time Constant of RC Networks in the Channels of Integrable Qdadr~turP Filter.s"], in the collection, "Izbiratel'nyye sistemy s obratnoy svyaz'yu" ["Selective Systems with Feedback"], Taranrog, TRTI, 1974, No 2, p 106. 7. Tarasov V.P., "Sinkhronno-fazovyy rezhektronyy fil'tr" ["A Synchronous Phase Rejection Filter"], Patent No. 506112, BYULLETEN' TZOBRETENIY [BULLETIN OF INVENTIONS], 1976, Ido 9. COPYRIGHT: "Izvestiya vuzov SSSR - Radi.oelektronika", 1980 - [11-8225] 8225 CSO: 1860 ; 53 FOR OFFICIAL USE ONLX APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2047102108: CIA-RDP82-00850R000300070024-5 FOR OFFICIAL USE ONLY PUBLICATIONS, INCLUDING COLLECTIONS OF ABSTRACTS UDC 621.396.677.494 ANTENNA SYNTHESIS METHOBS: PHASEll ANTENNA ARRAYS AND CONTINUOUS-APERTURE ~ ~ ANTENNAS ~ Moscow METHODY' SINTEZA ANTENNA: FAZIROVANNYYE ANTENNYYE RESHETKI I ANTENNY S NEPRERYVNYM RASKRYVOM in Russian 1980 signed to press 2 Oct 79 P~ 2-5 [Annotation and table of contents from book by Ye. G. Zelkin, V. G. Sokolov, Sovetska~je radio, 4000 copies, 296 pages] [Text] A study is made of the methods of determining the amplitudes and phases of antenna excitation currents, the coordinates of the location of - its elements and other structural parameters of an antenna to insure the - given radiatioa characteristics. Line, plane and curvilinear micrawave antennas are investigated. Special attention is given to antenna arrays. ~ Separate chapters are included on the phase synthesis and synthesis of nonequidistant antenna arrays. Solutions are presented for problems of optimizing antennas in the presence of various restrictions of a physical and technical nature. Along with the classical method of solving synthe- sis problems, some nimierical methods which have been recently developed find reflection in the book. This book is illustrated by a large number of examples of solving various synthesis problems. Many examples in which important practical problems are considered ha~e independent inter- est. The book is designed for scientific and engineering-technical personnel engaged in antenna development and postgraduates. ~ There are 99 figures, 15 tables and 77 references. - Contents Page Foreword 6 Introduction 6 Chapter 1. Statement of the Synthesis Problem 1.1. Initial relations for a c~ntinuous aperture 10 1.2. Statement of the problem of synthesizing an antenna array 13 1.3. Mathematical formulation of the approximate synthesis problem 15 - 54 ~OR OFFICIe,:, liSE UNLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02108: CIA-RDP82-00850R000300070024-5 ~ FOR OFrICIAI, USE ONLY _ " _ ~ Chapter 2. Conditions oi E~dstence of an Exact Solution for a Linear Radiator 2.1. Necessary conditions of realizability of a radiation pattern 18 - 2.2. Wiener and Paley theorem 26 2.3. Uniqueness of the solution of the problem of synthesizing ~ ~ a linear antenna 23 2.4. Conditions of existence of an exact solution for linear antenna arrays 2g Chapter 3. Solution of the Synthesis Problems for a Linear Radiator 3.1. Partial pattern method 31 ~ 3.1.1. Expansion of the radiation pattern with respect to - the functions Sn(z) 33 _ 3.1.2. Solution of equation (2.2) in the form of a finite s~ 38 3.1.3. Ea-pansion with respect to Bessel functions 40 3.2. Eigenfunction method 43 3.3. Fourier integral method 49 - - 3.4. Linear radiator a�rray 53 3.5. System of linear radiators in a straight line 57 . 3.6. System of point radiators at identical distances apart 59 3.7. Representation of radiation pattern of the nonuniform array in the form of a sum of uniform array patterns 61 Chapter 4. Approximate Calculation of an Antenna by a Given Radiation Pattern 4.1. Statement of the problem 64 4.2. A. A. Pistol'kors methorl 65 4.3. Expansion with respect to Bessel functions . 67 4.4. Expansion with respect to the functions Sn(z) 68 4.5. Approximation using an equidistant linear array 76 4.6. Approximation using nonequidistant linear arrays 78 Chapter 5. Phase Radiation Pattern 5.1. Statement of th.e problem 82 - 5.2. Phase center of antenna 82 _ 5.3. Selection of thE phase radiation pattern 86 5.4. Calculation of the phase radiation pattern 88 Chapter 6. Approximation Synthesis of an Antenna Array 6.1. Initial relations 94 6.2. Approximation synthesis in a Hilbert space 95 6.3. Representation of the equidistant array factor in the - form of an algebraic polynomial 100 6.4. Methods cf Chebyshev approximation 104 6.5. Construction of the best approximation by quadratic approximation correction 108 ' 55 rOR OFFICI~~:, tiSE OvLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2047102108: CIA-RDP82-00850R000300070024-5 FOR OFrICIAL USE ONLY Chapter 7. Synthesis of Antennas with Optimal Parameters - 7.1. Lobeless,pattern 110 7.2. Optimal field distribution for a linear radiator array 113 7.3. Gain of Dolph arrays 125 7.4. Modified Dolph arrays 129 7.5. Optimal field distribution for a linear radiator 131 7.6. Quasioptimal linear antennas 141 7.7. Optimal difference pattern 142 7.8. Synthesis of a sectoral pattern 144 7.9. Matrix method of synthesizing optimal antennas 147 7.10. Some problems of superdirectional antenna theory 152 _ Chapter 8. Synthesis of Phased Antenna Arrays 8.1. Approximation phase synthesis 162 8.1.1. Method of Fourier coefficients 163 8.1.2. Projected gradient method 166 8.2. Synthesis of the square of the modulus of a radiation pattern 167 _ 8.3. Diminishing side radiation of a phased antenna array 170 8.4. Solution of the problem of phase synthesis using the Chebyshev norm 174 ~ 8.5. Solution of the Dolph problem of phase synthesis 177 8.~6. Method of e-steepest descent 179 8.7. Meth ods based on equivalence of the phase and amplitude distributions of currents 181 _ 8.8. Partial pattern method 188 Chapter 9. Synthesis of Nonequidistant Arrays 9.1. Statement of the problem 191 9.2. Gradient methods 193 9.3. Method of dynamic programming 196 9.4. Use of gaussian quadratures 199 9.5. Methods based on the application of functional operators 202 9.5.1. Fourier transformation 203 9.5.2. Laplace transformation 206 9.5.3. Differential equation method 208 9.5.4. Volterra equation method 210 9.5.5. Finite difference equation method 211 9.6. Restrictions on the coordinates of the location of elements and their radiation pattern 213 Chapter 10. Planar Radiators 10.1. Planar continuous aperture with linear polarization ~19 ~ 10.2. Planar aperture with elliptic polarization 223 ~ 10.3. Approximation calculation of field distribution � - and aperture shape 224 10.4. Synthesis of an antenna with given radiation pattern with respect to pawer 226 _ 56 . FOR OFFICIl,;. LSE UNL1 APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02108: CIA-RDP82-00850R000300070024-5 FOR OFrICIAL USE ONLY - 10.5. Rectangular radiators 227 10.6. Radiators with circular aperture 230 10.7. Approximation calculation of the field distribution by the method of approximation of a planar aperture - - by a beam antenna 238 Chapter 11. Planar Arrays 11.1. Conditions of existenc~ of an exact solution 244 11.2. Orthogonal equidistar.t array 246 11.3. Nonequidistant array 24g 11.4. Ring arrays 249 _ 11.4.1. Single-ring ar.ray 249 - 11.4.2. Multiring arr.3y 250 11.4.3. Array made of rings with uniform current distrib ution 252 11.4.4. Phase synthesis of an array from N uniformly excited rings 253 11.5. Optimal planar arrays 256 Chapter 12. Synthesis of Arbitrarily Shaped Curvilinear Arrays Located in a Plane 12.1. Initial relations 261 ' 12.2. Conditions of existence of an exact solution to an equation of the type of (12.1) 262 ~ 12.3. Solution of an equation of the type of (Y2.1) 266 - 12.4. Conditions of compatibility of equations (12.1) 267 12.5. Curvilinear radiators of complex shape 269 12.6. Synthesis of an array of radiators located in a plane along a curve 270 12.7. Some properties of 52,~~~~ and SZ`,~ Q, class functions 274 . _ Appendix Some Relations Between the Functions f(y) and R(z) 279 Basic Notation 286 _ Bibliography 288 Subject index 292 COPYRIGHT: Izdatel'stvo "Sovet;koye radio"~ 1980 [53-10845] 10845 CSO: 1860 57 FOR OFFICIt,;., li~E ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000300070024-5 V rutc ~rrl~ieu~ voc virLi ~ � ~ ~ ~ - UDC 629.7.054 , AUTOCOMPENSATION OF DRIFTS OF POWER GYROSTABILIZERS ; Moscow AVTOKOMPENSATSIYA IIKHODOV SILOVYKH GIROSTABILIZATOROV in Russian 1980 signed ~ to press 24 Apr 80 pp 1, 2, 108, 109 ~ i [Annotation and table of contents fro~ book by Georgiy Ambartsulovich Dzhagarov, Mashinostroyeniye, 780 copies, 109 pages] [AnnotationJ The book presents theoretical principles of drifts of power gyro- stabilizers. Versions of a method of autocompensation are examined, designs of hypothetical gyrostabilizers that realize the method of autocompensation are pre- sented, and drifts as a consequence of deterministic perturbations are determined. An examination is also made of the drifts of various types of biaxial and uniaxial ' - gyrostabilizers due to vibrations of the base relative to the unstabilized axes of the gyrostabilizer. Examples are given of calculation of drifts of various types of gyrostabilizers. The book is written fcr engineers who work in the field of designing and studying ~ gyroscopic devices and systems. Contents 3 ~ Preface Introduction 6 ' Chapter 1. Equation of Motion of Gyrostabilized Platforms 9 ' 1.1. Design of gyrostabilized platform with rotation of the input axes of the i gyroscopes about their own output axes 13 ; 1.2. Design of gyrostabilized platform with rotation of the input axes of i the gyroscopes about the proper axes of rotation of the rotors 16 ; Chapter 2. Autocompensation of Systematic DrifCs of Gyrostabilized Platforms . by Continuous Rotation of the Input Axes of the Gyroscopes About the Proper Output Axes 19 ' 2.1. Equations of motion of gyrostabilized platforms 19 , 2.2. Angular oscillations of a platform cause~? by external torques relative ; to the axes of the Cardan suspension of th~ platform 23 i 2.3. Angular oscillations of a platform caused by dynamic imbalance of gyro- scope rotors 28 ; 2.4. Linear vibrations of a vehicle 31 ; 2.5. Constant perturbing moments 32 ! 2.6. Moments that increase monotonically with time relative to the output axes of the gyroscopes 36 ' j . . ~ 'S8 I FOR OFFICIAL USE ONLX' I ~ . ~ , ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 FOR OFFICIAL USE ONLY 2.7. Moments that vary according to a harmonic law relative to the output axes of the gyroscopes 37 2.8. Forced motion of ball-bearing supports of a gyroscope suspension 38 Chapter 3. Autocompensation of Systematic Drifts of Gyrostabilized Platforms By Synchronous Continuous Rotatlon of the Input Axes of Gyroscopes About the ~roper Axes of Rotation of Rotors 53 3.1. Equations of motion of gyrostabilized platforms 53 3.2. Angular oscillations of a platform caused by external tarques relative . to the axes of the Cardan suspension of the platform 55 3.3. Angular oscillations of a platform caused by dynamic imbalance of gyroscope rotors 60 3.4. Linear vibrations of a vehicle 61 - 3.5. Constant perturbing moments 62 3.6. Error in setting the axis of rotation of gyroscopes 63 3.7. Moments that increase monotonically with time relative to the output axes of the gyroscopes 63 ~ 3.8.~Forced motion of ball-b.earing supports of a gyroscope suspension 64 Chapter 4. Autocompensation of Errors of Gyrostabilized Platforms by Synchronous Continuous Rotation of the Input t~es of Gyroblocks with Kinematically Coupled Gyroscopes 70 4.1. Autocompensation of errors of the inertial con_rol system 70 4.2. Autocompensation of systematic drifts of gyrostabilized platforms 80 Chapter 5. Investigation of Systematic Drifts of Gyroscopes due to Vibration of the Base Relative to Unstabilized Axes ~ 87 5.1. ~ao-axis gyroscopes 87 5.2. Single-axis gyroscopes 100 _ Referei~ees 1Q7 COPYRIGHT: Izdatel'stvo "Mashinostroyeniye", 1980 - [SO-6610] - 6610 CSO~ 1860 - 59 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000300070024-5 FOR OFrICIAL USE UNLY , ~ . ; ~ ~ UDC 621.396.98:681.322.05 j_ DIGITAL RADIO NAVIGATIONAL SYSTII4S ' _ ; Moscow TSIFROVYYE RADIONAVIGATSIONNYYE USTROYSTVA in Russian 1980 ~ signed to press 7 Sep 79 pp 2, 285-287 [Annotation and tab le of contents from book by V. V. Barashenkov, ~ A. Ye. Lutchenko, Ye. M. Skorokhodov, V. B: Smolov, G. T. Stepashkin, ; Ye. Ye.'Afanas'yev, edited by V.B. Smolov, Sovetskoye radio, 6000 copies, 288 pages] , [Text] In this book a description is presented of prospective digital - radio navigati_on devices and their roles in navigational complexes. A I study is made of the standard version of on-board equipment, automated { methods of designing it, and the problems of servicing, operating and main- ~ _ taining it. Flow charts are presented for the algorithms for processing ; the radio navigation information by computer engineering means. ~iuch ~ attention is given to integraCed microcircuits which make it possible to ; build small, economical on-board radio navigational devices with high ogerating reliability which are convenient to service. This book is designed for specialists in the development and servicing of - radio navigational devices and will b~ nseful to teachers and students of ~ the navigational departments of the tiigher institutions of learning. ! There are 12 tables, 175 figures and 110 references. ; - Contents Page I ~ ; Forewor3 3 ~ Introduction 5 i - Chapter 1. Primary Data Processing Algorithms ' 1.1. Radio navigational sysitems. Classification and , operating principles ~ ' 1.2. General problems of signal processing 20 1..3. ?�4ethods of describing signal processing algorithms 24 ~ ' 1.4. Processing the signals of pulse-phase systems 29 i 1.5. Processing the signals of phase radio navigational systems 41 ! 1.6. Principles of the digital processing of the signals ~ - from goniometric, goniometric-rangefinding and ! differential-rangefinding radio navigation~l systems 46 f 60 ~ ~ ; FOR OFFICI~,:. LtiE ONi.Y ~ ~ ~ _ ~ ~ - i i- . � ~ ~ ~ . i ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 rOR OFrICIAL USE ONLY Chapter 2. Secondary Data Processing ~ 2.1. Preparation for data reception 49 2.1.1. Steps tn processing radio navigational data 49 2.1.2. Direct and inverse geodetic problems 50 _ 2.2. Selection of a radio navigational tazget 52 2.3. Finding denumerable variables ~2 2.4. Frequency timing of the reference oscillator 55 2.5. Introduction of corrections to the measured radio - navigational parameters 55 2.6. Resolution of ambiguity of phase readings 57 2.7. Determination of the type of received signals 58 2.8. Determination of navigational variables 59 - 2.9. Estimating the reliability of radio navigational findings 68 - 2.10. Kalman-Bussey filter 69 ~ Chapter 3. Functional Units of Radio Navigational Systems 3.1. Integrated microcircuits 73 3.1.1. Basic types 73 3.1.2. Classification of digital bipolar and field transistor microcircuits 74 3.1.3. Basic parameters of integrated microcircuits 78 � 3.1.4. Triggers 79 3.1.5. Analog integrated microcircuits 87 3.2. Standard functional units of integrated microcircuit - radio navigatioaal devices 89 - 3.2.1. Counters 90 _ 3.2.2. Registers 97 3.2.3. Adders 101 3.2.4. Decoders 107 3.2.5. Coders 108 3.2.6. Pulse distributors 109 - 3.2.7. Digital phase shifters 109 3.2.8. Digital phase discriminators 113 ~ 3.2.9. Digital frequency discriminators 115 Chapter 4. Specialized Radio Navigational Modules ~ 4.1. Radio navigational system modules and channels 117 - 4.2. Structural characteristics of receivers using digital - - control techniques 121 4.3. Analog-to-digital and digital-to-analog converters of radio navigational systems 123 4.3.1. General information 123 4.3.2. Time interval-to-code converters 125 4.3.3. Code-to-voltage converters 128 4.3.4. Analog-to-digital PNK [voltage-to-code converters] 137 4.3.5. Binary quantizer 145 4.3.6. Converters of angular displacements ~ to code N 146 - 4.4. Synchronizers 146 4.5. Reference oscillators 151 4.6. Data displays 156 61 . FOR OFFICI~t;. L'SE UNLY t APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2047102108: CIA-RDP82-00850R000300070024-5 FOR OFrICIr1L U5E ONLY a Chapter 5. On-Board Computers 5.1. Structural principles of arithmetic-logical circuits 157 5.1.1. Designation and general characteristics 157 S.1`.2. Algebraic addition of fixed-point numbers 159 5.1.3. Multiplication of fixed-point numbers 162 5.1.4. Calculation of functions 164 5.2. Memories 166 5.2.1. Designation, classification, basic characteristics 166 5.2.2. Ready-access memories 167 5.2.3. Permanent memories 170 5.3. Control panels 171 5.4. Control circuits 176 5.4.1. General principles of the organization of control 176 5.4.2. Microprogram control systems 1~~ 5.4.3. Methods of writing microprograms 179 5.4.4. Microprogram control circuits 181 5.4.5. Program control principle 184 - 5.4.6. Operation execution control 186 . 5.4.7. Operation execution sequence control 193 - 5.5. Microprocessors . 196 Ch apter 6. Structural Principles of Digital Radio Navigational Devices 6.1. Classification and structural principles 198 6.2. Radio navigational data pickups and radio nav~gational indicators 201 6.3. Coordinators Z~~ 6.4. Construction o~ radio navigational devices using microprocessors 210 6.5. Structural principles of navigational complexes 212 - Chapter 7. Design Principles of On-Board Systems 7~1. Organizational and procedural design principles 224 _ 7.1.1. Organizational design principles ~24 7.1.2. Procedural design principles for specialized digital computers 226 7.2. Selection of the internal language for specialized digital computers 229 7.3. Development of structural diagram 241 7.4. Logical design 250 7,~. Use of a computer for design 255 , ;.6. Selection of the general-purpose on-board digital computer 261 Chapter 8. Problems of the Operation and Maintenance of Digital Radio Navigational Systems 8.1. Preparation for measurements 26~ 8.2. Servicing equipment when determining navigational variables 271 8.3. General information with respect to preventive maintenance and repair of digital radio navigational systems 273 62 FOR OFFICIn:, liSE UNi,Y APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 FOR OFrICIAL USF, ONLY Bibliography 2~~ Sub j ect_ index 2g1 COPYRIGHT: Izdatel'stvo "Sovetskoye radio", 1980 [52-10845] ~ 10845 - CSO: 1860 63 FOR OFFICIt~L L'SE ONI,Y APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000300070024-5 rux urrl~t~ uan unLi ~ i UDC 621.396.6.002:621.9.047 ~ ELECTROCHEMICAL PROCESSING IN THE TECHNOLOGY OF EI.~CTRONIC EQUIPMENT PRODUCTION _ - Moscow ELEKTROKHIMICHESKAYA OBRABOTKA V TEKHr10LOGII PROIZVODSTVA RADIOELEKTRONNOY _ APPARATURY in Russian 1980 signed to press 27 Jun 80 pp 1, 2, 136, 137 - jAnnotation and table of contents from book b~? Fedor Vladimirovich Sedykin, Lev Borisovich Dmitriyev, Viktor Vasil'yevich Lyub imov and Valentin Dmitriyevich Strukov, No 19 of the series "Biblioteka tekhnologa radioelektronnoy apparatury" ; (Library of the Electronic Equipment Technologist), Energiya, 4500 copies, 136 pp] i i [Annotation] The book describes electrotechnological processing methods used in ~ the production of electronic equipment. An examination is made of problems of the theory of the process, the feasibility of using electrochemical processing to make ; f ittings and printed-circuit boards, for deburring and marking, data are given on ; the use of combined electrotechnological processes, and equipment for electro- ~ chemical machining is described. For techologists and engineers in the radio and electronics industry. ~ Contents 3 PrefacE 5 , Introduction Chapter One. General Description of Electrotechnological Methods of Producing $ ~ " Electronic Equipment ; 1.1 Requirements for technological processes in production of electronic 8 ; equipment 10 ~ 1.2. Survey of inethods of electrotechnology 11 ' Electrochemical machining 11 Electroerosion machining 14 . Ultrasonic processing 16 ~ Ultrasonic cleaning 16 Ultrasonic welding 17 ~ Light-beam machining 18 Electron-beam machining 19 Combined processing methods ' _ Chapter ~ao. Theoretical and Physical Principles of Electrochemical Methods 22 of Machining Metals Chapter Three. Using Electrochemical Machining to Make Fittings for Electronic 36 Equipment ~ ~ 64 ' FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000300070024-5 - FOR OFFICIAL USE ONLY 3.1. General description of die sets, molds, and ~ethods of making them 36 3.2. Electrochemical methods of making die sets and molds 39 3.3. Technology in making die sets and molds on small interelectrode gaps 46 3.4. Electrolytes 51. 3.5. Tool electrodes 53 - Chapter Four. Combined Methods c~f Machining Parts, Electrochemical Marking and Deburring 57 4.1. Machinab ility and methods of machining cast magnets 59 4.2. Diamond electrochemical surf,ice grinding 61 - . 4.3. Diamond electrochemical internal grinding 64 - 4.4. Tools for diamond electroch~:mical grinding of magnets 67 ~ 4.5. Advantages of combined procasses of machining magnets 59 4.6. Electrochemical marking and deburring 71 Chapter Five. Making Printed-Circuit Boards by the Method of Electrochemical Machining 82 5.1: Particulars of electrochemical machining of printed-circuit boards 83 ~ 5.2. Arrangements for electrochemical niachining of printed-c ircuit boards 88 - 5.3. r[ethods of making printed-circuit boards in custom production 91 5.4. Electrochemical methods of making printec~-circuit boards in series ' and mass production 96 Chapter Six. Equipment and Facilities tor Electrochemical Machining of Apparatus 104 6.1. Makeup of electrochemical facility and major requirements to b e met by - - electrochemical equipment 104 6.2. Classification of equipment fc~r electrochemical machining 107 6.3. Machine to.ols for making the cavities of die sets and molds 107 6.4. Machine tools for deburring 123 6.5. Equipment for diamond electrochemical grinding of magnets 126 - Conclusion. Extending the Field of Application of Electrotechnologacal Method 128 Ref erences 131 C(~PYRIGHT: Izdatel'stvo "Energiya", 1980 [49~- 5b10 ] 6610 CSO: 1860 65 FOR OFrICIAL USE QNLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000300070024-5 FOR OFrICIAL USE ONLY UDC 656.254.16:621.317.2:629.114 . MOBILE COMrtLT1VICATIONS CENTER Moscow AVTOMAT~KA,TFL~MlICItANIKA I SVYAZ' in Russian No 8, 1980 pp 18-21 [Article by B, P. Rol'shchikov, chief of the communications division of the Signal and Communications Service of Odessa Road] [Text] The large-scales of introduction of new, more complex equipment have required a basic change in organization of its technical servicing. - Studying the system for servicing the communication systems at the - Poletayevskaya and Kartalinskaya ranges of the Southern Urals Road and also considering the experience in the organization of the communications KIP [control and test points] on the Gor'kiy, Moscow and other roads, the co.llectives of communications specialists of some of the stations on the Odessa Road have gone over to an industrial base for servicing the communi- cations media. At these stations independent communications repair shops - (RTTs) have been created, advanced technology has been introduced, and the equipment servicing system has been changed. The introduction of advanced servicing methods has made it possible sharply - to improve the producrivity of labor, improve the operating quality of communications equipment and aci~ieve more reliable operati.on of the devices. - The working conditions c,f the technical personnel have also been improved. The introduction of new service technology at the Odessa, Odessa- Sortirovochnaya, Pomoshnyanskaya, Nikolayevsk and other stations has made _ it possible to exclude failures of the equipment at the communication terminals of the train dispatchers, the station and ].ine-track communica- - tions. The number of cases of damage to station eQUipment, power supplies and cable communication lines has been reduced. Thus, at the Odessa- Sortirovochnaya [Odessa Shunting] station in 1979 the number of cases of - damage was reduced by 4.3 times by comparison with 1976, and at the Pomoshnyanskaya station, by 11 times in the same period. _ The creation of the communications RTTs has permitted technical servicing of the communications equipment to be converted to the centralized method. , 66 _ FOR OrFICI~~:. liSE UNLY - APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000300070024-5 FOR OFFICIAL USE ONLY Significant remoteness of the communications facilities from the large populated areas and absence of the required number of qualified specialists in the line sections have led to the necessity for organizing mobile groups i~i the communications RTTs. Such groups have been created at the Odessa~ ~ the Nikolayevsk, Pomoshnyanskaya and other stations. Mobile communications centers (PUS-LK) have been designed and built for them. The general view of a PUS-LK appears in Fig 1. ~ : : < : : : . . . . . : , . . n~e. ni';~:: , '+t~ E$:.',ir';?i�.'.� .::.i::::nni . . ' . %o~.;'2;%(i:::;~ :'a t. . a z~; ~ c ..::,:.::a.:.:.,o::;;,'; ' . b :~iiY..;,-~1v:ti.:i~ v: 1: : r .b:4:;yi.:~.:. Si ~ . ...n ....~an..... x...vi.n:.:Y^'F.'.:~i?...ni.:.'v' p1...: ~vy~:vx:::::n $>r :.:::.::.:::.::::.::.~..~..�..:~...s..:,::..:~:..... ......4~,1,,i::~: d, (24) - then the individual parts of the investigated segment make contributions in counter- - phase, and the total results drops results. For illustration of the conclusions obtained above regarding the possibil:ity of re- ~ producing the target ima~e when rec~rding the spectrum along ~ straight line, the folloWing experiment was performed. An optical system was assembled, the schematic - diagram of which appears in Figure 2. A diaphragm was located in the (x, y) plaae. It was illuminated by a penci'1 of rays converging at the point f. The .~mplitude - distribution of the light oscillations in the hole in the diaphragm Riviulated the ob~ect the function J(x, y). The light source (a helium-neon laser~ and the lenses used to ahape the converging beam are not shown in the figure. In the glane passing through the point f, the spectrum G(u, v) w~as formed. If a lens L was placed - on the path of the rays, an image of the target was obtained in the X, Y plan~. - x,~y ~ u,v X,Y - ! _ " f J( ) -S(LL v) ~ - ~ ' I J ~ S`y) - x,y ~ 7 x,~ , Figure 2. System for optical simulation of the recording and repro- - duction of an image by the frequency scanning method. Iiowever, if a f ilter with pass band ~16) was placed in the u, v plane, also, then light distributtion proportir~nal to s(x) was obtained in the X, Y plane. A slit located located along the u axis was used as the filter. Its width was about 4 microns. By using an additional diaphragm at the slit, the central part ~u~ < ul and continuations ~u~ > u2 were covered, creatin.g the expression uo u? u~ U = 8. _ uz-u~ _ - 99 ~ $OR OFFICIAI, USE ~NLX - APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 ~ ~~a ~ � 1 � ~ . � . . ,N~ ~ 9 I~ - ' ~I ~f i ~ ; `~~r ~ = � : j ~ t; ui'' i ~ r i~ , . ~ i ~ ~ I I +11 . ~i � ~ ~ ~ - _ ~ ~1 5) , . ~ ' ~ ~ . ~ 2) - a) b) c) d) - = Figure 3. The upper row is a photograph of the target; the midd].e row is the photographs of the same targets obtained on simulation of the ' - frequency scanning method with two antennas; the lower r~w is the re- � sult of photometric measurement of the negative images of the middle row. F-~gure 3 shows photographs of targets obtained without and with a f ilter. On the ~ photographs with a filter (the mi~idle row) the sides of the targets parallel to the x-axis were not represented. This coincides completely ~aith the theoretical conclu- ` sions. The sides perpendicular tc thE x-axis were transmitted the most intensely. . The illumination distribution in their i.mage is proportional to P2(x). The function (21) explains the appearance of fine structure with a period d and the course of the envelope in the image. In the image of the figure with the step (photograph b) the intensity is appreciably less in the transmission of the short vertical segments than in tr~e transmission ef - the long one. This is connected with the fact that when representing the vertical - segments the illumination must be proportional to the square of theiL length. The sloping side of the trapezoid was not represented in photograph c. The reason was the following. Considering the photograph, it is possi},le to see that the pro- - iection of the sloping side on the x-~is contains several periods of f ine structure d, that is, the inequality (24) exists and, as a consequence, there is a stY-~ng drop in illumination which is intensif ied by the nonlinearity of the photographic pro- . cess. _ , 100 FOR OFFICIAL USE ONLy APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000300074424-5 . FOR OFFICIAL USE ONLY In photograph d the image of the art cf a circle ~s attenuated signific~ntly. Only - the segment close to the vertical tangnet for which inequality (23) is sati~fied . was actually depicted. _ If smooth variations are characteristic for the function J(x, y), then by the output signal s(x) the corresponding target will be equivalent to the target with sharp ' varfation of J(x, y), buC with curvilinear outline. ~ In conclusion let us note ttxat when observing targets of simple shage which is a priori known, the described setup permits determination of the overall dimensions of Lhe target just as during spatial synthesis of the aperture along one straight line. The advantage of the radiovision system with frequency scanning is speed and absence of complex devices for mechanical movement of the antennas. More complete infor- mation about the target can be obtained as a result of complicating the system: - either increasing the number of antennas or rotating one antenna aiound the other. - BIBLIOGRAPHY 1. E. I. Gel'f er, Yu. V. Lebskiy, S. Ye. Finkel'shteyn, N. A. Yakun', IZV. VUZOV ` RADIOFIZIKA (News of the Institutions of Higher Learni.ng Radiophysi~s), Vol _ 19, No 10, 1976, p 1512. - 2. E. I. Gel'f er, S. N. Mensov, RADIOTEKH2dIKA I EL~KTRONIKA (Radio Eng~.neering and Electranics), Vo1 22, No S, 1977, p 914. 3. A. A. Pistol'kors, RADIOTE;~iIvIKA I ELE:CTRONIKA, Vol 11, No 10, 1966. 4. A. P. Reutcv, B. A. Mikhaylov, G. S. Kondratenkov, B. V. Boyko, RADiOLOKATSIOid- NYYE STANTSII BOKOVOGO OBZORA (Side-Looking Radar), Moscow, Sov. ra,dio, 1970. j 5. V. A. Zverev, RADIOOPTIKA (Radiooptics), Moscow, Sov. radio, 1975. I 6. E. I. Gel'f er, V. A. Zverev, S. Ye. Finkel'steyn, TEZISY II VSESOYUZNOGO SIMPO- . ZIUMA PO MILLIMETR04'YM I SUBMILLIMETROVYM VOLNAM (All-Union Symposium on Milli- _ meter and Submillimeter Waves), Khar'kov, No 2, 1978, p 210. 7. G. Berbekar, S. Tokes, ULTRASONICS, Vol 16, No 6, 1978. 8. A. Michelson, F. G. Pease, ASTROPHYS. J., iVo 53, 1921, p 249. 9. N. A. Yesepkina, D. V. Korol'kov, Yu. N. Pariyskiy, RADIOTELESKOPY I RA.DIOMETRY (Radiotelescopes and Radiometers), Moscow, Nauka, 1973. - COPYRIGHT: "Izvestiya vysshikh uchebnykh zavedeniy","Ra.diof izika", 1980 [38-10845] ~ 10845 - CSO: 1860 FND 101 APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000300070024-5
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