JPRS ID: 9240 USSR REPORT ELECTRONICS AND ELECTRICAL ENGINEERING

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• Content Type: REPORTS

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E~t~: ~ E _ ~ ~
RU~U~T ~ F~U~ ~ ~F ~

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JPRS L/~240
- 7 Auc~ust 1980 _
' ' -
~JSSR Re ort
p
ELECTRONICS AND ELECTRICAL ENGINEERING
- (FJUO 13/80)
i -
- FB~~ FOREIGN BROADCAST INFORMATION SERVICE _
~ FOR OFFICIAL USE ONLY -
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~
~
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~ JPRS L/9240
7 August 1980
~
_ USSR REPORT
ELEC?ROMICS AND ELECTRICAL ENGINEERING
(FOUO 13/80 )
CONTENTS _
ANTENNAS
M::thod for Calibrating Load Resistors of Two-Dimensional
- Periodic Structures 1
COMMIJNICATIONS, COMMUNICATION EQUIPMENT, RECEIVERS AND TRANSMITTERS,
NETWORKS, RADIO PHYSICS, DATA TRANSMISSION AND PROCESSING, INFORMA-
TION THEORY .
5
Data Transmission Via a Telephone Exchange Network 6
Some Problems of Telephone Network Control 13
Digital Transmission System Signals and Codes 22 -
Digital Coupling Devices (Transmultiplexers) in Co~unications
Systems 33
The Service Quality of Automatic Long Distance Telephone
Service 44
CONVERTERS, INVERTERS, TRANSDUCERS ~
Broad-Band Matching of Piezotransducers of Acousto-Optical ~
Devices 50
- INSTRUMEN~S, MEASURING DEVICES AN1) TESTERS, METHODS OF MEASURING, -
GENERAL EXPERIMENTAL TECHI~?IQUES -
Optical Heterodyne Method for Study�ing Surface Acoustic
_ Waves 55
PUBLICATIONS, INCLUDING COLLECTIONS OF ABSTRACTS
, Abstracts of Papers on Dynamic Process and Signal Identification
and Recognition 59
' a" LIII - US5R - 21E S&T FOUO]
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L'VA Vl'1'L1i121L UJL' V1YL1
Abstracts of Papers on Electromlgnetic Wave and Signal _
Conversion and Transmission 63
_ Control in Microelectronic Technology 71
- Laser Beams, Collection of Articles Announced 74
Lines of Communications 77
Production Technology for Microelectronic Devices 86
~ Scientific Articles on Antennas 92
Small Signal Modulators ..........e 94
Space-Time Processing of Signals, Collection of Articles
. Announced 96
- QUANTUM ELECTRONICS
Calculation of Angular Characteristics of Lasers With
Unstable Resonators 99
- b -
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,
ANTENNAS
= UDC 621.396.676
METHOD FOR CALIBRATING LOAD RESISTORS OF Z'WO-DIMENSIONAL PERIODIC STRUCTURES
Kiev, IZVESTIYA VUZ SSSR-RADIOELEKTRONIRA in Russian No 3, 1980 pp 90-93
[Article by 0. N. Tereshin, V. A. Konskiy, and V. I. Kornyukhin, submitted
- 26 ~'eb 1979 ]
[Text] At the present time, two-dimensional periodic loaded structures [1] -
are beginning to be used widely in the synthesis of low Q-factor antennas
= working in the leaky wave mode [2]. Such antennas continuously trans~orm
' the feed wave along the antenna into the radiaCed electromagnetic wave.
- They can be constructed, for example, on the basis of a stripline one of whos~
plates goes into a two-dimentional periodic loaded structure or on the basis
of a coaxial line whose external braiding also goes into a two-dimensional
periodic cylindrical loaded structure. The reactive Ioad resistors of two-
dimensional periodic structures played a role of couplers between the radi-
ating slots and the feed wave. The main parameters of the antenna, such as
the constancy of the input resistance and the directional diagram in the
operating frequency band, depend considerably on the degree of couping be- -
tween the radiating elements and the feed wave. Therefore, the accuracy of
- the realization of the calculated values of load resistors must be sufficient-
, ly high. -
Unf ortunately, the existing measuring equipm~2nt makes it impossible to mea-
sure the reactive loads (capacitance and inductance realized, for example, _
_ on the basis of segments of a two-wire line) in the microwave--band with a
- high degree of accuracy.
r
- This article describes a method for measuring reactive loads in the microwave -
band which makes it possibl~ to achieve a sufficiently high degree'of accu- -
- racy.
' A plane homogeneous electromagnetic wave propagating along the axix z falls
' onto a two-dimensional periodic loaded structure situated in the plane (x,y)
which is characterized by the periods T, T1, and the value of the loa3 ~esis-
tance Z H(Figure 1). It is assumed that there is no variations of the field
and load values along x. For this case, with the structure of TEM-waves in ~
half-spaces I(z~ 0) and II (z < 0), there exist two components of the elPC-
tromagnetic field [3J:
1
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r~~K Ur'P'1(:lAL U5~ UNLY
~ aHz ~
.
Hx' v--~e dz
(1) (2~ _
1, ~noa to~P IrE,> > T
D _
_ ~ ~ T ~-a-
y
- T - - -
' ~~n..
+ /j~Q(Lr ~l (E2) � Xc.~~ -
:i )
3
Figure 1. Two-Dimensional Periodic Loaded Structure -
Key: 1. Incident
2. Ref lectEd
3. Transmitted
Figure 2. Stripline Used in Calibration: 1-- two-dimensional ~
periodic structure; 2-- hi~h-frequency connectcr; -
- 3-- metal plates; 4-- dielectric bushings
: Figure 3. Two-Dimensional Periodic Structure with Capacitive
Loads Realized on the Basis of Open Segments of a
Two-Wire Line
_ With consideration of the above assumptions, the field of the incident elec- _
tromagnetic wave can be written in the foZlowing form:
k -
HsnaA = Aoeikz~ Eyne,q - (UE �9p2tkz~
where Ao amplitude coefficient of the incident wave; k='? i"/~1, wave
number.
The plane homogeneous electromagnetic wave falling on the two-dimensional
- periodic loaded structure partially reflects from the stru~ture and partially
passes through it. ~
_ Tht~~, the resulting elec~romagnetic field in the I half-space can be ~ri.tte~~
in the following form:
(1'> rk: -rkZ.
Hxl - HxnaA. + Hxorp - Aoe -E- Ale .
k ~Aoetkz _ Ale ~kz~~ (1) =
E~i ~ WEl
Key: 1. Incident ~
2. Reflected
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- where A1 amplitude coefficient of the reflected waves; ~1 dielectric
permeability of the medium in I half-space, and in II ~half-space:
~2)
Key: 1. Transmitted
~ where B-- amplitude coefficient of the transm~ltted wave; ~ 2-- dielectric .
permeability of the medium in II half-space.
Accor3ing to [1], on the surface of the location of a two-dimensional per- ~
iodic loaded structure the following boundary conditions must be fulfilled
for z = 0: -
~ 1~ rk:, k rru -
_ Hx2 = Hx�pom, = Be Eu~ - c~e~ Be , (3> _
_ _
E~,~ = E~,
z=0 za0
T E~a~o ~4~ -
ZN = - .
T~ Hat - Hx2
z~0 z=0
With consideration of (1) and (2) the conditions (3) and (4) ~ill, respec-
, tively, assume the following f orm;
e
A1= ,go ei g~ ~ 5 )
T ~
- Z~ T1~g2Ao-B(1-{- e~ I ~6~ _
~ ~
where W2 = k/GJ E 2-- wave resistance of the medium of II half-space.
Assuming that the loads are purely reactive Z H = iX H and ~1 2 e
and using (S) and (6), we obtain an expression for the reflection coefficient -
_ in the form of
A1 1
, I' = A 3 q.l ,
� 1 2iXg ` ( 7 )
where Xx =XLI~; W= k/we wave resistance of the medium. '
The modulus and the phase of the reflection coefficient can be determined
from (7) by the formulas: ;
3
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L'vl\ Vl'1'1V1[iL UJG Vl`ILL
1
Irl=l T~
z~
Y 1~-(2X"-T-~ ~8)
3
I , T' 1
- ~=arctgl--2Xd T (9)
~
The obtained calculated relations (8) and (9) makc~ it possible to determine -
the value of the reactive resistance flf the loads Z~ measu ed �f the two-
_ dimensional periodic structure by the measured values of t~ie modulus and
phase of the reflection coefficient.
_ For measuring the modulus and the phase of the refle~tion coefficient, it is
possible to use a strip~:~ne matched with a feeding coaxial cable. The two-
_ dimensional periodic loacled structure whose value of the reactive resistances
of the loads has to be measured is placed between the plates of the strip-
line perpendicular to the direction of the propagation of the elec~romagnetic
wave of the stripline (Figure 2). This makes it possible to measure the
modulus and the phase of the reflecCion coefficient with a high degree of -
accuracy by the known methods [4, 5].
The method described above was used in developing models of antennas discus-
~ sed in [2], which made it possible to improve substantially the electrical _
parameters of the antennas; bringing them close to the calculated values.
Reactive loads of the antenna m~dels were designed on the basis of segments
of a two-wire line. _
~
A two-dimensional reriodic structure with capacitive loads achieved on the
, basis of open segments of a two-wire line is shown in Figure 3. The length _
J of the wire segments, the distance between them, and the diameter of the
wire were selected on the basis of the following formula [6]:
X~~ = 2 arcctg ( ~ft ~
Z t'~
_ . Key: 1. Zload ` -
- 2� Wlength
where X~~ length o~ the open. segment of the two-wire line equivalent to ~
_ the prescribed capacitive load ZH=_~~~~;;~, calculated wave lcngth: ~
~ ik~An=276}'�/e1gD/r wave resistance of the two-wire line; D-- di~tance
between wires: r-- wire radius.
In the process of the calihration of X~~, D, and r were changing until tY~e _
value of the load resistance Z~ measured determined by the proposed methc.:
reached the required calculated value z H .
4
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Bibliography
1. Tereshin, 0. N., and Azoyan, R. S. "Generalized Boundary Canditions of
the Impedance Type for Two-Dimensi~nal Periodic Loaded Stri~line S~ruc-
tures," RADIOTEKHTTIKA (Radio Engineering], 1976, 3~; No 1� p 36.
2. Tereshin, 0. N.; Yuvko, A. N.; and Borovik, N. B. "Cal~.ulation of the
Characteristics of Antennas in the Form of Loaded. Curtains with a Twr~-
= Dimensional Periodicity Suspended Low Above the Ground," R,ADIOTERHNIKA,
1978, 33, N~ 9, p 57.
3. Ayzenberg, G. Z.; Yampol'skiy, V. G.; and Tereshin, 0. N. "Antenny UKV"
~ [Ultrashort-Wave Antennas], Moscow, Svyaz', 1977. -
4. Fradin, A. Z., and Ryzhkov, Ye. Vo "Izmc~reniye parametrov antenno-fi3er-
nykh ustroyst~~" [Measurement of the Para+.neters of Antenna-F,eeder De�rices1,
Moscow, Svyaz', 1972.
~
5. Lebedev, I. V. "Tekhnika i pribory CVCh" [Micro~aaue~Equipment
and Instruments], Moscow, Vysshaya Shkola, 1970.
6. Ayzenberg, G. Z. 14Antenny dlya magistral'nykh korotkovolnovykh radic- -
svyazey" [Antennas for Shortwave Main Radio Communication Lines], Moscflw,
Svyaz', 1948.
COPYRIGHT: "Izvestiya vuzov SSSR - Radioelektronika," 1980
[252-I0,233] ,
- 10,233 ~
- CSO: 1860
5 ~ . _
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COMMUNICATIONS, COMMUNICATION EQUIPMENT, RECEIVERS AND ~
TRANSMITTERS, NETWORKS, RADIO PHYS?CS, DATA TRANSMISSION
AND PROCESSING, INFORMATION THEORY
~ UDC 621.391.7
DATA TRANSMISSION VTA A TELEPHONE EXCHANGE NETW~RK
Moscow ELEKTROSVYAZ' in Russian No 1, 1980 pp 25-27 manuscript received
29 Jun 79
[Article by V.O. Shvartsman and V.G. Os3pov]
[Text] The ever increasing demand for data transmission (PD) is leading
to the necess3ty of using the most branched co~nunicafiions network for this
purpose: the general service telephone exchange network (TF-OP). The fast
- rates of growth of automation in~the long distance portion of the network
are making data transmission available between prac~ica~,l~y any points in
the nation.
Desp~.te the development of specialized data transmission networks, usually
no less than 50 ~0 55 percent of data transm~ss~.on subscribers make use of _
the switched TF-OP network. However, in tAe organ~.zati:on of data transmis-
sion via the TF-OP network, it is necessary to take into account the fact
that its characteristics do not meet a11 of the requirements of data trans-
mission subscribers, while data transmission, in turn, can theorezically
- prove to have an undesirable impact on th~ operational quality of the tele-
phone network.
The characteristics of the TF-OP ne~work. S~nce in thP design of this net-
work, it was not intended for data transmission, some characteristics of =
the TF-OP network (the nozuniformity of the amplitude-frequency response
and the group delay time short-term interruption, pulse intzrference,
etc.), which do not exert a marked influence on the quality of speech
transmiss~on, considerably degrade the fideli;:y of data transmissic~a.
- The reduction in accuracy is primarily due to interference arising in t1e `
electromechanical equipment of municipai ATS~s [au~omatic telephone
exchanges], and its 1eve1 depends on the tyg~ of :;iS [2, 3~: in crossha:
exchanges, the error fact~r runs on the order of 2~ 10"S; in computer =
exchanges it is 5� 10-5; and in 10-step exchanges, it runs up to -
2� 10-2. The load on an ATS likewise has an impact on transmission
accuracy. T.hus, even 10-step exchanges in a_.light load period (for _
example, at night) provide a fidelity 2~to 3 orders of magnitude better
titari ix1 ~I~e peak loa.d. Long distance calls usually have enormously better _
- 6 -
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_ indicators with respect to fidel~,ty (by one ~o two orders of magnitude). _
The introductxon of crossbar and quasi-elecrronic, and thereafter even
electronic ATS's and MTS's [long distance telephone excfianges] wi11
promote a s~gn~`ficant increase in the quality of data transmission via
a TF--OP network.
When data is transmitted via a TF'-OP network, the discrete data signals
are converted as a result of the modulation into voice frequency signals,
while back conversion is realized for the recept~on. Because of the
nearness or equality of tRe frequencies far telephone signalingland the
characteristic frequencies of the most ~rSdespread modems (modulators-
- demodula~ors), it is possible for the data signals to im~tate the
telephone signaling, as a result of which, a connection can be broken. _
~hus, two of the four characteristic frequencies (980, 1,180, 1,650
_ a~nd 1,850 Hz) of a modem, operating at a rate of 200 bit/sec, are close
_ to the frequenc3es of the dual frequency teleph~~e signaling system
(~.,200 and 1,600 Hz), while one of the characterist~c modem frequencies '
at 1,200 bit/sec (2,100 Hz) matches the #requenc}r of tfle s~ngle frequency
signaling system.
Al1 of the difficulties mentioned here in the utilization r~f a TF-OP -
7qetwoxk for data transm~s~s~;on can be completely overcome [3]. One of the
Ways of boosfiing transmission fidel~Cy up to the requisite 1eve1 (an -
error �actor of ICerr < 10-6) is t~ie use of error protection devices (UZO),
- based on the method of resolving feedback in con~unction witfl an error _
detecti,ng code.
The danger of data signals simulating the telephone signal3ng currents _
can be elim3nated by means of limiting the transmission time for signals
of one polarity (and correspondingly, one f~requency) to such short values
that the teleghone signaling equipment does not have time to actuate. Th3.s _
limiting is usually achieved either by the use Qf a specially chosen
~axxect~hg code which does not have code combinations incorporated in it
which consist of continuous zeros or ones, or by using a scrambler. The
latter converts the signal being transm~tted to a quasirrandom sequence, -
- a characteristic distinction of which is the 1ow probability of the ,
appearance o~ long sequences of one polarity, something practically
_ precludes the possibility of telephone signaling equipment actuating from
- da~a signals. ~
' Until recently, the data transmission rate via a TF-OP network did not
- exceed 1,200 bit/seco Success in the sophisticat3on of modems and -
adaptive correction devices have recently made it possible to go over to
- hi;ghex rates: 2,400 and 4,800 Bit~sec. The cRaracteristi;cs o~ sach
- ~tod.e~s have already been standard3.zed by.the CCTT~. Tests of 2,400
- and 4,800 bit/sec modems on a TF-OP network, which were performed by the
- TsNTTS [Central S~ientific Research Institute for Communications] and the
KONTIS [Kiev Branch of the Central Scientific Research Tnstitute for
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- Communications] in 1974, showed that the value of the error factor is _
p~actically the same when operating at speeds of both 1,200 bit/sec and
- 2,,400 bit.sec. When operating at a speed of 4,800 bi.t/sec, despite the
increase in the error factor (by 4 to 6 times), the uCilizatioii of a _
` TF-OP network is justified at the present t3me since thYs increase can _
easi7.y be compensated by using error protection devfices in the data -
transmi,ssion equipment (APD). Modern APD makes it possible to aesure a =
transmission accuracy of no less than 7.0-6 on a TF-OP network.
Thus, one can argue that the specific featur~s and poor characteristics -
of the TF-OP network for data transmission, when the appropriate
termi.ztal equipment is present, are not an obstacle to data transmission
at rather high speeds via the PF-OP network. -
The impact vf data transmission on the characte2~istics of an TF-OP
netzaork. This problem involv~s two aspects. One of them consists 3.n '
the influence of the additional load (the data transmissi.on) on the _
_ quality of service to telephone subscribers of a TF-OP network, while
the other consists in the possibility of the degradation of the operational
quality of the system due to the ~ncreased output power of the terminal -
data transmission equipment as compared ~o a telephone set. Tt is not
difficult to convince oneself that these dangers are without any serious
bases.
The number of data transmission subscribers is many times less than the
r~umber o~ telephone subscribers. Thus, for example, based on data from ~
the U.S. (the nation which makes the greatest use of data transmission),
the ratio of the number of APD's to the capacity of the T'F-OP network is
so sma7.~. that even in the future it wi11 am~unt to only units of percent
_ [Z, 4]. The relative number of data transmission sets is even less in
Western Europe and Japan, where it is not planned that they tiri1l nun~ber
= more than one percent. Such a low relative nuinber o~ data transmission
subscribers attest to the theoretical impossibility of a negative impact
of data transmission on tfie operation of a TF-OP network, even in those
cases where the parameters of the~data load do not meet the norms adopted
in this network.
Hawever, the data transmission load pardmeters do not basically differ
,from the corresponding characteristics of tYi~ telephone 1oad. Thus, the
data signal 1eve1 at the input to data transmission equipment in.~~-'~ed
in a Tr--OP network is set at SO or 32 uW 0 for va~ious typas ~f equipment.
_ A power of 50~�W 0 somewhat exceeds that level at ~:,hich the channels can
be use3 j,rithout limitations. At the sarne tim~, ~overloading t;~e tians-
mission systems of the TF-OP network with data s3gnals is practically
i.mpossible because of the miniscule probabilit;J of signals from two or -
. more data transmission sets gett3ng into one channel generating system,
because of the small number of them. Also to be taken ir,to account is -
_ che fact that a power of 50 UW
0 is characteristic of data transmission -
equipment produced in earlier years. The new terminal equipment developed =
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_ after 1?anuary, 1974 in accordance with OST 4. G0. 208. 004, should
operate w~th a 1eve1 0~ 32 uW 0, sotnething witfich generally eliminates
_ the question of limitations in the use of transm~ssion system channels R
J~ ~or data tra~nsm~ss~on. _
As far as the que.sL3on of the load on subscriber lines is concerned, it
- ~ w~7,~ known that low data volumes are characterist3.c o~ the over-
_ khe],ming portion of data transmission subscribers: on the order of 10,000 -
- chaxacte~s per 24 hours and 1ess. Such a volume even for a transmission
rate of 1, 200 bit/sec 100 r.har/sec) car. be ~ransm~tted ~n 100 sec. _
Gonsidering the fact that data exchange is usually accomplished twa to `
~ three times a day, the dura~ion of one data transmi,ssion session amounts
to tens of seconds, and taking into account the service telephone convers- -
ations, the length of a session obviously �hould not exceed units of -
_ minutes (hundre~ths of an Erlang), 3,.e., the duration of one telephone -
conversation. However, the utilization of lower transm~,ssion rates
(200 bit/sec and below) is not desirable, s3nce the prerequisites for a -
marked a.ncrease in the load can be created. Transmission rates of 600
bit/sec and above are recornmended. The possibility o~ utiliz~ng rather
~1~gh data transmiss3on rates on a TF-OP network makes it poss3ble to
_ reduce the load on the network. For data transm~^ss~on at 1ow rates, it
is expedient to use the PD-200 network which has been created.
- The conclusion concerning th~ 1ow data transmission load which has been
dxawn here applies to systems wi,th so called batch transmissibn, where
' the information is generated 3n the forru of one dafia P:~1e ("packet"),
following the transmission of which, the communications session is
terminated. Packet transmission is characteristic of planning, statis- _
ti.ca~, reporting and other kinds of data transmitted in a relative time
scale. A1o;lg with such systems, interactive data transmissi.on systems
axe finding application, which provide for 3nterac.tion in real time
. between man and computer or camputer and computer. -
- Tncluded among such systems are some queuing systems (reference services,
- ticket ordering systems, systems for the solution df various problems
on remote computers, etc.). The interact3.ve mode includes pauses, during
which Che results are e$ti_mated, the situation is thought out, etc. The
pauses lead to an increase in the overall length of a data transmission
session, because of which, it is possible in some cases for interactive
~ data transmission systems to have a negative impact on the operation of
a TF-OP network. For this reason, the interactive transmission mode L`
basically requires the construction of specialized data transm~ssion
- networks. -
The specific features of the data load presented here raise the question
of monitor3ng the power of data signals and t?~e length of time a sub- ~
- scriber line is busy. However, because of the small number of data
~ transmission subsclibers and the absolutely insignificant differences
between the major paramecers of data and telephone loads, it is not
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expedient to organize systemati,c monitoring of the parameters. Exceed-
~ ing the establ~shed duration of subscri.ber line occupan~y~in the peak
. load hour (an average of 0.1 Er1~,. the max~Cnum permiss~ble mode is 0.15 =
Erl) is not a real Fossibility because of tite 1ow data volumes charac- .
~eristic of data transmission subscribers, while operation a~ an elevated -
J,eve2 is improbable in pract3.ce because of the ex~stencE oP the pracCice
of placing a lead seal on the output signal level regulator. Nonetheless,
it is useful to organize selettive monitor~ng of the transmit level. Such
IIionitoring, wt~ich it is obviously expedienL to accompl3sh ~manuallp, w3.11
provide an adequate guarantee of protection o~ fihe telephone exchange
_ network against any negative influences.
The advantages o f the use o f a TF-OP ne�~work for data transrrtission. The
TF-OP network makes it possible to design not only~data transmission -
systems access~.ble to a wide group of users, but also maximallp si.mplified
systems. Such systems, usually designed for the transmission of 1ow data
volumes, can be built on t.he bas3s of mult3frequency keyboard telephone
- sets, which, besides their main function, play the part of an extremeiy
- simple data transmission set. Data transmiss~on is accamplished by
punching the buttons on tlze telephone set keyboard following the establish-
ing of the ca11 connection, and data reception ~ws ac.camplished at the .
computer center using a modem which received multifrequency signals from
push-button telephone sets.
, In some cases, data transmission can be accomplished in practice only
by us~,ng the accessible and widely branched TF-0P network: for example, -
in the public service ~ for the remote monitoring of the status of non-
_ tx~nspoxfiab~,e seriously i11 pat~.ents by means of a computer or for the
transmission ofcardiogramsfrom the apartment of the sick person to the -
cardiol~gical center for analysis; in the sphere of everyday life - for
~ the cashless payment for electrical power, gas, etc.
- The utilization of a TF-OP network for data transmission is being stimu-
- ~,at~d by~ its universal nature: the transmission of the most diverse -
infoxmat~on i:s poss3;b2e via this network (speech, data, facsimile signals).
_ Considering the fact that managing the national economy, as a rule,
requires the organization of a11 kinds of communications (or at least,
_ telephone and data transmission), the orientation towards the telephone _
= network proves a natural one.
Data transmission via the TF-OP network in our c_~u.itry is regulated by
~ the "it~gulations on the Conditions for the iJt~1w:.ation of th~ Switched
Telephone NEtwork for Data Transmission". The bas~c stipulaticns of this =
document, which opens up broad prospects for data transmission user.s.
- cons~,st in the following:�data can be transmitted without limitations
at any time of the day; the average load on a subscriber line should not
~ exceed 0.1 Er1 ~n the peak load hours, and the ma~imal load should not
exceed 0.15 Erl; the average data signal power at the input to the
_ 7.0
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closest transmission system should not exceed 32 pW 0(for terminal data ~
, transmission equipment developed prior to 3'anuary, 1974, a 1eve1 of
SO uW 0 is permitted); the data transmiss3.on rate, as a ru1e, should be
no lower than 600 bit/sec: the maximum permissible rate 3s established at ~
4,800 bit/sec; th.e type of terminal set connected to the TF-OP network -
_ shou]_d be included i.n the products 13;st approved by the USSR Ministry
of Communications; complaints concern~ng data transmiss.~.on quali.ty dur~ng
the normal course of a telephone conversat~Lon are not accepted by tfle
communications organs.
The area of TF-OP network utilization is an extremely wide one, however,
_ it is far from unlimited. Tt is apparent that this network cannot be
used 3.n cases where: the load generated by a data transmission subscriber
exceeds the intrinsic level for telephone subscribers; data ~ransmission -
subscribers need specific services not provided by the Tg-OP network (for
example, multi-address commun~cations); the network does not prov3de a
subscriber with the requisite operat~onal mode in tAe needed directions
- (for example, automatic dialing oz a long distance ca11); the t3me making ,
a call connection or the network reliab~lity~do nofi satisfy the subscriber
- requirements.
There is no automatic identification of the called subscriber in the
- TF-OP network, since it is accompl3shed by the subscribers themselves in
- telephone communications. For this reason, when exchanging data via the
TF-OP network, it is necessary at the start o~ a sess~on to make sure
that the connection has been correctly establ~.shed. This precludes the
possibility of sending data to the wrong address. Tfi should also be kept
ia: mind that the use of radio relay and satellite communications links
in the TF-OP network places we11 known limitat~tons on the possibility of
= using the TF-OP networ'K for data transmissiono
ConeZusion. The capacity of the TF-OP network has substantially increased -
over recent years and the 1eve1 of long distance automation is growing at
- a~ast pace. The quality indicators of the network are being improved ~
through the introduction of increasingly ref3ned equipment. Tn the future
is the saturation of the network with equipment, the design principle of
- which is based on digital trar~smission and switching methods. Such
equipment provides for high quality characteri.stics, something which is
especially important for data transmission. However, even a digital
switched telephone network does r~ot eli,mi,nate the need of des~,gning
specialized data transmission ne~works, s~nce tli~ zequ~rements o~ many
' data transmission subscribers as regards a numBer of netWOrk parameters -
(signaling, services, switching methods, etc.) can be specific, and more-
over, change rather rapidly, while the requirements of telephone sub-
scribers have primarily remained the same.
11
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- Considering the comparatively~ sma11 number of data transm3ssion sub-
scribers it is not expedient to extend these requirements to the entire
telephone networ~C. fhe most efficient approach to the development of
data transmission technology is the design of spec3alized data trans-
mission networks in con~unction with the use of ~he TF-OP network for
data transmission, taking into account the 1~n~tations witich follow from
the specific features of this network.
- BIBLIOGRAPHY r
l. "Ekspress~informatsiya. Zaruhezhnaya tekhnika svyaz~F' j"Express Tnfor-
mation. Foreign Co~unications Engineering~'], 1975, No 23.
2. Morev, V.L., Nakhimovich, I.T., '~Tssiedovaniye dostovernosti peredachi
diskretnoy infurmatsii na gorodskom uchastke mezhdugorodnogo soyedinen-
iya" ["A Study of the Transmission Conf~dence Zeve1 of Discrete Infor- -
mation on a Municipal Section of a Long Distance Line"], in the collec-
tion, TRUDY LF TsNTTS [PROCEEDTNGS 0~' THE LENTNGRAD BRANCH OF THE CENT-
RAL SCIENTTFIC RESEARCH TNSTTTUTE 1~OR COMMUNTCATZONS], 1969, No 21.
3. Pugach, A.B., Tumanovich, V.N., Chexnobyl�skiy, B.M., "Problemy pere-
dachi dannykh po seti kammutiruyemykh telefonn}*kh kanalovF' ["Problems
of Data Transmission via a Network of Switched Telephone Channels"],
' in the collection, TRUDY KONTrS j~ROCEEDI'NGS OF THE KTEV BRANCH OF THE
CENTRAL SCTENTTFTC RESEARCH TNSTTTUTE gOR COMM[1N~".CATTONS], 1976, No 6,
4. "The World~s Telephones. A Stat~Lst~cal Compilation as of January 1,
1976-1977", ATT Long Lines.
5. Shvartsman, V.O., "Tekhnicheskiy progress v oblasti peredachi dannykh"
["Engineering Progress ~.n the Fie1d of Data TransmissionF'], ELEKTROSVYAZ
ELEKTROSVYAZ' jELECTRTCAL COMMUNTCATTONS], 1978, No 6. -
COPXRTGHT: Tzdatel~st~~o "Svyaz~," "Elektrosvyaz'," 1980.
[1239-8225] -
8225
: CSO; 8344 /1239
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UDC 621.391+519.872(031) -
_ SOME PR~BLEMS OF TELEPHONE NETWpRK CONTROL -
- Moscow ELEK~ROSVYAZ' in Russian No 1, Jan 80 pp 21-24 manuscript received ~
5 Apr 78 -
[Article by M.A. Shneps)
[Text] Tncreased demands are placed on the theoretical basis far the
carrying capacity of a communications network and on the substantiation
of the standards set for com_munications qual~t}r because of the need for
the large capa^ta1 investments in tRe Unified Automated Commun~cations
Network [1]. This confronts telepfione network des~gners with problems,
for the solut3on of which tRere ~s unfortunatel}r.st~11 no adequate
_ theoretical basis.
Many problems in telephone traffic theorl: are aolved without sufficiently
taking into account the actual operating conditions of a telephone network.
Specifically: the capacity of the trunk group of cha.nnels ~s computed
, from Erlangfs first formula, which does not take into account repeat
attempts made by the calling subscriber with. the.blocking of the
_ next attempt to make a connect~on w~th the called sgbscriber; rel3ability -
_ indicatars are not refiected in the calculations of the carry~i,ng capacity
of the fletwork, or in the standards set for losses; when planning bypass
routes,~the fact that the utilization of them increases the carrying
capaci;ty of a network only 3n the nonoverloaded state of the network or
_ with overloads (failures) of individual trunk groups is not taken into
account.
However, the elimination of the difi�~.cult~es enwnerated above on an
- individual basis does not answer a11 of the quest~ons wh3,ch a~i,se in the
de~ig~t of a network, especially those rel3ted to network control in over-
7.oad modes. A general approach to the solution. of telephone network
coz~txol problems as a whole is presented�in this paper, including the
calculation of the carrying capacity o# the sw~tchit~~ equ~pment, the ~
~ control devices, aad considerations for the setting oz 1os~ standards and
rel3ability ind3cators are given, where these considerations are based on
economic calculations.
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An appr~oximate ne~twork design method. We sha11 begin with a simple example _
which illustrates the complexity of the prob7.ems which come up in network _
desi~n. We sha11 consider a fragment of a channel sw~:fiching network (Fig-
ure 1). Communications are establ~sRed between the calling subscriber A
and the called subscribei B through four
Stat~on 1 Stat~.on 4 switching stations, each of which has its
- .Y~en 1 y~e~ ~ own switching circuit, KS, and controller,
W. We shal~ assume that the subscriber is -
,a NC � K~ g a=persistent, i.e., following an unsuccess-
fu~. attempt to make a ca11, the subscriber
yy yy repeats the call with a probability a af-
- C21:~ ter a random time, and gives up on trans-
� mitting the message (the conversat~on) with
Figure 1. a probability of 1-- a. Tf a= 1, then
Key: 1. KS [switching circuit]; the subscriber 3s termed absolutely persis-
2. W [controller] tent.
We shall introduce the rest of the symbols: m is the number of traff ic
stations on the call connection path; q and na are the probabil::_ies
~ that the attempt wi11 be blocked at an individual station and in the called
subscriber circuit (the subscriber is busy or does not answer) respectively; _
t and ta are the average duration of time for making a ca11 connection -
at one station and in the called subscriber circuit respectively; T is the ~
average duration of a conversation.
- We shall calculated the load intensity* approximately, which the KS and W -
of the first station handle with the arrival of the ca11 from subscriber A _
to subscriber B. If the duration of time needed for making the call connec-
tion is neglected and the subscriber is considered to be absolutely persis-
tent, then the load serviced by the KS is equal to T in Erlangs, while the
~ load serviced by the W is equal to zero, something which does not agree
wi.th measurement data for the network.
'we shall cite the formulas for the network design. The probability for the
unsuccessful attempt to make a ca11 connection via the path fr4m A towB is:
Q=1-(1-q)'" (1-~ca)� ~1)
We shall subsequently make use of the geometric distribution, in accordance
wi.th which the number of attempts until the first success with,a,success
probability p is equal to 1/p. The average nutrh~r of attempts per ca:~l.
- M is determined by the geometric distribution witiz a parameter of p=~~ -a Q
, * In following the tradition of literature on telephone traffic theory,
we sha11 employ the concept of "load" in the follow~ng instead af the
concept of "load intensity" (which is measured in Erlangs). This dues
not lead to a:misunderstanding, since the remaining load parameters wi11
- not be treated as a random process. `
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t
and therefore: ~~=~_a ~~-~I-9~~ ~~-na~~�
~2)
- The call loss probability is:
pc=G;Q (1 -a). ~3~ -
The overall load handled by the switching circuit of the first station is: �
A=N1 [t9~-214 (!-9)-f-319 (1 -91'~-
-~4.9 (1-q)'-{-(4l-I-ta) (~-q)~na-1- (4) -
-{-(4t~-te-i-T) (1-q)~ (l-Za)~� ~4)
The useful (paid) load is: A.~ = T(1 - P~) (5)
and the load s~rviced hy the W of the first station is: ~
Y = tM (6)
In order to make a transition from the load per ca11 to the load per unit
time, the quantities A, A.~ and U must be mu1t3p13ed by 7~ - the average num- -
ber of calls per unit time. Tn this case a should be chose~} so that the
probability of blocking an attempt is equal to q.
TABLE
q Q M P~ A Ap Y I~ A A AII -
~I~~~~I~~
0.01 I 0,62I 1,8d I O.I I I 1.15 O.R9 0.02 f 39 4b 31.6
J,! ^,8? 2,b: n,I7 . 1 nR 0.83 0.03 I~4,4 48 I 36,b
0,5 ~ 0,97 ~ 7,75 ~ 0,75 ~ 0.44 I 0,25 0,08 I 1I I 49 ~ 27.8 ~
The results of calculations using formulas (1) -(6) are shown in the Tab1e
- for the case where: m= 4; a= 0.9; ~ra = 0.5; T= 1; fi= 0.01 and ta = 0.1.
- The column of values for a was taken in approxiznate manner by working from
- the assumptions that the number of channels in the trunk group is V= 50, _
_ the repitition rate is v= 10 anc~ the servicing time has one or two
phases: the first is the time for making the ca11 connection and the
second is the duration of the conversation j2]. The unsuccessful attempt
probability is equal to ~ra = 1-(1-q)3(1-tra), and in this case, the
_ servc~'.ng time conta3.ns one phase. . -
The data of the table show that in step with an increase in the unsuccess-
ful attempt probability of makig$ a ca11 Q, the number of repeat attempts
M rises rapidly and exponentially, something which leads to a correspond-
ing exponential growth in the load Y on the controllers; in step with a
rise in the ca11 flow rate a, the ove�~a11 serv~ced load ~A tends to v
- (i.e., to a 100 percent busy circuit); while the useful load ~A~ first -
- increases.~and then fa11s off.
The resul~irig data are approxi.mate. A precise solution of the problem
is apparentl}* accessible only by means of stat~stical mode~ing. An -
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1,0 7l a=~
q5 -
G,9 ?
0,1 Q
0,05
_ 0,01
o,oa5 A, erlangs
0,001
9D 3�5 40 45 50 A, 3pn o.
Figure 2.
analytical solution is given 3n [3] for a lossy fu11y accessible trimk
group which handles a poisson load. Curves for the probability of an
unsuccessful attempt at mak3ng a ca11 ~rt in a 50 channel trunk with a
- repetition rate of v= 10 are shown 3n Figure 2 far values of a= 0.9,
a= 1(an absolutely persistent subscriber) and a= 0(fiAe last curve
coin,cides wi~R tAe curve for Erlang's -~irst formula). A comparison of
the three curves shows that Erlang~s formula, wh~ch has up until now been
u~~.vexsal.7.y used in calculations, cannot serve as the basis for the _
determination of the carrying capacity of t~nnk groups, especially in
_ the case of large losses.
Two unsolved problems follow from the example considered herz: 1) For ~
the design of the controller, it is necessary to study systems with
waiting during the admission of the load, during which, in step wi.th the -
- increase in occupancy of the system, ~a secondary additional flow of
repeat attempts appears with an exponentially increasing rate (its own
kind of positive feedback effect); 2) For an approxitnate calculation of
the carrying capacity of a network, it is necessary to study systems with
repeat attempts in the case of two-phase servicing, whicfi can serve as a
model of a network Plemenfi.
~n anaZ~s2s of the car2~ing capac2t~. The efficiency of a long distance -
telephone network is determine~' by the income from payments for conversa-
tions which have taken place, which iorm the useful (paid) load. It is
always less than the serviced load. As the dat3 of the tab7e show, the ~
ratio A.~/A amounts to 77 percent when Q= 0.01 and 55.5 perc~..r overall
when Q = 0.5. -
The results of an analysis of the carrying capacity of a channel trunk
group, a switching station and controZler are shown in F~gure Tt can
be seen in ~'igure 3a how the serviced ioad A and the use~ul load A~
change as a function af the incoming load Ap (V is the number of channelsj. .
We sha11 call the di:fference A- A~ the service load AS~,, and it is ~
composed of the occupancy intervals i.n malcing the ca11 connection.
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~
Ho2py3k� Load The nimmber of channels is
, L~---- ~~I`------ usually chosen during the des3gn
Q A/ , stage so as to assure the permis- ~
~ ~cn Asl s3b1e loss possibrlity ~rdes�
A~ j However, because of the inac-
(a) ' ~ curate calculation of the serviced
load A, the loss probabiliCq
- U Aa, exlangs n~zm W~ich is obsPrved in practice =
~ , exceeds ndeS (F~gure 3b).
~b~ 1 -
- b) HQ ~i akmuke 6Te wi11 note thafi it is desirab? e -
- ~N3M ~~a~t~ to take an estimate of the time-
~ ~ iz ~ ~7ome0pur~ wise los~es (the prob3bility of
T~QC4 _ ~ In theory a loss with the first attempt)
_ es erlan. s as the loss probability, and not
' Aoq,aKrAopacy Ao,3pn g the estimate of losses based on
_ rayg r~v ~o fact ca11s (the loss probabilitp for
r - - - - _ the attempts), s~ice ~he first
Ha npak~riu~re ~sfi~alate fias a low-er statistical
B~ in prac ce scatter than the second. Tt
/lameapuu wou7.d be even ~mo~e ~ustified
in theory
~es i to take the ca11 loss probability
Yo nere P~, but unfor.tunately, there
yo~rrKr yopQC,r Yo,3pAerlangs are as yet no si.mple methods of
fact des measuring it. ~
Figure 3. The lack of agreement between the
theoret3cal calculation of the
average number of busy waiting positions, rayg, in the controller and the �
res~lts of observations in practice is shown in F3.gure 3c. This lack of
agreement 3s due to two factors: the presence o~ an addifiional load because -
of repeat attemF.~s and the fin3.fie number of waiting positions, r, (in con- "
trast to the calculat ion where an unlimited n~ber of them is usually as-
sumed). Because of these factors, the permissible mean number of occupied -
waiting positions, rd es~ ~s achieved not at the design load YO des~ but
rather at Yp gact�
The ~'expenditures--in~ome~' reZationsh�~p for a netu~ork, Tt is important for
designers when planning and egpand3ng a ne~work to determin~: its economic
efficiency S. This indicator can be appro~timately expressed in terms of
the received iacome, i.e.;
S = D - (B+C) ~7)
_ where D is the payment for conversations which ha.ve taken place
- (income); B is the speci.fic capital investment~; C axe the expenditures -
for the ongoing operat ~on and repai;r and restoration work for a specified
equipment readiness.
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- I'igure 4a illustrates the terms of expression (7~ where the curve D is -
derived by multiplying A~ (Figc~re 3a) by the payment per conversation unit.
Based on formula (7), one can ~udge the disadvantageousness of the ~ommun-
- ications syatem operation ~n the case of overloads (the range Ap > A~ in
- Figure 4b) as we11 as the economic eff~,ciency of var~ous~measures t:o change
the capita7. investments (a change in the curve B), operat~onal exx,endi-
- Cures (curve C) or to change the amount of payment per conversation
(curve D) . TH~'-i~come-" S is shown in Fa.gure 5a as a function of the
i:~Grease in the expenditures for repair and res~Coration work (a transz.tion -
from curve C1 to C2). The latte~ increases the equ~pment readiness indi-
~ catox and can increase the ~useful Zoad (the ~ransit~on ~rom Dl to D2).
And then we obtain two curves for the incomes S~ and S2 from formula (7)
CFigure Sb), from an aaalysis of which it can be seen that.the ~cpedience
o~ a decision to increase the outlays for repair and restoration work de-
_ pends on the size of the incoming load Ap: if Ap < A~, then the transition
�xom Cl to C2 is not advantageous, and in the case of A~ ~ A~, it is ad-
yaRta~eous,
a~ D
~ D~ -
Q, n - ---8 C2~i
~ -B .
~o, 3;:.7 A
s(Aol �
S 2
bl Ao ei langs S
~ i s,
Cb? Ao Bbiib~-A~ Ao,3p~ C~~ Ao
_ Ho IAO -
~HB Bbli0df10 H8Bb1- ~
(2~ ~00'HO ~gblZOdf10
~.Z ~2~
Figure 4. Figure 5.
~ Key: 1. Advanta~eous; Key: 1. Non advantageous;
2. Not advantageous. 2. Advantageous.
- The substantiation of standards for Zosses, The major indicator of the
carrying capac3ty of a network is the loss probability during the peak load
- hour. A1ong with this, work is being done to ref~:.�: ~he standards set for
communications quality, for example, not only th� .:rage losses are ..~xen
into account in paper [4], but also the losses ~�~~ri~g periods of scatisticai -
overshoots. For this, it is proposed in [5] that the average value of the
losses among 30 and 7 of the maximum peak load hour values over a year of
observations be standardized. Si:milar considerations are also taken as the
basis for a design load procedure treated in j4].
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However, why can~t the entire d~stribution curve for the valu~s of the in- =
coming load, A~, be used and then be limited by one value o~ this load in
the peak load hour? In fact, the incoming 1oad, A0, and, correspondingly, ~
~he serviced 1oad, A, vary during the course of a 24 hour day (Figure 6a).
If a histogram of the load values W(Ap) is plotted for hourly intervals
over the course of a year, it then turns out that the values of the load .
_ over one selected hour during the period of greatest occupancy (whirh is
also understood as the values in the peak load hours) fall in a range which
is not completely w~thin the reg3on of greatest load values (indicated by
the shaded area in ~'igure 6b) .
- Q~ Ao ~b) bl w W(Acl .
_ wyHMr If tt?e distribution density of the load
values W(Ap} and the income function S
~ 1�~Ny 2~ Ao 3(A0~ are known, then the average in-
yaca~ cymon coine can be calculated:
Hours of, .~h~ day
~3gure 6. ~ (g~ -
S= IS (Ao3 1~' (Ao) ~Ao.
Key: 1. Pe~k load hour. O
~ This quantity provides information on the economi.c effic~,ency of a trunk
group of channels or a network as a whole, and can serve as the basis for
setting carry~ing capacity standards. On analvgp w~.th (8~, one can define
= the average losses:
~ = j n (Ao) ~ (Ao) QAo, ~9~
0
where various kinds of losses (timewise, call losses, etc.) can be taken
as ~r(AQ). Expression (9) is closer to the standards adopted at the pre-
_ sent time than the economic characteristic of (8). A universal changeover -
a.n standards documents to characteristics of the type of (8) is hardly ex-
pedi:ent, but they should be used for the economic substantiat~:on of net-
work expansion variants.
- s(qoJ Netraork controZ. It is shown in Figure 4b
that it is economicallp disadvantageous to
operate a network if the incoming load goes
- ~ i Ao beyond the limits of the interval (A1, A~). -
In network operat3on, it is desirable to
Tarif i i avoid disadvantageous operational modes,
Rate i ~ and this especially applies to network over- _
~ ~ loads. Tt is possible to eliminate them
~ I ' ~ 4 by means of the following:
Q ~ 3~
I 2 i 1. The selection of the amount of payment
~ ~ for a completed ca11 (the tariff). Th3s
� measure is the most powerful tool of load
An control for the purpose of increasing 3t
during the night hours and reducing it dur- -
F~gure 7. ing overload periods. The interesting pro-
blem of choosing a model for the behavior
of a subscr3ber in the situation of changing
= 19
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tariffs arises in this respect. For the needs of automated service, it is
necessary to develop a tY4eory of self-adapti:ng tariffs [7] . The payment -
per current connection and ca17. is established based on the results of ob- -
_ servati~ns o� trunk opexat~on during the preced~rtg per~od (fihe cho~ce of
the length o~ this peried is also to be substantiated).
One of the possible variants for the solution of this problem is given in -
Figure 7, where 1 is a red~~ced tariff, 2 is the normal tariff, 3 is a doub-
- led tar3ff and 4 is a tripled tari~f. The selection of the boundaries of
the transitions from one tariff to another can be solved as an optimal con-
trol problem. -
2. Control of bypass routes. The generation of signals which limit or in-
hi.bit the ut%lization of bypass routes is one of the problems confronting
the CCTTT j3]. There are no theoretical prerequisites in existence today
for its solution. Questions of the calculation of the efficiency of by-
pass routes have now beenworked--o~fi for conditions wtiere Erlangts first
formula is applicable j6]. A similar problem, including the incorporation
of economic relationships for the c~st of direct and bypass routes must be
solved for a system with repeated ca11 attempts.
BTBLTOGRAPHY
1. Davydov, G.B., Rogi.nskiy, V.N., Tolchan, A.Ya., "Seti elektrosvyazi" _
["Electrical Communications Networks"], Moscow, Svyaz~ Publishers, 1977.
2. Ionin, G.L. Sedol, Ya.Ya., "Issledovaniye polnodostupnoy skhemy s -
povtornymi vyzovami i predvaritel~nym obsluzhivaniyem" ['~A Study of .
- a Fully Accessible Circuit with Repeat Calls and Preliminary Servicing"],
in the book, "Metody teorii teletrafika v sistemakh raspredeleniya in- ~
~ormatsii" jF'Telecommunications Traffic Theory MeCliods in Information
Distribution Systems".j, Moscow, Nauka Publishers, 1975.
3. Shneps, M.A., "Sistemy raspredeleniya~1informatsii. Metody rascheta"
- ["Informa.tion Distribution Systems. Design Procedures"], Moscow, Svyazt
Publishers, 1979.
_ Livshits, B.S., Fidlin, Ya.V., Kharkevich, A.D., "Teoriya telef~nnykh
i telegrafnykh soobshcheniy" ["Telephone and Telegrapn Traffic `lhe~rv"1,
Moscow, Svyaz~ Publishers, i971.
5. Ellc:in, A., "Dimensioning for the Dynamic Properties of Telephone
Traffic", Ericsson Technics, 1967, No 3. -
6. Gersht, A.M., Gersht, Ye.N., "Uproshchennoye opisaniye setey svyazi"
["A Simplified Description of a Communications Network"], TZVESTTYA A~1 _
SSSR. AVTOMATIKA I TELEMEKHANTKA jPROCEEDTNGS OF THE 'JSSR ACADII~IY OF
SCIENCES. AUTOMATTON AND REMOTE CONTROL], 1975, No 5.
20 =
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7. Kotov, A.V., Kutov, N.A., "Tnzhenerno-psi.kho~.ogicheski,y i ergonomicheskiy
podkhody k analizu i s3ntezu telefonnyitR s~stem~} j~'Psychological Engineer- -
ing and Ergonom~c Approaches to tRe Analys~s and Synthes~s of Telephone ~
_ Systems"] , in the book, "Postro}ren~ye ust~roystw uprav7.enfiy~a setyami
- svyazi" j~'TEie Design of Control Devices for Commun~cations Networks~�],
_ Mo3cow, Nauka Puhlishers, 1977.
COPYRIGHT: Izdatel~stvo '~Svyaz~," "Elektrosvyaz'," 1980.
[1239-8225]
8225 -
CSO: 8344/1239
i
~
- 21 -
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' ~JDC 621.394.62(088.8)
DIGITAL TRAIVSMISSTON SYSTEM STGNAT,S AND CODES
- Moscow ELEKTROSVYAZ~ in Russ~an No 1, 1980 pp 33-37 manuscript received
S Jun 79
~ [Article by O.N. Porokhov]
[Text] .I3~ttroduc-~ion. The present stage of the introduction of digital
transm~_ssion systems (TsSP) is characterized by the offering of analog and
digital channels to subscr:~Bers for data excltange, where the cfiannels are -
formed by the series insert~on of hieraxchical sex~es transmission systems :
with differing transmit rates and d~fferent means of routing. The develop- -
ment of uniform requirements for tRe des~gn pr~nciples of transmission sys-
tPms is one of the most important proDlems confronting digital transmission
system designers. A1ong with tAe tra~ditional quest~'ons in digital commun,
' ications - improving noise immunity~ and carry3ng capac~ty - of no less im-
- portance is the synchronization of a large numb~r of transmission systems ~
- which are tied together in ser~es. =
A great diversity of data transmission ~nethods i:s cRaracter~stic of evezy
transmission system (cahle, optical, radio relay, etc.~. However, the =
- selection of the optimum method and the development of general recommend-
ations for a specific system run up aga~nst difficulties because of the
specif tc features of the system, the lack of a uniform listing of the para-
meters and estimates of the~Lr maximum value~, as we11 as inaccuracies in
individual terms and definitions.
An attempt is made in the following to resolve these problems based on re-
~ commendations from general cammunications theory.
Specific features of digi~aZ ircfor~ma~ion ~rans�r.s: ion me~hods. T' e mer.ho's
of inf ormation transmission via cable digital }~.~smissi.on ~y5tems witt.
their specific character~,stic features Aave proved to be unacceptable for
transmission systems with other ~means of routi`ng. Thus, ~he requirement
fox the ~a~,anc~ng of a d~g~ta1 signal with respect to the DC component in
- cable transmission systems j1, 2] fias 1ed to its substantial redundancy, -
because of which these methuds have proved fio be unacceptable in optical
and radio systems. On fihe ~ther hand, the we11-known methods of digital '
~ '
- 2 =
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I
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information transmission by means of multi:pos~tion modulat~Lon o~
- radio signals are unsuited to cable syatems, :fn particular, because
of the fact that the}r do not mee~ the requ~rements fo~ synah~on~zafi~on
- of the transmission syFtem.
~ Methods of signal reception are known for cable transmission systems
are known which provide for a slight dependence of the noise immunity
on the properties of an unbalanced signal [3, 4]. Because of this,
_ a general approacPt to the design o~ transmission methods used in ver3ous
transmission systems is possible.
_ w+
- The difficulty of developing a general approach to digital information
transmission methods consists in the fact that in cable transmission
- systems, the concept "coding" in cable transmission systems is frequently
- understood to be some mathematical conversion of the binary information
being transmitted and s3.multaneously, the signal waveform, transmitted
via the communications line. We would recall that ...'~in thQ liter-
- ature on information theorp, the term ~coding~ ~s used ~,n d3fferent -
senses. Tn the broad sense of the word, coding is the term for the
conversion of a message to a signal. Tn a narrow sense, coding is
~ defined as the mapping of discrefie messages by a sequence of preselected
symbols" [5], with the additional explanat~on that the new symbols
change (modulate) the parameters of the line signal. Thus, the code
- designation .4B3T [13] reflects the concept of coding in the broad sense -
of the word: the conversion of binary symbols to ternary symbols and the
. transmission of the symbols by a spec~f~c v~deo pulse s~gnal (DC pulses
of different polarity and a passive pause).
Although such a repreaentat3on of the coding operation is permissible,
_ it still has certain drawbacks, since an,analy~sis of the code properties
is needed in con~unction with the parameters of any of the various
- transmiss~on system signals. By using the concept of coding in the �
narrow sen~e of the word, we sha11 assume that binary signals, generated
by any digital information sources and referenced to one of the hier-
= archical ~ates of a digital transmission system, regardless of their
_ type, are converted to a digital~signal in two stages (~igure 1): the
_ coding operation (not obligatory) - the conversion of the bina~y
~ ~ymbols to a sequenc~ of new symbols (code symbols); and the modulation
operation.- the change of ~he corresponding parameters of the carrier'
, as a function of the code symbol. The vehicles for code symhols in ~
cable systems can be the direct current parameters (polari:ty, amplitude, ~
video pulse width), in radio systems - the parameters o~ the carrier
_ (amplitude, frequency, phase), and in optical systems - the number of -
quanta. Tn analyzing transmissi.on methods in optical systems, it is
expedient to consider the signals transmitted via these ~ystems as video
pulse signals, because o~ tfle d~fficu7.ti:es irl process3ttg fihe adopted
s~;gna7.s. .
- 23
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, ~
1 ` (s) ! s,rr~ i i s,~~~ ~ ~ s,~t~ ~ i s~~e/ ~
/ I I
Nc.~novMUr ~(p y/;pr~ c~r~as~r~ ucu~t~a~ 1 ~ i I~~ ~ 4 i
- u~'G~paBcu Hodep r~~rl. A
(!Nla0~7M0({(!(/ Cf/MBO~l61 I(0(~0 i ~ 1 I I
~et ~ ss(~;/ ~ ~ s6(tl I ~ s~(tl s,(t! ~
~ g c~ 6 I 61 I~ ~j BI I
Fi ure 1. =~~_i ~
- Key: 1. Digital informat3.on source; ; t i T i~-~ T~ j~
f�--=, ~--~1
2. Binary symbols;
= 3. Coder; 9~ 59~t) I
4. Code symbols;
5. Modulator;
6. Digital signal. Figure 2.
TYte sigrtaZs of digi~aZ transmission systems. In contrast to radio signals,
it is difficult to make a breakdown of video pulse signals according to
kinds of modulat3on. We sha11 consider a video pulse e7.ement to be any
combination of video pulses and pauses within the clock interval T set
aside for the transmis~ion of one information symbol. :
- We sha11 assume the following (Figure 2) ~,n order to limit the infinite ~
set of video pulse signal elements: the pulses are square waves and their
width if T or T/2; the leading edge of the pulses coincides with eitiZer _
the edge or the center of the clock interval; the ampl~.tude o~ the video
pulses (and later on, also the radio pulses) is the same regardless of the
number of elements (we sha11 designate it as A/2).
, Under these conditions, the number of video pulse signal elements is _
equa7. to nine. A video pulse signal can be generated from the elements -
o~ Figure 2 by either an abs'olute or relative modulation method [6].
In the first case, a correspondence is established between the transmitted
= symbols and the signal elements. Then the number of binary video pulse
signals composed of hhe ~lemenfis of 'Figure 2 is:
C9 = 9!/2! 7! = 36
In the case of the relative modulation method, the binary information . _
= symbol 1 is transmitted by means of alternating two elements of the
- signal, while a zero is transraitted by repeating ~_ne elemen~ correspondi~:� .
to the transmission of the last symbol 1. For th~~ reason, the n~imber vi -
_ relative binary signals is likewise equal to 36. But the diversity of
video pulse signals is not limited to these figures. Mu1ti-eleme~lt video -
- pulse signaZs are used in transmission systems (several elements are
- used for the transmission of one symbol), as we11 as mult3posit~.on modu-
1at~on of the individual elements, etc. Tt is expedient to limit
ourselves here to a treatment of absolute binary and few niulti-element ~
24 -
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FOR QFFICIAL U~E ONLY
TABLE 1
9nen+eHr~ cxr- 2 video pulse S~:gri32S~ a compari^
~~?enoe pNC. 2 yHCno SOII4' O~ tPl@IIl and t0 COID are radio
npx nepc~ave y~oP, p K x P
I H~a ' us �r s~gr~als based on generalized
' � Pe dB parameters, wfi?ich rather s3mply
�i 2 s n~ o o,s o and completely characterize the
? + ~ A'/2 -3 0;5 o est~mate of the possib3lity of -
? 5 1 n'/s -9 o,s o their use in a di ital trans-
1 I 6 3 SA~/8 -2 0,5 0 g
~ 7 3 A'/8 -9 0,5 0 iTI~S3~Otl S 3teIII. -
t s ~ s~~~a -s o,s o Y
1 9 3 A~/4 -6 0,25 0
~ 3 �2 A'/2 -3 0,5 0
2 4 2 A'/2 -3 0,5 o The parameters treated in the
2 5 2 SA'/8 -2 0.5 0
2 6 2 ^'/e -s o,s I o following are svmmarized 3n
2 7 3 SA'/8 0,5 0
s s z nt~s -`s o,s o the tables: 1. For a11 (36)
� 3 4 2 A;/a -o o,~s o absolute binary video pulse
s s 3 q~%g _2 ~ i signals; 2. For some multi-
3 8 3 Ai/88 -g ~ i element video pulse s~gnals; ~
"'3 9 s nt/a -e o,s o 3. For b3nar radio si als.
4 5 3 5A~/8 -2 ~ ~ y ~
_ 4 6 3 A~/8 -g ~ ~
4 7 3 At/8 -9 I I i -
- a 8 3 SA'~8 -2 ~ ~ The potentiaZ noise ZilACllirl2'~ Of
~
b 6 3 A~%2 _3 0,5 0 a digi~aZ S2g'YILZZ. An important
5 8 3 1~%4 -6 i i parameter which assesses the
- ~ 5 9 2 A~/8 -9 0.5 1
~ e ~ s A~/4 -6 i i qual3.ty of digital information
- 6 8 ~'~4 ~ ' ~ transmission is the error
6 9 2 A~/8 -9 0,5 0
- ~ 9 2 ~'%s -s o,s o factor of a transmission system
- 8 9 2 A'/8 I-s o.s o (!~hich depends on the noise
immun~ty of each repeater), the
Note: *This signal has been g3,ven determinat~on of wfl~ch is
the designation '~monopulse" [11]; difficult. Therefore, to compare
**This one is called "bipulse~~ [12]; any dig3tal signals, it is
***Pulse doublet coding [17]. proposed that their potentia]
Key: 1. Elements of the signals of noise immunity be found under
Figure 2 when transmitting~a:; ideal conditions. As is well -
- 2. Number of levels; kr?own [5], the potential noise -
- . immunitp of a digital signal
depends on the "equivalent" .
p~wer P@ , of its elements,
s~(t), s~(t), i.e.
1 T
Pa = T f IS~ ~t) - SI ~r) d t, ~1)
S
in which case, it is proposed that the potential noise immunity be
determined for two elements of a signal with the lowest 1eve1 of Pe for
a comparison of multi-element and multiposition signals (the applicability
of formula (1) for the s3gnals of cable systems requires additional
research). _
25
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_ .v.. vi.~~,iru, ~.~L:, VLYLL
TABLE 2 -
Signals, the elements of which `
Ta6.iHue s (2) ~3~~ are opposite to each other and
~ ~1~ 3neyexrd m sat~sfq~ tAe equal~:fiy S~(t~ (t~
cxrxanon dg have ~he maxi~~n noise i~nmun~.t
- Iiai~MeHOeanHe PNC. 2 nps Y -
cerNanoe nepe,qave . G p, ~ PT Kt [5] . FOT example, fOY' the signals
i I o 7T Pe ~ shown in F3gure 2, this condition _
- 3s met for only two k3nds: with
nxi s-e 9 3 n~~s -9 ~ o,s o elennents of s1(t) s2 (t) and s3 (t)
CD11 (8) I-2 ~ 2 A~ 2 -3 0,62 0,5 ~ ~
AtPDC [9j 3--4 9 3 A~~(4 -6 0,5 0 S[F~t~. The equir.alent power ~1~
Millcr Coding 3-4 I-2 2 A~/2 -3 0.7b 0.8
~~ol _ of each pair reflects the max3mum
, Key: 1. Designat3on of the signals; Potential noise immunitp of the
2. Elements of the signals of digital s~gnals, Pe.max - A2� _
Figure 2 when transmitting ~e reZa~ive no2se i~rQnunity
3, Number of 1evels. coefficien~.sh,ows by how much
= t~,e potential noise immun3ty of
a dig~tal s~gnal differs from
tt~e ~axi'~ntan no3se immunity: KP =
TABLE 3 = 10 lo (P P
g e/ e.max)�
, Type of P Ix ns p K The mLnimum upper frequency of the
BxA aoAYnA4x~~ ~ n~
Modulation e d$ r I T s2gnaZ spec~2~tp~t, fv.m~, is a
Q~890B8A p~Se A~ls ~-a j ~,a o condit~onal frequency which is
y8CT07H8A ~ I A+/4 I-b I 0,6 I 0 equal t0 the first harmon3c Of
Awnnxrynt+an ~ A~/8 I-9 0.5 0 the per~od~c sequence Of those
signal elements for wh3ch it is
, a maxiinum. Tt is expedient to
express this paramefier 3.n terms
of the clock frequency of the
di.gital signal, fT. With the exception of a monopulse signal (Tab1e 1)
and an AMT signal (Tab1e 2) for which fv.min - fT~2~ the remaining
vidc~o pulse signals have fv.min - fT�
Thp probabiZity of a change in the parameter being moduZated, pT. Th3s -
indicator is introduced to esfi3uaate the mean value of the clock -
�requency in the digitai signal for the case o~ the equal probability of -
- the transmission of the binary symbols. The presence of attributes 0f
the clock frequency in a signal depends on the presence of leading edges
e~ pulses (transit3ons between ieve~s) ~ video pulse si:gna~.s and on the
change in the modulated.parameter~; in radio signal~, ~
Since the elements of the video pLlse signals of Figure 2 have transi-
tions a~ the boundaries and in th~ center of the clock intervals, taken
into account in the determination of rT (see Tables 1 and 2) are the
probabilities og the transitions, the density~ of the appearance of which
depends to a lesser extent on the variation ~n the statist~cal character-
istics of the information being transmitted.
~6
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The stabiZity fae~or of ~he eZock frequency at~x~ibu~es.characterizes
the stability of the change in the dependence of the modulated parameter
_ of a digital signal on the stat~stical properties of tRe ~nformation
being transmitted and is defined in terms of the ~max~mum pT~~X and the
minimum pT.min PrababiliCies o~ a change in the modulated parametere in
- ttte clock inLerval, i.e., KT ~ pT.min~pT.max�
_ Besides the enumerated parameters, also given in Tables 1 and 2 are the
numbers of the signal elements in accordance w3,~h F~gure 2, the n~ber
of 1evels as we11 as the well-known des~gnat~ons of the signals.
We shall expla3n the rules for the generation of muiti~element video
pulse signals shown in Tab1e 2. Desp3te the presence of the term "code", ?
it is proposed that they be considered multi-element s3gnals in the
. ma~ority of the designations. ~n .AMT (alternative mark inversion) [7],
the binary symbol 1 is transmitted b,y alternating the elements s,5(t) and
s6(t) while 0 is transmitted by the passive pause s9(t). I11 G'~~IT (coding
mark inversion) j8], the symbol 1 is transmitted by the aiternation of
the elements sl(t) and s2(t), while 0 is transm~tted by s4(t); in MPDC
(modified pulse doublet cod~ng) [9], the symbol 1 is transm~tted bp the
alternation s3(t), s4(t), while 0 is transmitted by s9(t). In Mi11er
coding [10], two elements each of the s~gnal are used for each binary ~
symbol: s1(t) , s2 (t) and s3 (t) , s4 (t) . -
The following conclusions can be drawn ~rom an analpsis of the digital
binary signals based on the 1ist3ng of the par.ameCers cited here: the
change in the potent~al noise immun3.ty of d~gifial s~gnals amounts to 9 dB;
monopulse [11] and b3pulse j12] signals have the maximum poten~~.a1 noise
immunity; the gotential noise immunity of phase keped signals is 3 dB
_ Be1ow the inax3~mum for video pulse signals, something which is explained '
by the differ3ng power 1evels of the square wave video pulse and
sinusoidal s3.gnals in the case where theix amplitude and widths are equal;
the use of radio signals and the ma~or3ty of video pulse signals for
which KT = 0 in d3gital transmission systems (in ~he case of arbitrary
stat~stical properties of the d3g3ta1 informat3.on) requires the steps
be taken to increase the stabil3,ty of the attributes of the clock fre-
quency.
In this case, the multiposition modulation methods with a base of 2Z -
(where Z is any integer, greater than one) wh~ch are we11 known from
radio systems, because of tfie lack of redundancy in the s3gnal do not
_ eliminate this drawback, and as has been noted, are not used for v3deo
signals. An exception is the b3pulse signal. Because of the balanced
nature of each of each of its elements s3(t) and s4(t), the max3mum
noise immun3ty and the maximum value of the stability factor of the
clock frequency attriDutes,~multiposition ~modu7.ation of the elements of
a bipulse signal makes it possible to compensate for the drawback: an
_ increased miniznum upper frequency of the spectrum o~ fihis signal (as
compared to certain other signals).
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~~,irw v..ru vLVLl
DigitaZ transrrtission sysEem codes. Addit3.ona1 convers~on of the binary
infor~ation (prior to the modu~ati;on of the carrie~ parameters) by means
of varying its statistical propert3es is necessary~for the purpose of
increasing the stability of the clock frequency attribu~es. For this, ~
scrambling and coding is accomplished prior to the 3nsertion of the
_ information in the digital transmission spstem.
_ Questions of scrambling (random~Lzation of the statist3.ca7, properties of
digital informat~on) are of ~ndependent interest and not considered
here~ We wi11 nbte only that sc~ambling and cod~ng are not mutuallp
exclusive, but are operat~ons wh3cA complement one another, however, it
is necessary to take into account a drawback to randomization: a certain
probability of maintaining extremal statistical situations.
Tn classifying codes, it is expedient to break them down into nonalpha- -
betic and alphabetic codes. Tn the first case, changing the statist3cal -
properties of the original binary information (while preserving its clock
frequency) occurs on1y~ under def~,n~,te condit~ons: a specified ntnnber of
continuous zeros, and sometimes also ones of tRe b~tary informat~on.
Alphabetic coding cons3sts in dividing the sequence of binary symbols
~ into groups with a constant number of clock intervais and ~nto groups of
code symbols with a new base of nvmeration i,n tAe~r subsequent conversion
according to a definite alphabet, and predominantly with a new number of
� clock intervals. Thus, in the case of alphabetic coding, agreement is
established between each bi.narp group of symbois and the group of code
symbols (or the groups in balanced codes jl, 2]). ~TA.en tRe clock fre-
quency is changed, it is necessary to transmit attr~butes wh~ch are
suff3cient dur3ng decod3ng to restore the boundaries (the frequencp) of
the groups of code symbols. Alphabefiic coding is cRaracterized by
redundancy of the convers3on of the binary informati.on.
A common drawback to scrambling and coding is tiZe possibil3ty of error
- multipl:~cation. The appearance of a single error during eode symbol
reception can cause errors 3n the binary information reproduced by the
decoder over the extent of several clock intervals. -
Nonalphabetic codes include the BnZS, HDBn and C~IDBn [2], in which a
sequence of binary zeros of spec3.fied length (equal to n+ 1) is
transmitted by a specified combination of pulses and pauses in the signal.
. The utilization of three elements of an AMT s3gnal. 'see Tab1~ 2) is a
common feature of the codes enumerated here. Howev..r, reduci~�; the number
of elements which do not contain clock frequer:y attributes [a signa' -
element with a passive pause sg(t)], as compared to AMT, violates the
condition for the alternation of pulse polar~fiy~ an,d ~ncreases the minimum ~
upper frequency of ttle s~gna7. spectrum up fio values of 0.6 fT to 0.7 fT
[16]. The ma~imum no~`se i~mmunity of signals of tnese codes corre~�vnds
to the quant3ty obtained for AMT. ~
2$
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Alphabetic codes, besides improving tl~e stab~7.~ty of the cloclc frequency
- attributes, increase the carrying capacity of a transmiss~Lon system and
_ lower its clock frequency. The following rule ex~sts for the designation
- of alphabetic codes. The first number in the name of the code type
indicates the number of symbols n, in the b3nary group being encoded.
_ A binary numerat3on ba;;e is 3ndicated by the Lat3n letter B(binarp).
The second number indi_cates the number of symbols, k, in a code gro~p,
_ while the last letter (or letters) reflects the new numeration base,
- M: T is ternary, Q is quaternary, QT is quinary, S is sextenary,
H is heptanary, etc. [1, 2], Thus, 4B3T code indicates that each group
of four binary symbols is converted into a group of three ternary symbols.
~ It is obvious that the transm3,ss3on ~f code symbols w3th an increased
numeration base (M > 2) requires 3ncreas3ng tfie distinc~ive attributes,
i.e., a mult3pos3tion signal. For example, to translait ternary symbols,
one can use any three elements of the video pulse signals d~piCted in
Figure 2, or one, but with three amplitude values, or a m~ture of
elements and their amplitudes; for radio signals, cne can use three
position modulation (phase, frequency or ampl~tude), as we~i as mixed
kinds of modulation.
- It is sufficient tp base a comparison of alphabetic codes on the follow-
- ing parameters: the number of groups of binary symHois, 2n and code
symbols, Mk (these parameters characterize the co~pie~ity of the real3za-
_ tion of the coding and decoding operations); the c~efficient of the change
in the clock frequency, KM = n/k; the code redurtdancy is:
r=(k/n logsM-1) l00~~
~2 )
and the maximum coefficient for the reduction in the clock frequency
_ (r = 0) for any numeration base M, which, taking formula (2) infio account
is defined as:
rl maY xn+M~ r o n~k -~0gz ~1�
.
In compiling a list of aiphabet3c codes, it is neeessary~ to observe
the condition for independent transmission of groups of binary spmbols
by combination of code symbols, i.e., the condition 2n < Mk. In the
case of the limitation of an infinite set of code fiypes wi'thin
_ reasonable bounds - to tens of symbols in binary groups (code types up
to lOBnM, for the realization of ~,~hich, it is necessary ~o discriminate
uP tp 1010 = 1,024 binary groups) and to a base seven numeration sys~em -
the list of alphabetic codes presented in Tab1e 4 was comp~led.
29 _
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~ .�v~~ vi�i�l~,l~w uo~ ULVLi
The term (code type) adopted here i,s understood as a general algorithm
for the conversion of binary symbols to code symbols. I`n Table 4, the
4B3T code is understood to be not only the 4B3~ code j13], but also
variants of :it: MS43 j14] and FOMOT (four znode ternar}r} [16], and the
- L742 code j15] belongs to the 4B2H type code, etc.
The total number of code tables (a table show3ng the c~~rrespondence
of the groups of b3nary symbols to the code symbol grot;ps) is extremely
large for eyery type of code. For example, for one of the siznplest code _
types, 3B2T, the number of code tables ~s equal to the number of perm~ta--
_ tions of 23 = 8 or Pg = 8! = 40,320.
TABI,E 4
C~JicoAa I 3t IKMI %.!I .N J1 I 4k IKM) % I~ Ko~a I 5k IKMI xoAa I 6k IxMI �o ~ Koqa I 7k IK/yl
A
IE31'I' 3I1.00I5A,501~ IB'Q 4II.00 IOO I 1Bl~fI 'S1.00I32,19~I 1BIS I 61.00~158.SOI lB1H 71,00180,73 -
28'?T g~1.00~58.50 4Bi 41.00 I00 2H1 II 52,00 16.10 2B!S 62.00 29.^.S 261H 72.00 40.37
3B^_T 9'I,50~ 5.66 3B_Q l6 I,50 33 3B2QI S 1,50 b4,60 3R'LS 3G 1,50~ 72.33 3B?H 49 1,50 87,16
4A'sT 27~1.33~ 16,67 4B3Q Crt 1,3:i 50 ~B2QI 252,00 16,10 I 4B2S 36^.,00~ 29,25~ 4B2H 492.00 40.37
5B4T 81 1,?Si 26,80 5B9Q 2561,25 60 SB3QI 125 1,66 39,32 SB25 36.2,50 3,40' uB2H 49i2,50 14,29
GR4'C Sl 1,50 5,66 6B4Q 2561,50 33 6B3Q1 1252,00 16,10 6B3S 216~2,00 29,25I �6B3H 343~2,00 40,37
7BST 2431,40 I3,21 7BSQ 10241,40 43 7S4Q1 6251,~5 32,G8 7AJS 2152,33 t0,f9 i 7B3Fi 343~2,33 20,31
,'E36T 729~1,33 IR.87 ~ 8B6Q 2045 1,33 b0 ~ BF34Q i 6:52,pU I6,10~ bB4S l_xJ62,U0 29,?5I~ bB3H 3i3~2,G6 6,27
9B6T 72911,50 5,66 9B6 ^048 1,50 33 9B401 625 2,25 3,20 9845 1295 2,25 :4,89 ~ 9B4H 2401 2,25 24,78
IOB7T I2l87II.S3II0,95 IOB7~ 8192I1,43 40 IOBSQI 3125i2,00 16,I0 IOB~S 1296 2,50 3.40 lOB4H 2401I2,50 12,29
x~~ x~xaKC ~ 2�~ K6M3KC � 2.32 KaMBKC ~ 2'~ K71/AKC a~�B~
- Key: l. Type of code.
A criLerion is proposed for the comparison of codes and code tables of
one type't the multiplicaCion factor for s~ngle errors, which result
- during decoding. Although minimization wi~h respect to the indicated
criterion does not lead to a unique code table, it nonetheless sub--
stantially reduces the nimmber of them. Thus, for a 3B2T code, it is _
reduced to eight with a minimum single error multipl~cation factor of
1.375.
The following conclusions can be drawn from an analysi~ of the list ~f.
alphabetic codes based on the proposed parameters ~e following ccaes -
have an advantage in terms of closeness to the ~o~~asponding maximum co~--
ficients of reduction in the clock frequency and code redundancy (with tne
- clock frequency change coefficient indicated in parentheses): 3B2T (1.5);
_ 9B4QI (2.25); 5B2S (2.5) and SB3H (2.66), the sma11 redundancy of which is
sufficient to preclude extreme situations during the transmission of digi-
_ tal information (which lead to a loss of synchronization in transmission
systems); if no substantial reduction in the transmit rate is required in
the transmission systems, then the best code is the 3B2T based on the ~
30 -
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aggregate of parameters (redundancy, complexity in the realization of the
coding and decoding operations and the error multiplication factor).
ConeZusion. The utilizat3on of the coding concept in the narrow sense of
the word and the breakdown of inethods of digital informat~on transmission
into coding and modulation operations make ~t possible to more completely
consider the specific features of each operation and evaluate their poten- -
tial capabilities. The subsequent selection of the set of operations for
- specific transmission systems should satisfy~ tfie requiremenfis placed on
digital covmmun3cations networks. Tn ~his case, because of the sfireng de-
pendence of some digital signal parameters on the stat~s~ica7. properties
of the digital informat~on being transmitted, they are to He deterwined
for worst case conditions to obtain a qualitative comparison of the para-
- meters.
- It is exped3ent to combine the codes cited above with monopulse, bipulse
and phase keyed s~gnals to obtain the maximum noise immun~tp of repeater
sections and the carrying capacitp of digital transm~ssion spstems, as we11
as to meet the requirements for digital transmission spstem synchronization
given any statistical character~stics of tfie digital ~nformation.
BTBLTOGRAPFIY -
1. Duc, N.Q., "Line Coding Techniques for Baseband D~gital Transmission"
AUSTRAL. TELECOMMUN, RES., Vo1 9, 1975, No 1.
2. Duc, N.Q., Smith, B.M., "Line Coding ~or Di.gital Data Transmission, _
AUSTRAL. TELECO~A4UN. RES., Vo1 11, 1977, 1Jo 12.
3. Shteyn, V.M., "Nekotoryqe voprosy postropenipa sistem svyazi s TKM"
["Some Questions in the Design of Pu1se Code Modulat~on Communications
~ Systems"], ELERTROSi1YAZ', 1966, No 5. -
4. Porokhov, O.N., "Metod priyema tsifrovykh signalov~' ('~A Dig3tal Signal
� Reception Method"], ELEKTROSVYAZF, 1978, No 4.
5. Fink, L.M., "Teoriya peredachi diskretnykh soobshcheniy" ["D:Iscrete
Message Transmission Theory"], Moscow, Sovetskoye Radio Publishers,
- 1970.
~ 6. Petrovich, N.T., "Peredacha diskretnoy informa.fisii v kanalakh s
fazovoy manipulyatsipey" j"D3screte I`nformation Transm~,ssion in Channels -
with Phase Keying"], Moscow, Sovetskoye Radio Publis$ers, 1970.
7. Patent No 706687 (England).
8. Takasaki, Y., Tanaka, M., "Line Coding P1an for Fiber Optic Communication
- System", PROC. TEEE, Vol 63, 1975, June.
31
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1'Vl\ VL'1'tli1L1L UJL' Vl'ILL
9. Pospischil, R., '~2 Mb/s Zong-Hau1 Data Above Vo~.ce Transmission over
- Cable", 1975 TEEE Tntl. Conf. on Commun., San Francisco, Calif., 1975,
June.
~ 10. Patent No 3108261 (USA) -
il. Patent No 524469 (USSR), "Ustroystvo priyema monoiznpul~snpkh ~ignalov"
["A Monopulse Signal Receiving Device~~], Porokhov, O.N.
12. Porokhov, O.N., "Predel~naya potentsialfnaya pomekhoustoychivost~ _
_ priyema videoimpul~snykh signalovt' ["The Maximum Potential Noise Immu-
nity in the Recept3on of V3deo Pulse Signals"], RADTOTEKEIIdTKA, 1978,
, No 12.
13. Jessop, A., "High Capacity PCM Multiplexing and Code Translation", 1968
IEEE Colloqu3.um on PCM, London, 1968, March.
14. Franaszek, P.A., "Sequence State Coding for Digital Transmission",
- BSTJ, Vo1 47, 1968, Jan.
15. Benedetto, S., Castellani, V., De-Vinsentus, G., "On a Class of Alpha-
betic Nonlinear Multilevel Codes for Synchronous Data Transmission",
1973, IEEE Tnt1. Conference on Communications, Seattle, Washington,
1973, June.
- 16. Buchner, J.B., "Ternary Line Signal Codes", 1974 Tntl. Zuric~h Sem3nar
on Integrated Spstem for Speed, Video and Data Communication, Zur3ch,
_ ~.974, 1~la,rcR.
17. Marko, H., Weisz, R., Binkert, G.A., "D3gital Hybri.d Transmission Sys- -
tem for 280 Mbit/s and 500 M bit/s", TEEE TRANS. COMMiTN., Vol Com-23,
" 1975, Feb.
COPYRTGHT : I`zdate~ ~ stvo ~~Svyaz ~ , "Elektrosvyaz ~ 1980.
[1239-8225] .
8225 .
CSO: 8344 /1239
32
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i
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UDC 621.395.5:621.372.544
DIGITAL COUPLTNG DEVICES (TRANSMULTTPLEXERS) IN COMMUNTCATTONS SYSTEMS
Moscow ELEKTROSVYAZ' in Russian No 1, 1980 pp 28-32 manuscript received -
- 13 .Sep 79
[Article by L.M. Gol~denberg, B.D. Ma.tyushkin and M.N. Polpak]
[Text] The stage of the wt,descale introduct~,on of dig;ital transmission
systems (TsSP) which use the pr~,ncip7.es of pulse~code modulation (TKM),
- as well as electronic d~gital sWitch3ng systems, has started on the
communication networks [~,2]. Digital transmissfion sys~ems are universal
and can be used to organize a specif~ed numBer of telephorie channels
(depending on the type of syste~) us~ng time d~''vision of the channels
(TKM VRK) or a group signal with frequency d~vision of the channels
(IKM ChRK). The principles of electronic sx~tch~ng of IKM VRK signals
_ have been taken as the basis for the design of the automatic switching
centers (UAK) and automatic electron~c long d~stance telephone exchanges
" (EAMTS).
At the same time, the basis of the existing communications network is the
multichannel analog systems wi,th frequency divis~on multiplexing [2J. For
" this reason, when organiz3ng a long distance commun~cat3ons network, auto-
matic switching centers should operate during a spec~fic, rather long period
of time using a combination system gor the organization of transmiss3on ser-
vice (analog.frequency d3vis3on systems, r3me division PCM and frequency
div3.sion PCM). Consequently, the construction of a commun~:cat~ons netwoxk
is impossible without the design of ~,nterfaces frir~systems with frequency
- and time division mult~plexing, as w~ell as dev~ces for coupling frequency
division systems to automatic switching centers (or EAMTS's). These coup-
1i.ng devices have been given the name ~Ftransmult~plexers" (TM). -
This articl~ is the first part of a paper devoted to the presentation of
the design theory and principTes for transmult~plexers using the modern
component base, wh~ch are of considerable importance to other fields of
communicat~ons engineering, for example, ~n tAe construct~Lon of digital
modems, PCM to binary PCM signal converters, etc. Transmultiplexer circuits
~7.7. be treated in the second part of the paper and a comparative analysis
wi17. be made of them.
33
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The funct,ions of trar.smuZtipZexers. Transmultiplexers have been called
upon to solve two basic problems: i.n the f~rst place, the segregation of -
individual channel signals from a group frequency division signal for
transmission to the switching field of an automatic switching center, and
secondly, the generation of a~group frequency division signal from the ~
individual channel signals incoming from the switching field of an auto-
matic swi.tch~ng center, for subsequent transmission in a frequency divi-
sion system. These problems could 3n princ~ple be solved using the set
of standard terminal equipment of frequency div~sion analog systems and
- PCM systems (for example, the K-60 and IKM-30 equipment for 60-channel
frequency division systems~. However, such a solution is hardly accept-
able since it involves the use of comparat~.vely expensi.ve analog equip-
ment, which is addit3onally of considerable size.
In step with the development of future digital transm3ssion systems, when
an integrated network comes to replaae the existing communications network,
in which signal transmission and switching is accomplished only in digital
' form, the functions of transmultiplexers will change to a certain extent,
They will serve for interfacing wideband PCM system channels to time divi-
- uion PCM systems as we11 as to interface ~requency division PCM systems -
and automatic surntcfizng centers (or EAMTS~s).
In connection with what was said above, a number of requirements must be
placed on the principles for the design and realization of transmulti-
plexers:
A T'M should take the form of a digital device, the design princip les of
which are in line with the design principles for future d igital trans-
mission systems and couple to contemporary transmission systems by means
of the simple addition of an analog-digital (or digital-analog) c onverter
at the input (or output);
A TM should be designed around a digital component base with rather strict _
- li.mitations on size and cost, something whi:ch ~s due to the need for a con-
siderable number of interface equ3pment sets for coupling frequency divi-
sion analog systems to one EAMTS; _
The digital signal processors included in the complement of a TM should
operate at high signal digitization frequencies (on the o rder of hundreds
of kilohertz, even in the case of a 60 channel group si.gnal).
- The latter requirement leads to the use of special design methods for tt~~
devices and the development of procedures which assure the optwmization -
specific TM parameters (for example, the minimization of the standardized
- number of operations per unit time or equipment volume), as we11 as the
newest series of integrated circuits which contain h~gh speed immediate
access (OZU) and read-on1}r (PZtJ) memor~Les, arithmetic-logic devices, re-
gisters and other functi:onal assemblies.
34
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Transmultiplexer realization using a digital component base requires the =
application of digital methods of f ilfiering, modulation and d~modulation
of the signals, which differ in many respects from the traditional analog ~
methods. TM variants are treated in [3 - 7], the pracfiical realization of
which proved to be rather complicated because of their considerable vol-
ume.
TM structures were proposed in [8, 9] for 60-channel transmission systems
which lead to a substantial reduct~on in tha equi,pment volume through the
standardization of the digital filters, the TsF, ~ncluded in the structure.
The standardization of the digital filters made it poss3ble in the reali-
zation of TM's to use the latest ach~evements of the theory and practice
of digital device syntYies3s (the construction of the dig3tal filters using
read-only memories and multichannel signal processing).
F~.gure 1. _
(2 ) yilmnTl ~r~ y~ltl _
y~ Key: 1. Analog-digital converter/digi-
yz(mnll yi(t/ tal-analog converter; -
ltt~'~~~T~ TM uA~ 2. Frequency divis~on--time
~ � div~sion;
_ . eg3yR SlR(O1~I~LA~ 3. Time division--frequency
~ ~ division;
4. Digital-analog converter/
/analog~-digital converfier.
As was noted above, a TM serves to interface systems with frequency and
time division multiplexing (Figure 1). The ~requency division and time
division systems can be both digital and analog. Tn the latter case,
analog-digital converters, ATsP, and digifial-analog conver~ers, TsAP, are
incorporated in the transmultiplexer. The ~ollowing symbols are adapted
in Figure 1: x(t) and x(nT) are the group analog and`digital signals from
the frequency division, respect3vely; y1(m n T} arid yi(t) are the digital
and analog signals of the i-th channel (I.= 1, 2, k).
The group k-channel analog signal with x(t) frequency division of the
channels has a spectrum of: k
X (i _ ~ Xt
t~t
- where Xi(iw) are the spectra of the channel signals, each of which occu-
pies a bandwidth of~dWi = L1w = const. The group signal takes up a band-
width of [u~in, c,.r~~] , where wmin - Z~w~ Wmax =~Z + k)dw. The spectra
of the~individual channel signals, yi(t), in a time division system are
located in the 1ow frequency range j0, aw] (Figure 2)*.
~
The absolute values of the signal spectra are depicted in Figure 2 and _
a11 the subsequent figures. However, for the sai~~ o,f brevity ~n the
~o7.lowing, we will be speaking of signal spectra when referring to the -
figures. -
- 35
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(X(iQ1) C~,~ ~Y(iwl~ Figure 2.
yQ~gd K
~ Key: l. Frequency division--
/ 2 3 H B~ y'~ p --time division;
C21 ~
p -~q o Q~ ~ 2. Time division--frequency
c;n,,,,=[d~ ~NOKC-(l,~)d~ division.
mj.Tl IaBx
The spectrum X*(e~T) of the group digital signal x(nT) is periodic with
a digitization frequency of wp [10]:
X�(e~��7~= ~ X(Iu~~-In~o)=
f.~
n~-o
- k o -
- L~ l1.d X[ ~t ~u i n~o).
tal rr~-ao
where the quantity wp is chosen from the condition of [1]: ~ax -
_ < u'min when c~ax ~ 2 Wnin ~ 2 Wnax ~~'~0 when > 2 uy~in ~ w0 = u 2~w,
� u= 1 2, while the main spectrum (when n= O~ occupies a bandwidth -
of ~ w~ E CWnin~ Wnax) �
_ The spectrum Yi(eiwT~) of the digital channel signal, yi(m n T) is
periodic with a digitization frequency of wb = wp/m = 2~ w:
Yl~e~~ur�~_ 1 'S` X~ (i~,-{-in~o)=
m T
n,a_ao
1 X~'(ic~-f-in~o)~- ~
~ mT ~
n=-w
~
1 ~ X~ (i~u-f-in~,o). ~l) ~
mT
n=-ao
~1~
where Xi(iw) and X~(iw) correspond to the upper (w > 0) and lower
(w < 0) bands of t~ie spectrum of the i-th channel signal.
The main spectrum of the yi(m n T) signal~occupic. a bandwic:th oL
IWI ~ to~ ~ -
A transmultiplexer should provide for the segregation of the yi(m n T)
channel signals from the x(n T) frequency division group signal with
the shift of the spectra of the segregated channel signals into the low
frequency range (direct convers~:on) and the generation of the group
~ si,snal x(n T) fron~ the individual channel signals yi(m n T) (back
conversi,on) .
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The baEic tz~pes of opera~ions in a~r~ansmuZtipZexex~. The main operations
in a TM in the case of direct conversion are: d~g3:ta1 filtering of the
group signal (to segregate the spectra of individual channels); the
_ shifting of the spectrum of a segregated ct~annel s:Cgna1 to the 1ow
_ frequency range and the reduction of the digitization frequency of the
channel signals (dec~uaat~.on) down to the quanfi~ty u,d; the inversion of
the spectrum of specific channel signals.
The main operations in a TM in the case of back convexsi.on are: digital
- filtering of the indivldual channel signals for the purpose of boosting
the digitization frequency (3nterpolat ion); ahifting the psectrum of
each channel signal to the requisite fr equency band; preliminary inversion ~
of the spec~r~ of individual channel signals.
The segregat~.an o~ a~hanneZ signaZ from the group signaZ urith simuZtaneous
~ conversion o f the segrega~ed spec~r~wn to ~he Zou~ fxrer{uency ~egion. Th3s
problem is solved by means of. the circu~i.t shown in gigure 3, which was
described in detail in [14].
x(nT~ ~n 9i (~Tl 3n 9i /mnT~
~7.) (2) -
Figure 3. �
Key: l. TsP [grobable misprint for TsF = digital filter]; -
2. 3n [inhibit gate].
I~, ir~r 2{ 2- 1- 1' yr .
_ iX +e l~l f~I~ /I/1 ~ I~I~
, A, L r~ r-~ i r-i r~ The segregation of an individual �
- ~7 ~ r~ ~ ~ r-~ r~ channel is accomplished by means �
~Y:~~e~,r~~~~---~~ of a digital bandpass filter TsF ~
~Yz(e, l,~ 2/1 I 1~2' ~ ' \
~y~�~eW~~I~~M~~~~~~~~ while fihe shift of the spectrum of
I'"~'~"(e"'jj~ the segregated s3gnal to the low
o a~ ~,o wo ~ frequency region is realized by ,
means of a simple reduction in the
Figure 4. digitization frequency of the out- '
pufi s~,gna1 of the digital filter
- by a factor of m, using an inhibit
gate, 3n. The principle of the
_ segregation of a channel signal froni a group to channel signal (Z = 1, -
k= 2, see Figure 2) urith the shift of the spectrum to the 1ow frequency
- region, where X~`(ei~T is the spectrum of the two channel group signal
_ x(n T) is illustrated in Figure 4. A1 and A2 are ~he 3deala:zed
- amplitude-freqLency responses (AChKh) of the digital filters for the
= segregation of the first and second channels; ~'1(ei~)' and ~2 (e1wT)
are the spectra of the y1(nT) and y2(nT) s3gnals at the outputs of the
37 ~
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,
*
filters which segregate the first and second channels; YZ(ei~~) and
Y2 (eio~'r' ) are the spectra of the yl fm �n T) and Y2 (m n T) si:gnals
following the reduct3.on of the digitization frequency. As can be
seen from Figure 4, either the direct epectrum of the channel being
segregated (for the second channel) or the inverse ep~ctrum (for the ~
first channel) is pos�itioned in the 1ow ~requency region.
= We shall note the following circumstances: The idea~.ized amplitude- ~
' frequency response o~ filter A~ for the segregation of the i:-th channel
i.n the passband ~w~ E[0, wp/2] i~ defined by the relationship:
a A1-IH�(etm~l-
1 npx ~ E[(t f--1) ~1-}-i) A wl ,(2)
0 npx u~E[(1-}-i-I)~~, (l-~-i)~~�],
_ whex'e
ly� ~~t ~r~ _ H, (z) ~ . y` (z)
~c,r
z=e ,
is the transfer function of the.digital filter.
In a real digital filter, expression (2) is approximated with a specif ic -
degree of accuracy, Ai � 0 when w~[(Z+i-1)~w, (Z+i)~c,~], and with the
reduction of the digitization frequency, the phenomenon of the super-
. position of the spectr.a takes place, something which.Zeads to si$nal
~ distortions. Because of this, rather severe requirements are placed
- on the parameters of the amplitude-frequen~y response of a channel filter
in the top band.
If one additioually takes into account ~he fact that the ratio of the
sum of the transition bands (the reg~on between the passband and the
_ stopband) to th.e sum of the passbands and stopbands is very sma11 (even
~ox a 12 channel group, it is approx3mately 0.033), considerable diffi-
culties ari.se in the realization of the channel fil~ers.
Moreover, it can be seen f rom (2), the transfer functions of the filters -
for the segregation of the various channels are different, and for this
" reason, the design of a coupling device based on this principle requires
the utilization of a set of bandpass filters. -
- Another solution ef the problem exists where one can use the same ciig~.tal
1ow pass filter for the segregation of any channel (Figure S). Figure 6
illustrates the operational principle of the circuit. The input group
= si,gnal x(n T) with a sp~ectrum of X*(eiwT) is multiplied by the carrier
_ so that the spectrum Xi(e~T) of the channel being isolated is positioned
in the frequency range j-~w/2, ~W/2] (Figure 6b). Then the requisite
38 =
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~
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channel is isolated by means of a 1ow pass filter (~'1,gure 6c, d), the
. digit3.zation frequency is reduced (~'~gure 6e) and the bactc conversion of ~
the spectrum to the frequency range I0, Aw] is realized (gigure 6f). Tt
should be noted that the input and output signals of the 1ow pass filter
are complex. This can also be seen from Figures 6b-d, since the spectra
of the signals are not symmetrical relative to the frequency w= 0.
-i~f 2(I+~il-14~
e t~o ~ ei�~n -
~1~ ~2~
- x(nTJ X,r(nj1 ~q~Hy yi (nrl 3~ y! (~nnTJ X yi(mn7 Re yi (m~TJ _
~ d a e ~
~
Ca) . ~b) ~d) ~f) ' ~g3
Figure 5.
- Key: 1. TsFNCh jdigital low pass f~.lter]; 2. 3n [inhibit gate).
- The process3ng of the cc5taplex signal is accomplished by a 1'complex~~ circuit.
This means that there are separate branches for the process3ng of the real
x1(n T) and imaginary x(n T) camponents of the signal x(n T). The operar.._:~~
_ tional principle of the "complex" circuit of Figure 5 is 311ustrated 3.n de-
tai,1 i.xi Figure 7. The signal w3th the requisite spectrum (1Z is derived
through the segregat3on of the real component of the s3gnal pi(m n T) (the
element Re in Figure 5).
_ The inversion o f the spec~z~um o f a signcz Z Zoca~ed in ~he Zotv f~requen~sy
~ range. If the primary signal spectrum z(n T) occup3.es a bandwidth of
~w~ ~(0, ~m], while the digitization frequency is Wp = 2pw, the
spectrum inversion is accomplishad by means of a simple change in the
sign of every second signal readout z(n T): z~(n T) _(-1)n z(n T), n= -
J ~ = 0, l, where 2(n T) is the signal, the spectrum of which 3s inverted
with respect to the z(n T) signal spectri~. The relevant e.~cplanations can
be found, for example, in [8J. -
- Sign~czZ interpoZution br~ means of a digitaZ fzZ~er. ~n pure form, the
interpolation problem cons3sts in boost3.ng the digit~zat~on frequency of
_ a signal having a fin3te spectr~mm. The analys3s of the interpolation
process in the frequency range [12] shows that this process 3s essentially
one of linear digital filtering of the signal be3ng interpolated.
If z(n T) is the signal being interpolated and hav3ng a spectrum Z*(eiwT~~
, and f([n/m]T) is the signal following interpolation (increasing the
digitization irequency by a factor of m) having a spectrum F*(eiwT~~ then
= as can be seen from F3gure 8(m = 3), the interpolat3on process cons3sts
in suppressing the components of the spectrum of the signal z(n T) which
~ fa11 in a range of [~/T, ~/T~). This problem can be solved bp means of
� a digital 'low pass f3lter, to the input of which the sequenc~ of readouts
is fed:
- 39
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r m \ for
- z l r~ npe n= 0, rrc, 2 m, -
Z~n T ~ for o~her n.
= 0 np?+ Apyrex n, -
a ca~ ~ ~ ~ f /1 /I -
b Ce;.7l~ ~ ' ~ -!1./~~ 1Jd.~'
i0 ~ rn� G!
~ r i : f~lf' ~ � Pr, ~
e ~a f~ f+. t~ t~ t~ t~ w
f' e' \ f~ ~f~' ~_f~ f~ f~ f~ ~ -
g ~~'i ~i~M /l I~ /1~_~dJ`..dL1
0 c~o c~o
Figure 6.
2(l+i)-/
cosl~ ~o d~af ' cos 2
a -
X Xt(~~l ~
Ny yi~(n7 3n 9~r(~nllX yi~lmnll
x(RT) sin ~~c' 2l
oiJ-1 d~~~ ~2~ sin Z n _ yilmnTJ -
X X2 (~TI urANy yi2(~~ 3n yit(~~T X yit(mnT)
Figure 7.
Key: 1. Digital 1ow pass filters;
2. Tnhibit gates.
t ir~i'
~Zr~p~~~~-~z~~`'~~j~~~?.~5?~d~L I A~(e 1~~
~ r1 ~f~~~a -
~t i�rt' i i G/ A r] ' n I ~
~f ~e 1~-~{~-q ~ 1 ~ ~ r?
0 ~L ~~t w ~f~~ei~~1,1 _d I/1 I~ ~/I
j � T ~ ~fz(e ~ ~ -
~ (J~ Z-~
' T
Figure 8. Figure 9.
In other words, the sequence z(n T~) is derived fro~ the sequence z(n T)
- by means of inserting (m-1) of fih.e zero readout be~~aeen two informarion
readout sequences. Tt was shown in [12] that the spectrum Z*(el~`) of
the signal z(n T') coincides with the :spectrum Z'~(e~wT) of the si~nal
z(n T) (see Figure 8), while the signal Frith a spectrum of ~'*(eiwT~~ is
attained by means of processing the signal z(n T') with a digital 1ow pass
filter operating at a dig~tization frequency of w~p = 2~r/T':
40
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- FOR OFFICIAL USE ONLY
Fs ~e1 tu T~1 = N' (e1 ~u i'~ zi /ei m T')
1 ~
The interpolation process can be camb~ted w~Lfih the sh~fting of the
spectr~ of the s3gnal be3ng interpolated to tfle requis~te frequency
band. For this, it is suffic3,ent ~b use a dig3tal bandpass filter as
the filter-interpolator. Figure 9 illustrates th~ process of interpol-
- at~'on with simultaneous spectrum convers~on. The follow~~ng symbols have
- been adopted in fihis figure: Zi(e1WT~) is the spectrum of the 3nput
si..gna~ to tRe i-th digital filter; A~, ar~d are the amplitude-frequency
responses of the digital bandpass filter-~nterpolators wh~c$ accomplish -
the simultaneous conversion of the pri~nary spectrum of the sigrtal be~ng
interpolated to the frequency ranges jew, 2~w] and [2Qw, 3Qw] respectively;
F1eiwT') and F2(eiWT~) are the signal spectra at the digital filter out-
put. In comparing ~igure 4 and ~'3,gure 9, it can be noted that when
interpolating signals, d~g~ta1 f~lters are used AaviXig fihe same txansf~x'
functions as in the case of the segregat~on of ~nd3v~dual channels from
_ the group signal with simultaneous conversion of the spectrum to the 1ow
frequency range. For th~s reason, the same drawbacks are inhe~ent in
the interpolation method described here wa.th spectrum convers~on as in
th~~ corresponding method of isolati,on of findividua7, channels.
The generation of a singZe sideband si'gnaZ u~i~h subseq~ien~ conversion
" of ~he spec~rwtt. The process o~ s~gna7. ~~erpolat~on and spectrum
_ conversion to the requisite frequency band can be carr~,ed out in two
stages using the circu~t shown in Figure 10, wRere fihe di,gital filter~
i.x~~e~rpo~,atox is designated TsFF. g~gure 11 explains this process. We
~ote that the signals z(n T), z(n T), ~(n T') and ~`(n Tf) are complex
and the circuit of Figure 11 conta~ns fiwo branches for process~Lng the
real and imaginary components o~ t$e complex signal, just as the circuifi
o~ F'i.gure 5.
B'~rt f111 trt -1.d47n
e
' ~2~ ~ (3) ;
- z(nTl X i(nTJ ~~Hy Zr~T) u~N flnT~l X f(~T~l RQ f(~T~1
~1~ ~npMUpoB~HUe i NH~epnonacfuA ~ /IepeHac
crtzHV~a c 06/1 I~~erpolati,o~t cnen~mpa ~4~
Figure 10. _
Key: 1. Generati,on of the SSB s~:gna1; _
2. Digi:tal Zow~ pass f~`7.ter;
3. Digi.tal interpo?atiun ~~1ter;
4. Spectrum corrvers~on. .
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. 11~~~%c~rj~ \ ~ ^ ~o be inclvded among the merits
I Z'(ef4'r1~ of t~~s circuit is the fact that
' AmNy~~T ~ the operat~ons og gerierating the
1z single sideDand s~:gna1 (SSB) is
~ F:~t~~~~~ ~ ~ accompl~sAed at the low frequency,
I f'(e""I~ i ^ and in tRe case of signal interpol-
- jF'~e""11 i1 n it at~on, there is considerable spacing `
' o~o= ~ s~a=~ ~ Detwecr~ ad~acent components of. the
spectrum (s~e ~igure 11). This
greatly simpl~f~es the transfer
- F~gure 11. funct~ons of the digital filters
used as w~11 as their realization.
The generation of a SSB signal at the loar frequency~can also^be realized
by means of the converter treated in [13].
BTBLTO~RAPRY
1. Levin, L.S., Plotkin, M.A., "Osnovy postroy~ni:ya ts~Lfxovy~kh sistem _
peredachi" ["Fundamen~als o~ D~gital Transmission S}*stem Design"],
Moscow, Svyaz' Publishers, 1975.
- 2. Bubman, D.R., "Sovremennoye sostoyani,ye i perspektivy razvitiya mnogo-
kanal'nykh sistem peredachi v provodnoy~ svyaz~:~' I"Tfie State of the Art _
and Prospects for the Development of MuStichannel Transmi.ssion Systems
in Wire Communications"], "Ttogi nauk~ i tekhniki. Seriya Elektrosvyaz
_ ["Progress in Science and Engineering. Electrical Communications Ser-
ies"], 1976, Vol 7.
3. Weaver, D.K., "A Third Method of Generation and Detection of Single
Sideband Signals", PROC. IRE, 1956, Vo1 44.
4. Darlington, S., "On Digital Single-Sideband Modulators", TEEE TRANS. -
. ON CIRCUTT THEORY, 1970, Vol CT-17, No 3.
5. Kurth, C., "SSB/FDM Utilizing TDM Digital Filters", IEEE TRANS. ON COMM.
TECH., 1971, V. COM-18, No 6.
6. Freeny, S.L., ~t a1., "Design of Digita7. gilters for an A11 D~_gica?.
- Frequency Division ~Iultiplex Time Division Mu~.~~p1ex Transiator~, lE~E _
TRANS. ON CTRCUTT THEORY, 1971, V. CT-18, No 6,
7. Bonnerot, G., Coudreuse, M., $ellanger, M., ~~Digital Processi.ng Tech-
- niques in the 60 Cfiannel Transmultiplexer'F, TEEE TRA.NS. ON COMM., 1S~i8,
V. COM~26, No 5. -
8. Gol'denberg, L.M., riatyushkin, B.D., "Vydeleni.y~e kanalov i.z gruppovogo
tsifro'vogo signala v sisteme TKM ChD" j"Th~ Segregation of Channels -
from a Digital Group Signal in a~~requency Division Pulse Code Modula-
tion System"], ELEKTRCSVYA.Z'~, 1978, hc 5.
42
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FOR OFFICIAL USE ONLY -
9. Tsudo, T., Morita, S., Fu~i, Y., F'D~gital TDM~PDM Translator with -
Multistage Structure~~, T~EE ~R,ANS. ON COMNI., 1978, 'V. COM~26, No 5. ~
' 10. Dzhuri, E.T., "I~npu1'snyye slstemy avtrnttaticheskogo regulirovaniya"
["Pulse Systems for Automated ControlF'], rloscoGr, Fizmatgiz Publishers,
_ 1963. -
11. Matyushkin, B.D., "Vydelen~ye otdel'nogo kanala ~,z gruppovogo tsifro-
vogo signala v sisteme svy~az~ ChA IIII~'IMl~ j"The Tsolat~.on of an Tndivid-
ua1 Channel from a D~g~ta1 Group Signal in a~requency Division Pu1se
Code Modulation Communi~ations System~'] , sn the booIt, F'~eti i kanaly
svyazi i raspredelen3ye informatsii'F j"~Commun~:cations C$annels and
- Networks and Tnformat~on D~'stra;but~;on"D] , TU~S' jnot furtAex' defined] ,
_ 1978.
12. Shefer, R., Rebayner, L., '~Metody tsifrovoy obrabotk~ signalov v
zadachakh interpolyatsii~` j"Methods o~ D3gital Signal Processing in
_ Interpolation Problems"J, TTTER, 1973, Vol 61, No 6. .
13. Rabiner, T~. , Gould, B. ,"Teoriya ~ pr~uez~eniye tsifrovoy obrabotki
signalov'' ["Digital Signal ~~ocess3ng Theory and Applications"], Trans- -
lated from the English, edi~ed by Y'u.N. Aleksandrov, Moscow, Mir Pub- -
_ lishers, 1978.
' COPYR~GHT; Izdatel~stvo F'Svyaz~,~~ "Elektrosvyaz~,F' 1980.
[1239-8225]
8225
- CSO: 8344/1239
43 -
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rvn vrrl~tru~ u~r. VLVLY
UDC 621.395.74'.001.2
TN.E SERVTCE QUALITY OF AUTOMATTC LONG DTSTANCE TELEPHONE SERVTCE
Moscow ELEKTROSVYAZ' in Russian No 1, 1980 pp 62-64 manuscr3pt received
14 Mar 78
[Article by A.B. Klibane1 a~d N.V. Pevtsov]
[Text] Introduction. The fast rate of growth in the number of long dist-
ance telephone conversat3.ons and the placement of new ~ypes of AMTS jauto-
matic long distance telephone e.XChanges] in service Rave created a number
_ of serious scientific and engineering problems related to the requirement
that the service quality for subscribers be increased j1]. One of the
major characteristics of service quality in the case of automatic long
d~stance telephone serv~ce is the losses.
Trunk groups of expensive channels are organized between various AMTS's,
� where these ch:annels must be utilized to the maximum possible extent. This -
can be achieved with a reduction in service quality, i.e., increasing the _
antount o~ losses j2], somethiag which is unacceptable. The capac3tp of a
trunk group of channels, in accordance w3th CCTTT recommendations, should
assure losses of no more than one percent. Optimal solutions must be found -
which tie together the requirements of increas3ng both the 1eve1 of channel
usage and communications quality.
Various factors have an influence on the quality of automat~c long distance -
service, and among them we shall single out the fo11ow3ng main ones: the -
variation 3n the load on the equipment and the 1ine; the perceptible flow
of repeat ca11s; and the lack of operationally timely monitoring of commun-
ications traffic.
Moreover, reasons for poor serv3ce quality can be inadequate knowledge of -
the nature of the load incoming to an AMTS, me~'_ous of calcu'lating it whicr,
- are not always satisfactory, the lack of the technical capabi~.3ty of con-
trolling the incoming load and d3stri~uting it. We sha11 cor.sider the thre~
major influencing factors which we have singled out.
FZuctuations in the Zong distcrnce Zoad. The long distance load, Y~, pro-
~ duced by ca11 sources is a random quantity and subject to fluctuat3ons.
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These are random fluctuations in the load intensity from long distance
message sources, as we11 as seasonal f7.uctuations,
The design procedure for AMTS's takes into account the nonuniformity of the
long distance load as a function of the seasons of the year. The average
number of incoming ca11s per 24 hours is detertnined by means of dividing tr?e
annual level by 300 days instead of 365 so that the load is increased by
approximately 20 percent. A similar approach in the area of large loads
_ can lead to a substantial overstatement of the planned equiument volume.
If, let us assume, with losses of one percent and an ~ncoming load of
10 Erlangs, 18 channels are actually required, then taking this 20 percent
into account, there ~ril1 be more than 20 channels; the volume of channel
equipment wi11 be increased by 10 percent. Given the same losses, an
increase in the load of 100 to 120 Erlangs leads to an increase in the
_ volume of channel equipment by more than 20 percent.
Consequently, it is insufficient to characterize the randari quantity YM -
with only the mean value. Deviations in the values, which can be treated
as a random quantity, can be so great that the qual3ty of a long distance
message can prove to be unsat3sfactory.
Because of this, the calculation of AMTS equipment volume must be based on
- that 1eve1 of the incoming load at wh~ch tRere is the probability w of
assuring the requis3te serv3ce quality to subscr3.bers with a specified
standard norm for the losses. Such a level has come to be called the
design level. -
The theory of the design load for municipal telephone exchanges is
presented 3n [2], where a relationship is found between the average Y
and design YP load levels when w= 0.75:
Yp = Y 0,674 YY, ~1~ -
_ Taking into account the specific features of fluctuations in the incoming
long distance 1oad, the design long distance 1oad, YP~m, can be determ3.ned
from the formula proposed 3.n [5]:
~ YP�M - YM 'I' Q~1 ~Y�H~ ~ ~2 ~Y~~ ~ ~2~ -
where YM is the average value of the long distance 1oad; ~~(YM) is a
function which takes into account the random fluctua~ions in ifis sources; -
~2(~M) is a function whicfi taI~es ~nto account tRe seasonal fluctuations
in the load. -
We will note that in accordance with the existing design procedure of
~1]: -
(YN) _ (}~M) _ ~~2 Y~.
(3)
45 ~
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~ v.� ~a ~ i~iaau V JL VL\L1 _
and only the seasonal fluctuations are reflected in it, something which is
clearly inadequate for the characteristics of a long distance 1oad. _
A detailed analysis of the statistical data from materials of the -
Leningrad AMTS and a hppothesis concerning the verp simple nature of -
ca11 flow and an exponential servic3ng time with an average value of
T= 0.05 hours has made it possible to derive the following formulas,
taking (1) and (3) 3nto account: .
~i (Yu) = 0,215 ~yL. C4)
~z tYr) = Yy exp [ - (1~6 ~ 0,01 YY)1.. ~5 ~
~ Formula (2) assumes the following form in this case:
Yp y= Y~ r~ +e- ~~.s+0.oi Y~)1-~
L ~ t6~ _
0,215 )~Y,,,
An analysis of formula (6) shows that the greater the value of YM. the less -
the design value YPM differs from it. Tab1e 1 illustrates wha~ ha.s been
said here. The physical essence of the flu~tuations is reflected here: the
_ greater the load, the smaller the fluctuations to wh~tch ~t is subjected.
TABLE 1 In the planning of an AMTS, the design
= value of the long d3stance load is
used only to determine the number of -
junction and control devices. A11
' Yp~-Y~ x operations to comb~ne and split the
Y~.3pu `Yp~.3pn y
~ flows of long distance traffic at
_ X10�~~` �~arious selector stages of the AMTS "
a.i o,iaa es and the transition to the calculated
io i~a~5 z4 design values are realized in
ioo io:,is ~~i accordance with the generally well
known algorithm of [2].
The design long distance 1oad, determine~ from formula (6), is justified
for the calculation of the number of channels or devices, which are -
i.nserted in a fu11y accessible~manner. Studies show that the design long
- di,stance loads, in the case of incompletely accessible insertion, with a -
- sma7.7. amount of error can also be taken as equal to ~p~M.
Since load fluctuations lead to a:~ increase in the ~erage traffic losse~
pl.ann~stg an AMTS with the use ~f the design load method makes it possible
to specify regulations for the ~ean 1eve1 of losses can a communications
xoute. -
Setting Zoss s~anda2~ds. As has aZready been mentioned, the main charac~er-
_ ~.8tfc of service quality is the losses. Tn accordance with j1], losses
are standardized for a switching section o~ a long distance telephone
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TABLE 2
Item Peak
No. Route Load
Hours
1 Vi1'nyus 20-21
2 Tallin 20-2'1
3 Arkhangel'sk 20-21 -
4 Volgograd 20-21
5 Riga 10-11
6 Kalinin 10-11
7 Novgorad 9-10
8 Voronezh 14-15
9 L'vov 15-16
10 Moscow 15-16 -
11 Tntrazonal routes 10-11
- network, i.e., the trunk group channels between AMTS's, wihhout taking -
into account the switching equipment of the AMTS~s; a norm of one pereent
has also been adopted there. At the same time, the operational instruc~'.
t~ons for an ARM-20 AMTS sets the standard for failures in an exchange;
at a level of tw~ percent, taking into account failures on ~he traffic
routes, leaving one percent for losses due *_o the channels being busy.
Such an approach is correct, however, 3t is useful to specifp tP~e two
percent level more precisely. Tn facr, losses at an AMTS are a~so due
to the occupaney of the channels, instruments as well as blockages in ~
the swi,tch field; losses can occur because of row overflow and the limited
wai~ang t itne in the control devices which service the ca11s in a system
1t~'v~g waiting. For this reason, 3t is more expedient to understand the
switched section of a long distance telephone network to t~e the aggregate -
of the AMTS equ3.pmen~ and the long d3.stance channel, where the input ~o
the section is the input to the swftching equipment, while the output is
the sets of term3nal equ3pment of the channels or lines.
The question of setzing loss standards for AMTS~s requires careful study. _
First, the overall standard for losses from subscriber to subscriber 3n
_ the case o~.fa long d3stance call must be determined, and then this quant3.ty
must be d3str3buted over the switched sect3.ons. The loss standard for a
section wi11 depend on the type of ,~dE~l~S, something which wi11 make it pos-
sible to reflect the actual cost relat~onsA~ps on the network. Tn this
case, it is necessary that the loss standard for a trunk group og channels
- not exceed one percent in accordance w3th modern xequizements. -
47 -
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rvn urrit,ttit, UD~ vt~LY
In the case of loss distribution� it is necessary to take into account the
specific features of each particular commun icat~ons route. Tt was shown in
[4] that routes can exist, for wh3.ch a degradation of service quality is
permissible from an economic point of t~iew. This question can be resolved
_ ~tn precisely specifying the network structure and the existing equipment.
The principles for the distribution of the overall loss standard for rhe
switched sections of a long distance network are the topic of a separate
article.
The organization of cruaZitz~ eantroZ for Al?~'S service. The organization of
- observations of service quality and the measurement of the parameters of
long distance telephone messages are complex techn3cal problems, the solu~~ The
- spin device is understood to be a multifunction parametric device. -
It is shown that the spin device, which operates using a dual pulse proce-
dure, can be equated with a signal spectrum analyzer under certain condi-
tions�
UDC 621.376.239
THE I'VFLUENCE OF LOCAL IZED STATES ON THE PROPERTYES OF METAL-INSULATOR-METAL
_ TUNNEL STRUCTURES
[Abstract of article by Zhgun, S. A. and Shtykov, V. V., pp 16-19]
[Text:] An accounting is made of the influence of localized states on the
- proper ties of the volt-ampe~e characteristic of inetal-insulator-metal struc-
_ ture;;, By using a method of expansion in a Maclaurin series, it is shown
= that some experimentally observed features of the coefficients of the series
_ can be due t~ impurities and defects in the crystalline structure of the
dielectric.
: UDC 621.371:551.510.535
A NCI;IERICAL SJLUTION OF THE PROBLEM OF RADIO WAVE PROPAGATION IN AN INHOMO- "
GENF:OUS MAGNETICALLY ACTIVE ME??IiJM
[Ab;stract of article by Kramm, M. N. and Filonov, S. V., pp 20-�23]
[Te:Kt] A transmission matrix apparatus is used to determine the wave which
has passed through an inhomogeneous layer. The results of the calculations
- are represented in the form of curves f or the transmittance factor as a
, function of the magnitude and direction af the external permanent magnetic
fie]!.d and the layer thickness. .
65 -
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UDC 621.384.6
- A FUNDAMENTAL SOI.UTION OF THE INTEGRAL EQUATION FOR THE DENSITY DISTRIBU-
' TION OF A SPACE CHARGE IN THE PROBLEM OF THE INTERACTION OF A STRONGLY
MODULATED CHARGED PARTICLE BEAM AND THE SYNCHRONOUS HARMONICS OF A MICRO-
WAVE FIELD
[Abstract of article by Balashov, V, N., Gavich, V. T. and Zhileyko, G. I.,
pp 24-26] -
[Text] A method of solving the integral equation wr~ich relates the density
distribution of a space charge to the external electrical field is given.
, Special cases of the solution are also given. -
UDC 621.384.6
A C,OMPARISON OF ANALYT3~;AL AN~ ~.JMERICAL INTEGRATIONS OF PHASE EQUATIONS
FOR THE PROCESS OF THE INTE~'iACTION OF CHARGES WITH AN ELECTROMAGNETIC FIELD -
[Abstract of article by Azizbekyan, f;. V., Sveshnikova, N. N, and Zhileyko,
G. I., PP 27-29)
[Text] It is shown that the errors in calculations using analytical formu-
las and a numerical method for the process of the 9_nteraction of clusters
= of electrons with a~ electromagnetic field, taking into account the space
charge, fall in a range of 10 percent.
- UDC 621.376.019.4
OPTIMAL NONLINEAR CONVERSION IN A PHASE KEYING RECORDING AND CARRIER RESTORA-
TION CIRCUIT
[Abstract of article by Bezuglyy, V, V. and Zhukov, V. P., pp 29-34] _
- [Text] Characteristics of nonlinear elements which are optimal in terms of
. a signal to noise ratio criterion are determined. The maximum signal to -
. noise ratios in circuits with optimal characteristics are computed.
UISC 62i.396.668
THE STATISTICAL SYNTHESIS OF THE P~IRAMETERS OF A DUAL CHANNEL ITERATIOV =
PHASE LOCKED LOOP SYSTEM
[Abstract of article b_y Samoylenko, V. N., pp 34-38]
[Text] The optimal parameters of a dual channel phase locked loop system
are determined on the basis of the criterion of a minimum mean square err.or.
66 -
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= FOR OFFICIAL USE ONLY
_ UDC 621.391.22/23
- THE DETERMINATION OF THE PERMISSIBLE PRECISION IN THE EXECUTION OF AN
_ ALGORITHM FOR AN OPTIMUM RECEIVER OF BINARY SIGNALS
[Abstract of article by Arapov, S. M., pp 38-42]
_ [Text] A two-step procedure is proposed for the determination of the per-
missible precision in the realization of an optimal receiver algorithm,
- where the procedure is based on the introduction of the concept of the
equivalen~ shift in the threshold of a resolver. The permissible error
probability and the requirement of minimal receiving systeni cost are used ~
as the optimization constraiats. An expression is derived for the determina-
tion of the relative tolerance of the receiyer parameters.
UDC 621.396.677.3
THE EXCIT~TION OF A CYLINDRICAL RESONATOR WHERE A DIELECTRIC SOLID IS
PRESENT IN IT -
- [A~strac~ of article by Vasil'yev, Ye. N, ax~d Kapustin, Yu. G., pp 43-47]
- [Text] A system of integral equations for a dielectric axially symmetric
~ solid in free space relative to the surface electrical and magnetic cur- -
, rents is geiieralized for the case where the dielectric solid is placed in-
side a c~l.indrical resonator~ Th~ nuclei of the new integral equation dif-
fer f~rom the original ones in the existence of an additional term, which ,
has no singularities.
' UDC 621.396.6i7.3
AN INTEGRAL EQUATION FOR THE PROBLEM OF INTERNAL AY.;7ALLY SY1~IlrIETRIC DIFFRAC-
- TION AT A DIELECTRIC SOLID
[Abstracr of article by Kapustin, Yu. G. and Kovalenko, A. I., pp 47-52J -
[Text] The problem of d~termining the fields of a resonator perturbed by a
dielectric, axially symmetr~^. solid is treated. A planar non-self-adjoint
boundary problem is formulated with respect to the Abraham potential for �
- the E mode. A boundary problem, formulated using Green's theorem, which
adjoint to the other boundary problem, is defined. A system of integral
Friedholm equations of the second kind is written. An expression is given -
for Green's function for the problem of a circular cylindrical resonator.
67
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\
UDC 621.396
THE DIFFRACTION OF A PLANE WAVE AT A DIELECTRIC CYLINDER
, [Abstract of article by Sedel'nikova, Z. V., pp 52-55] `
[Text] The problem of electromagnetic wave diffraction at a dielectric
cylinder is reduced to an integral equation fnr the density of the surface .
- electrical and magnetic currents, whicl~ can be solved numerically. An ex- _
ample of the calculation of the excitation of a dielectric cylinder by an -
electrical dipole perpendicular to its axis is given.
. UDC 538.569:621.396.1
_ A NEW APPROACH TO THE CALCULATION OF THE CHARACTERISTICS OF ELECTROMAGNETIC
WAVE SCATTERING AT A TWO-DIMENSIONALLY INHOMOGENEOUS CYLINDER WITH AN
ARBITRARY CROSS-SECTION
- [Abstract of article by Kuvayev, V. M. and Permyakov, V. A., pp 56-60]
[Text] A new method of determining electromagnetic waves scattered by a
two dimensionally inhomogeneous cylinder is proposed with utilizes a method
- of straight lines for calculating the fields inside the inhomogeneous solid _
and an analytical extension of the external field at the surface of the
~ solid.
UDC 538.569:621.315.592
ON USING SEMiCONDUCTORS TO MODEL NONLINEAR MICROWAVE EFFECTS IN A GAS PLAS~tifA
_ ~Abstract of article by Korneyeva, T. M., Permyakov, V. A., Slezkin, V. G.,
Steshenko, A. G. and Fedesov, G. Ye., pp 61-66~
- [Text] The possibility of using semiconductors to model the self-stress of
a high power microwave field and the generation of the third harmonic, which
- arise in a gas collision plasma, is treated. The normal incidence of a _
plane microwave pulse on a plasma is described in the framework of element-
ary theory. The results of waveguide experiments with thin plates of sili-
con and modes where they are arranged transversely are given [sic].
68
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UDC 538.569 -
- THE COMPUTER CALCULATION OF THE PARAMETERS OF A DISPERSING MIDIUM USING
- BRIIr1ERMAN' S METHOD
- [Abstract of article by Finat'yev, Yu. P. and Tsel'sov, Yu. G., pp 67-68]~
[TextJ The determination of the equilibrium chemical composition of the
- medium is reduced to the solution of a system of nonlinear algebraic equa-
tions. This system is solved by means of minimizing a function of several
variables. It is shown that this is accomplished most eff iciently using
Bremerman's iterations.
_ UDC 621.371.332.4.001.5
SPECIAL FEATURES OF AURORAL COMMUNICATIONS LINKS
_ [Abstract of article by Bubennikov, S. V. and Volovskiy, V. N., pp 69-72] _
[Text] The special features of auroral cammunications links at frequency
of 144 MHz during the years of the "quiet" sun are treated on the basis of
processing experimental material. The range of reflection for moderate
and strong auroras is plotted and examples are given of two-way radio com-
' munications where one of the stations is located in Moscow.
UDC 538.574.6
, THE DIFFRACTION OF A PLANE E-WAVE AT A SLOT BETWEEN TWO SEMT-INFINITE
DIEI,ECTRIC PLAtES
[Abstract of article by Vasil'yev, Ye. N., Polynkin, A. V. and Solodukhov, -
V. V., pP 73-79J
- ~Text] The problem of the excitation of a plane electromagnetic wave of a
slct between two semi-infinite dielectric plates is solved numerically using
integral equations with respect to the equivalent surface currents. The -
amplitudes of the excited natural waves of the plate -~ere studied as a func-
tion of the slot size and angle of incidence of the plane wave. -
UDC 621.371 : 551.510.535
_ ON THE DEPOLARIZATION OF ELECTROMAGNETIC WAVES WHEN REFLECTID FROM A
MAGNETICALLY ACTIVE LAYER OF AN IONIZED MIDIUM WITH A METAL BASE
[Abstract of article by Kramm, M. N. and Goncharov, V. L., pp ga_g(~
[Text] A numerical method o~ computing the backscatter matrix elements is
proposed for the case of an electromagnetic wave which is normally incident
to a plane layered magnetically active ionized medium. Attention is turned
69
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- to the process of the transformation of wave polarization when reflected
from the magnetically active ionized medium, which is characterized by the
coefficients of the backscattering matrix, which are located outside the
m~in diagonal (by the depolarization coefficients). The results of the _
calculations are presented in the form of the depolarization coefficients
_ expressed as a function of the ratio of the gyro-frequency of the electrons
to the wave frequency.
UDC 621.382.323
SIGNAL QUANTIZATION NOZSE IN A CHARGE COL`PLED DEVICE WITH OPTICAL INPUT -
[Abstract of article by Zhurikhin, A. V., pp 86-88]
~
[TextJ For the case of the optical input of a signal into a CCD (charge
- coupled device), formulas are derived for the calculation of the signal
quantization noise dispersion based on the known energy spectrum of this =
_ signal.
- COPYRIGHT: Moskovskiy energeticheskiy institut, 1979
[237-8225]
- 8225
CSO: 1860 "
~ 70
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_ UDC 621.382
CONTROL IN MICROELECTRONiC TECANOLOGY
Minsk KONTROL' V TERHNOLOGII MIRROELEKTRONLRI [Control in Microelectronic
Technology] in Russian 1979 signed to press 20 Jun 79 p 2, 311-312
[Annotation and table of contents from book by V. M. Koleshko, P. P. Goyden-
ko, and L. D. Buyko, Nauka i tekhnika,..1475 copies, 312 pages]
" [Text] The authors describe modern problemSOf the theory and practice of
methods for controlling the defects of crystal lattices and electrophysical
properties of multilayer structures during various stages of manufacturing
semiconductor devices and integrated microcircuits. Th~y give the data and
practical recommendations for controlling the surfaces, structure, and pro- ~
perties of thin films and phase interfaces of the metal-semiconductor and
metal-dielectric-semiconductor contacts with the use of modern physical re=
~ search methods.
They examine physical methods of quali*y control of microwelding and solder-
- ing of integrated microcircuits, as well as the p~oblems of optimization
and automation of the control of technological processes with the use of in-
~ formation on the qual.ity of multilayer structures.
The book is intended for broad sections of scientists, engineers and tech-
nicians of enterprises and design and research organizations of the radio
and electronic industry, and can be useful for instructors and graduate and
undergraduate students specializing in microelectronics.
Tables 23, figures 108, bibliography 736 items.
Contents
Page
- Foreword 3
Chapter I. Main Stages of the Manufacturing and Controlled -
Parameters of Multilayer Semiconductor Structures ,5 -
1, Preparation of SubsCrate Surfaces and Epitaxial Growing
of Thin Films 6
2. Growing Dielectric Substrates in Epitaxial-Planar
Technology 12
71
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3. Diffusion and Ion Implantation in Silicon 16
4. Creation of Multilevel Metalization of BIS [Large-Scale
Integrated Circuits] 18
5. Assembly of Tntegrated Microcircuits 21 -
Chapter II. Control of the Parameters of the Surface and the
Transition Layers ir; the Film-Substrate Contiact 26 -
1. Control of Deformation and Residual Stresses in Semi-
conductor Structures ; 27
2. Methods of the Analysis of the Atomic Structure, Chemical
Composition, and Electronic Properties 39
_ Chapter III. Control of Electrophysical Parameters of Semicon-
ductor Layers 68
1. Control of the Thickness of a Monocrystal of Silicon
- Structures with Dielectric Insulation (RSDI) 68
2. Interferometric Method of Measuring the Thickness of
Epitaxial Layers 84
3. Control of the Thickness of the Epitaxial Layer of Silicon
on Sapphire (KNS) by the E1lipsometric Method in the -
Visible Region of the Spectrum 90
4. Measuring the Specific and Surface Resistances of
Epitaxial Structures wi~h Hidden Diffusion Regions 93
5. Determination of the Surface Resistance of Thin
Diffusion Layers by the Reflection of Infrared Radiation 112
Chapter IV. Control of Parameters of I~IDP [Metal-Dielectric-
Semiconductor]-Structures 118
1. Measurement of the Thickness.and Speed of Etching of
Dielectric Films at Various Stages of Integrated
Circuit Production 120
2. Fundamentals of the Theory of the C-V-Method 136 -
3, ftigh-Frequency C-V-Method 151 _
4. Low-Frequency C-V-Method 160
5. Pulsed C-V-Method 168
6. Temperature Measurements in the C-V-Method 181
Chapter V. Control of Parameters of the Metal-Semiconductor
Contact 184
1. Physical Parameters 184
2. Electrical Parameters i`~9
3. Optical Parameters 202
4. Mechanical Parameters 2'~~3
5. Mass Transfer of Substance in Thin-Fi1m Conductors 209
Chapter VI. Quality Monitoring and Controlling the Assemb~y
Process of Integrated Microcircuits 224
1. Quality Monitoring and Controlling the Processes of
Microwelding and Soldering by the Electrical Parameters
- of the Joint 224
72
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2. Quality Monitoring and Contro~ling the Processes of -
Micraweld ing and Soldering by the Acoustic Character-
isticsof the Joint
241
3. Quality Monitoring and Controlling the Processes of
Microwelding and Soldering by Che Therma.l Character-
istics of the Joint
250
- 4. Quatity Monitoring and Controlling the Pr~cesses of
Micrawelding and Soldering by Changing the Parameters
of the Equipment 256
5. Quality Monitoring and Controlling the Process of Laser -
Microwelding 265
6. Quality Monitoring and Controlling the Process of Elec-
tron-Beam Microwelding 270
7. Quality Monitoring and Controlling the Process of Plasma
Microwe ld ing 2~2 _
_ Chapter VII. Opt imiza~~ion and Automatic Control of T echnological
Processes 2~4
1. Optimizat ion of the Technological Process of the Grow~ing
and Etching Dielectric Films 2~4
2. Optimizat ion of Thermodiffusion Technological Processes
in Obtaining Semiconductor Structures 2g2
3. Automated Control Systems for Technological Processes 291
Bibliography 293
COPYRIGHT: Izdatel'stvo "Nauka i tekhnika." 1979
[269-10, 233] ~
10,233
CSO: 1860
73
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r~n urrl~ieu. uan v,.Li
LASER BEAMS, COLLECTTON OF ARTZCLES ANNOUNCED _
Gor'kiy IZVESTIYA VYSSHIKH UCHEBNYKH ZAVEDENIY, RADTOFIZIKA in Russian
No 4, 1980 pp 507-508 .
[Annotation, table of contents and supplementary information for inter-WZ
collection of articles "Lazernyye puchki" [Laser Beams] edited by N.K.
Berger, Izdatel'stvo Khabarovskogo Politekhnicheskogo Instituta, 1579] _
[Text] In this collection are published articles devoted to investiga-
tion of the space-time structure of laser radiation and to the formation
of this structure by means of active resonators and optical systems.
Spec.ial attention is paid to questions relating to the active contro 1 of
the space-time structure of laser radiation, i.e., to adaptive optic s,
wave front reversal, etc. -
;
CONTFSTTS
_ Kol'chenko, A.P., Nikitenko, A.G. and Troitskiy, Yu.V. "Inhomogeneous
Mirrors as a Means of Analyzing the Transverse Modes of an Opt3cal
- Resonator," USSR Academy of Sciences Siberian Division Institute of
Automation and Electrometry.
Bel'tyugov, V.N. "Calculation of the Selective Properties of a Resonator
with a Reflecting Grating," USSR Academy of Sciences Siberian Divis ion
Institute of Automation and Electrometry.
Karamzin, Yu.N., Sukhorukov, A.P. and Sukhorukova, A.K. "Generation of
Emission at the Difference Frequency by Means of Powerful Focused Beams,"
- USSR Academy of Sciences Institute of Applied Mathematics, Moscow S t ate
University, Moscow Institute of the National Econoray. _
Belonuchkin, V.Ye., Kozel, S.M. and Lokshin, G.R. "Square-Law Dete ction
_ in Problems of the Space Filtering of Coherent Beams," Moscow Physi co-
technical Institute.
74 -
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_ Kuzyakov, B.A. "Breadth of the Frequency Tuning Line of a Waveguide C02
Laser in the Dynamical Mode," USSR Academy of Sciences Moscow Institute of
Radio Engineering and Electronice.
Alekseyeva, L.L. and Tuchin, V.V. "Resonance Phenomena in Modulating
- the Pumping of a CO Laser," Saratov State University Scientific Research
~ Institute of Mathematics and Physics.
_ Rabino~ich, E.M. "Some Aspects of the Formatio;~ of Higher-Order Modes
_ in Inhomogeneous Laser Resonators," Saratov State University Scientific
Research Institute of Mathematics and Physics.
- Tagiyev, Z.A. and Chirkin, A.S. "Space-Time Structure of the Second
Optical Harmonic; Nonstationary Generation of Harmonics by Means of a
Powerful Field," Moscow State univ~rsity, Azerbaydzhau State University -
Kristallov, A.R. "Influence of the Spatial Distribution of Excitation
Density on the Output Characteristics of a Three-Mode Gas Laser,"
Saratov State University Scientific Research Institute of Ma.thematics and ~
Physics.
Mel'nikov, L.A. "Theory of a High-Gain Laser, Taking Cross Relaxation
into Account," Saratov State University Scien~ific Research Institute of
_ Mathematics and Physics
Lokshin, G.R. "Inverse Problem of the Theory of Qpen Resonators,"
Moscow Physicotechnic3l Institute.
Akchurin, G.G. "Stable Ztao-Wave He-Ne Laser (a = 0.63 and 1.15 u) for
Purposes of Geodesy and Interferometry," Saratov State University Sci- _
entific Research Institute of Mathematics and Physics.
Stol'nits, M.M. "Resonator Modes of a waveguide Gas Laser wifih a Wave- -
" guide c~rlth a Rectangular Cross Section: Matching Losses and Distribution
_ of Intensity in the Close-Range and Remote Zones," Saratov State Universi-
ty Scientific Research Institute of Mathematics and Physics.
Makhnev, V.P, and Telegin, G.G. "Change in the Statistical Properties of
Light in the Processes of Intensification and Absorption," USSR Academy of
5ciences Siberian Division Institute of Automation and Electrometry.
Tuchin, V.V. and Chetverikov, V.I. "Technical Fluctuations of the Fre-
quency of a Three-Mode Gas Laser in the Self-Synchronization Mode," -
Saratov State University Scientific Research Institute of Mechanics and
Physics.
Berger, N.K. "Some Questions Relating to Symmetry of the Field in the
Resonator of a Laser with Spatially Inhomogeneous Gain," Khabarovsk Poly-
technical Institute.
75
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L' Vl\ V1'L' LV 1L1L UJL' Vl\LL
~
I~
I
Lukin, I.P. "Distribution of Mean Intensity in the Focal Plane of a ;
Lens," USSR Academy of Sciences Sib erian Division Tnstitute of Atmospheric -
Optics.
I1'in, A.V. and Kozel, S.M. "Influence of Transverse Inhomogeneity of I
Inversian on Modes of Waveguide Lasers and Amplifiera," Moscow Physico-
technical Institute.
I
Stroganov, V.I., Illarionov, A.I. and Samarin, V.I. "Conversion of
Incoherent Radiation in an Infrared Vidicon with a Nonlinear Crystal," ,
~
- USSR Academy of Sciences Siberian Division Institute of Automation and ~
Electrometry. I
Zhukov, A.F., Lukin, I.P. and Tsvyk, R.Sh. "Investigation of the Internal
Scale of Turbulence," USSR Academy of Sciences Siberian Division Institute
of Atmospheric Optics.
Dubrovskiy, V.A. and Kolotyrin, A.A. "Influence of the Spatial Dimensions
- of an Electron Beam Laser on Its Energy Characteristics," Saratov State
University Scientific Research Institute of Mathematics and Physics. _
- Gavrilov, D.N. and Rabinovich, E.M. Automatic Registration of the
. Spatial Position of a Collimated Laser Beam," Saratov State Univer.sity
Scientific Research Institute of Ma.thematics and Physics.
This collection is sent C.O.D. Orders are to be sent to the following
address: 680035, Khabarovsk, ul. Tikhoekeanskaya, 136, Polytechnical
Institute, A.I. Kaminskiy, Pro-Rector for Scientific Work.
Publ.ication of the 1980 collection is planned for the third quarter of
= 1980. The issue of the 1981 collection is being put together at this
time. The deadline for the submission of articles is 20 Dec 80.
Articles for publication are to be sent to the following address: 680035, ~
Khabarovsk, ul. Tikhookeanskaya, 136, Polytechnical Institute, Quantum
Radiophysics Laboratory, "Lazernyye puchki" Editorial Office.
COPYRIGHT: IZVESTIYA VYSSHIKH UCHEBNYKH ZAVEDENIY, RADIOFIZIKA, 1980
[246-8831]
8831
CSO: 1s60
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r _
LINES OF COMMUNICATIONS
- Moscow LINII SVYAZI in Russian 1980 signed to press 25 Dec 79, p 2, 437-440
[Annotation and table of contents from book by Igor' Izmaylovich Grodnev
and Nikolay Dmitriyevich Kurbatov, Izdatel'stvo "Svyaz," 20,000 copies,
439 pages) .
Annotation
[Text] This book examines the principles of constructing -
_ mainlir~e, zonal and local communications networks. It cites
the designs, characteristics and electrical parameters of vari-
ous guid~ systems (symmetrical and coaxial cables, waveguides, =
- light guides, optical and superconducting cables, etc.). It -
outlines the th~ory of transmission through guide systems and -
- also the theory of the reciprocal and external influences and -
measures for shielding from them. The third edition was pub-
lished in 1974. New material is devoted to the planning, con-
struction and operation of the communications facilities.
The text book is for students in communications institutions of
_ higher learning, who are studying the specialities of multi-
channel and automatic electric communications.
Table of Contents
Introduction ........................................o..... 3
Chapter 1. Modern Electrical Communications and Build-
ing Electric Communications Networks 5 -
_ 1.1 Basic trends in the development of modern
communications 5
1.2 Systems for building Soviet communications
n~tworks .........................o................... 10 -
1.3 Systems of multichannel transmission through
lines of communications 14
1.4 Principles of building long distance communi- _
- cations on lines of communications ................a.. 16 -
1. 5 9asic req!:i~ emer~ts of ] ines of communications 20
1.6 Brief review of the development of lines
of communications 21
~ 77
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Chapter 2. Designs and Characteristics of Lines of
Communications ?2
Cable Lines of Communications 22
2.1 Classification and marking of lines of
commun.ications 22
2~2 Cable conductors 25
2.~ Di~electrics used for cable insulation 27
2.4 Fo~mation of groups in symmetrical cables 30
2.5 Composition of the core of a cable 32 ~
2.6 Shi~lding covers 34
_ 2.7 Armored coverin gs 37
2.8 Long-dist2nce coaxial cables . . . . . . . � � � � � � � � � � � � � 38 _
2 .9 Long-distance symmetrical cables � . . � � - � � � � � � � � � � 44
2.10 Zonal (interoblast) cables ...................e.. 48
2.11 City telephone cables 51
2.12 Cab~es for rural communications 53 ~
2.13 Underwater cab~.es 55
2.14 Cable armature, equipment and line facilities 61
Overhead Lines of Communication s......... 62
2.15 Types of overhe,;d lines of communications 62
2.16 Basic line mateiials 62
2.17 Cross sections a; lines 65
2.18 Types and designs of supports 65
- 2.19 Electrical characteristics of the circuits of
- overhead lines of communications 65
Chapter 3. Theory of the Propagation of Electromagnetic
Energy through Guide Systems 69
_ Electrical Dynamics of Guide Systems 69
= 3.1 Guide systems and their classification 69
3.2 Types and classes of electromagnetic waves 73
3.3 Physical processes in guide systems 74
_ 3.4 Basic hypotheses of the electrical dynamics of .
- guide systems 78 -
3.5 Initial principles for rating guide sy stems 87 _
_ Theory of Transmission through Lines of
- Communications (Quasi-stationary mode) . . . . � 88
- 3.6 Equation of homogeneous line 8~
= 3.7 Wave resistance 90
3.8 Coefficient of propagation 91
3.9 Dependency ~f secondary parameters upon fre- _
quency 93
3.10 Speed of propagation of electromagnetic energy
through communicatians circuits .........e............ 95
3.11 Properties of dissimilar circuits 95 -
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Chapi;er 4. Theory of Guide Systems 98
_ Coaxi.al Cables . . . . . . . . . , . . . , , . , , 98
- 4.1 Electrical processes in coaxial circuits 98
4.2 Electromagne:,ic field of a coaxial circuit 102 ~
+.3 En~rgy transmission through an ideal coaxial
_ circui * . . . . . . . . . . . . . . 103 -
4�.4 Energy transmission.through�a.coaxial.circuit
with cc~nsideration of losses in conductors 105
4~5 Capacity and conductivity of the insulation of -
r coaxial circuits . 110
4.6 Secondary parameters�of.the transmission of
c~~axial circuits 113
4.7 Most advantageous ratio of the diameters of
- the conductors of ,a coaxial pair 115
4.8 Design dissimilara.ties in coaxial cables 117
Symmetrical Cables . . . . . . . , . . . . . ~ . . 120 -
4.~ Electrical p;:ocesses in symmetrical c~rcuits . 120
4.10 Energy tran smission through an ideal symmetrical
~ circuit 122
4.11 Energy transmission through symmetrical circuit ~
consbdering losses 124 -
4.12 Capacity and conductivity of the insulation of
_ symmetrical circuits . . . . . . . . . . . . . . . . . . . ~ . , . . . , . . . 127
4.13 Parameters of symmetrical screened cables 129
4.14 Parameters of the circuits of overhead lines of
communications 131
4.15 Basic dependencies a~~ secondary parameters of
_ symrr~etrical circuits 132
4.16 Secondary parameters of symmetrical circuits 133
- Cables with Artificially Enhanced
Inductance 134
4.17 Need for artificial enhancement of inductance
of communications ~ables . . . . 134
4.18 Pupinization of cables 135
, 4.19 Other ways to enhance the inductance of commun-
- ications cables . . 138
_ Superconducting Cables . . . . . . . . . . . . . . . . . 139
4.20 Initia.l hypotheses 139
- 4.21 Superconductor:� and diPlectrics at cryog~nic
_ temperatures . 140 '
4. 22 Tltieory and ~electrical ~ rating of superconducting
- cables . . . . . . . . . . . . . . . . . . . . . . . . . . e . 144
4.23 Design and electrical characteristics of super-
- cor,ducting cables 147 -
_ 4.24 Cryogenic devices of lines of communications 149
_ 79 ~
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~Naveguides 152
- 4.25 Physical processes ocurring in waveguides 152 -
_ 4.26 Classification and structure of waves in
- waveguides 155
4.27 Special features of a HOl.wave in a cylindrical
waveguide 155
4.28 Electromagnetic fields in waveguides 1~8
4.29 Critical wave lengths and frequencies of
waveguides 161
4.30 Characteristic parameters of waveguides 162
~ 4.31 Attenuating of energy in waveguides 164
: 4.32 Rating of spiral waveguides 165
4.33 Design of a cylindrical ~aveguid~ 166
_ 4.34 Systems for transmitting through waveguides,
qualities and shortcomings 168
Optical Cables 169 =
- 4.35 Initial hypotheses 169
4.36 Lens lightguides 171
4.37 Physical processes in fiber lightguides 173
4.38 Basic equation for transmitting through a
_ lightguide 175
4.39 Critical frequencies and waves of lightguides. 179
4.40 Types of waves (modes) in lightguides 182 ~
4.41 Attenuation and wave resistance 182
- 4.42 Speed of propagation of energy in lightguides. 184
- 4.43 Influencing parameters in optical cables 186
4.44 Range and frequency range of transmitting
through an optical cable 189 -
4.45 Optic-~l cables and their installation 190
4.46 Systems fo~ transmitting througP~ optical =
cables 192
~ 4.47 Comparison of different guide systerns and
' prospects f~r their development 195
Chapter 5. Theory of Reciprocal Effects Between the Circuits
of Communications ancJ Measures for Shielding 202
Reciprocal Effects and Noise Immunity of
Communications Circuits 202
5.1 Causes of reciprocal effect betwet.:n communica-
- tions circuits and basic parameters ~f effect 202 -
5.2 Basic equation of ~ffect between cir~uits 208
5.3 Hodographs (frequency dependencies) of electro-
magnetic communications 212
_ 5.4 Dependencies of the transfer attenuation upon
the length of the line and frequency 215 ~
_ 5.5 Indirect effects between circuits 218
- 5.6 Norms of transfer attentuation between circuits 222 .
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~ Effects in coaxial cables 224
5.7 Nature of effect in coaxial cables 224
5.8 Resistance of communications 227
5.9 Transfer attentuation between coaxial cir-
cuits 229
5.10 Measures for shielding from reciprocal
effects 232
- Crossing of circuits of overhead lines of
communications 233
5.11 Principles of crossing 233
5.12 Basic rules of compiling crossing diagrams 236
5.13 Efficiency of crossing 238 _
5.14 Resultant transfer attenuation at rear and
far ends of the line 240
5.15 Design execution of circuit crossing 241 -
Sp?icing Cable Circuits 243
- 5.16 Basic hypotheses for cable splicing 243
5.17 Rating of coordinated steps of splicing 246
Symmetrization of Communications Cables 247
5.18 Methods of symmetrization 247
5.19 Symmetrization of low-frequency cables 249 ~
5.20 Symmetrization of low-frequency cables using
_ crossing 249
5.21 Symmetrization of low-frequency cables with
condensors 252 -
5.22 Stages of symmetrization of low-frequency
cables 7.53
5.23 Symmetrization of high-frequency cables 255 _
5.24 Concentrated symmetrization of high-frequency
cables using compensating contours 256 =
5.25 Symmetrization of high-frequency cables
according to shielding characteristics 258
- 5.26 Symmetrization of high-frequency cables
~ accarding to comprehensive communications 259
5.27 Stages of symmetrization of high-frequency
- cables 262
5.28 Raising the shielding of cable circuits on ~
the OUP -OUP (manned repeater poi:~t) sector 263
Screening of Cable Communications 267
5.29 The use of screens 267 ~
5.30 Principles of screening in a broad frequency
_ range 268 -
8~
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5.31 Electromagneticstatic screening 271
5.32 Electromagnetic screening 273
5.33 Wave mode of screening 276
5.34 Principle of the effect of magnetic and non-
magnetic screens 278
5.35 Comparison of the screens of various designs 280
5.36 Screeiing effect considering effects of
third circuits 281
5.37 Principle of action of multilayer screens 283
5.38 Screening characteristics of multilayer
screens 284 _
- Chapter 6.Shielding of Communications Facilities from External
Effects and Corrosion 287
Theory of Effect 287
6.1 Physicai nature and sources of electromagnetic
effects on communications circuits ..e............ 287
6.2 Types and ~lassification of external effects 289
6.3 Effect of atmospheric electricity 291 _
6.4 Effect of electric transmission lines 294 -
6.5 Effect of electrified railroads 296 -
6.6 Special features of the effect on overhead
and cable communications lines 297
6.7 Norms of dangerous a~~d hindering effects 298
6.8 Rating of dangerous electrical effect 300
6.9 Rating of dangerous magnetic effect 301 _
6.10 Rating of hindering effects 303
_ 6.11 Effect of radio stations on cammunications
lines 304 -
Shielding Communications Facilities 307
- 6.12 Shielding measures for communications facili-
ties fromexternaleffects 307
6.13 Diagrams of shielding, dischargers and
protectors 307
6.14 Cascade shielding and lightning rods 310
6.1: Storm protectiong lines 311
6.?6 Screening 312
- 6.17 Reduction transformers 312
6.18 Exhaust transformers and loops 31~
- 6.19 Grounding device 314
Corrosion of Cabie Coverings and Measures -
for Protecting 315
= 6.20 Types of corrosion 315
82
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0.21 Soil electrochemical corrasion 316 '
0.22 Intercrystalline corrosion 318
6.23 Electrical corrosion 318
6.24 Rating of potential and flows ocurring on the
cable covering Prom impinging currents 319
6.25 Measures for protecting from corrosion 321
6.26 Electrical drainage 322 -
_ 0.27 Cathode stations 323
- 6.28 Protective installations 324
6.29 Passive protective devices 325
_ 6.30 Measurements of the potential ona cable co-
vering and a KIP (surface use coefficient) device.. 326 -
Chapter 7. Designing Communications Networks ......e... 328
- 7.1 General hypotheses 328
Long Distance Lines 329
7.2 Tasking for planning 329
7.3 Technical plan 329
7.4 Blueprints . 331
7.5 Selectian of~type of line for planned mainline 332
- 7.6 Selection of path for construction of line 334
7.7 Locating the repeater points 335 -
Lines for City Telephone Communications 337~
~
7.8 System for building city telephone networks 337
7.9 Composition of technical plan 341
7.10 Distribution of subscribers throughout the
� city and selection of locations of stations 3 41
' 7.11 Selection of capacity of case and planning of
the distribution network of the city telephone
system 342
7.12 Designing the mainline cable network and
_ channel allocation of the city telephone system 345
7.13 Multichannel connecting lines of the city .
- telephone system 347
Lines for Rural Communications 348
,
7.14 System for building rural telephone networks. 348
~ 7.15 Composition of the technical plan............ 349
7.16 Selection of transmission system, type o~
_ line and equipment 350
7.17 Technical and economic Justification of plan. 352
- 83
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Chapter 8. Construction of Facilities for Lines of
Communications 354
8.1 General information concerning the organiza-
tion of construction 354
Cable Lines of Communications 355
S. 2 t~lechanism used when constructin g cable lines 355
8.3 Laying underground armored cable 360
8.4 Cable canalization 363
8.5 Cable laying in a ditch 367
8.6 Laying underwater cables 369 _
8.7 Laying a cable ac.ross a bridge, building walls
and the suspension on supports of overhead lines of
communications 371 -
8.8 Installation of communications cables......... 373
- 8.9 Input devices of overhead cable lines 386
Overhead Communications Lines 387
_ 8.10 Basic kinds of work for the construction of
overhead communications lines 387
8.11 Mechanisms usea when construction overhead
communications lines 392
8.12 Input devices of overhead communications line. 394
8.13 Safety equipment when performing line work 394
Chapter 9. Fundamentals of operating line communications
- facilities and their reliability 397 _
Technical operation 397
9.1 Organization of the operational servicing of
communications lines 397
9.2 Technical maintenance of line facilities 398 _
- 9.3 Autamation and technical servicing of cable
- mainlines 399
- 9.4 Unattended repeater point devices and princi- _
ples of organizing the long distance power supply
on cable mainlines 401
9.5 Electrical measurements 407
9.6 Determinirig location of damage on communica- _
tions lines 408 -
_ 9.7 Maintaining cables under excessive gas
pressure ........................o................. 415
- Reliability of Cable Communications Lines 420 _
9.8 Concept of reliability of .,ommunications lines 420
04 -
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9.9 Parameters of reliability 420
9.10 Evaluation of reliability 422
9.11 Basic factors affecting the reliability of =
cable communications lines 423
9.12 Rating of the reliability of cable communica-
tions lines 425
9.13 Me~sures to increase the reliability~of cable
communications lines 426
Appendix 1 428
Appendix 2 429 `
Appendix 3 430
Bibliography 435
- CUPYRIGHT: Izdatel'stovo "Svyaz"', 1980
[2~o-s92~~
8927
CSO: 1860
85 ~
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UDC 621.3.049.77.002(075)
PRODUCTION TECHNOLOGY FOR MICROELECTRONIC DEVICES
Moscow TEKHNOLOGIYA PROIZVODSTVA MIKROELEKTRONNYKH USTROYSTV in
Russian 1980 signed to press 15 Feb 80 pp 442-447
[Title, annotation, and table of contents of a book by Ideya =
Aleksandrova Malysheva, Energiya, 15,000 copies, 448 pages]
[Text] This book give a general description of the production
_ of microelectronic devices,~and over-a11 production require-
ments are formulated. The basic technological methods and pro-
cesses described include mechanical working, cleaning the sub-
_ strate surface, photolithography, the free mask method, x-ray
and electronic lithography, film deposition methods, epitaxy,
diffusion, and ion doping. Typical manufact.uring processes for
bipolar and MDS microcircuits and for thin-film and thick-film
microcircuits are analyzed. Assembly and sealing processes,
problems connected with ensuring quality and efficiency, and
- trends in the future development of microelectronics are con-
sidered. -
This book is designed as a textbook for students in techr,ical
schools specializing in the production of microelectronic
devices, ~
_ Table of Contents _
_ Foreword 3
Introduction 5
- Chapter 1. General Description of M~,crocircuit Production 9
1..1. Hasic concepts 9
1.2. Classification and general characteristics of ~
microcircuits 12
1.3. Development of technologX and techniaal documen-
tation for microczrcuits 15
1.4. Easic processes for IC production technology 19
Test problems and assignments 26
86
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Chapter 2. General Requirements ~or Microcircuit
Production 27
2,1. General requirements for the technologi.cal
process 27
2.2. Requirements for the purity o~ an air medium and
environment parameters 29
2.3. Requirements for pxocessed gases and water 35 -
2.4. Basic principles of electron-vacuum hxgiene 39
2.5. Basic features of microcircuit production 40
Test questions ar_3 asignments 42
Chapter 3. Manufacture of Semiconductor Plates and Dielec-
tric Substrates for Microcircuits 43
3.1. General information on the mechanical working of
semiconductors and dielectrics for IC's 43
3.2. Abrasive cutting 46
3.3. Grinding and polishing of blanks for IC structures5l
3.4. Monitoring of plates and substrates after mechan-
~ ical working ~ 55 ~
- Test questions and assignments 58
_ Chapter 4. Chemical Working and Cleaning of the Surfaces
of Semiconductor Plates and Substrates 60
4.1. General information 60
- 4.2. Methods for fluid working of plates and
substrates 64
4.3. Intensification of cleaning processes 68
4.4, Typical cleaning processes for plates and
substrates 71.
4.5. Dry cleaning of plates and substrates 74
4.6. Check,ing the quality of cleaning for plates and
subst:~ates 80
Test questions and assignments 82
Chapter 5. Contact Photolithography 84 -
_ 5.1. Basis of photolithography and its applications 84
5.2. Forming a photoresa.stive layer 94
- 5.3. Forming a photoresistive mask 100
5.4. Obtaining a configuration for the parts 105
5.5. Production technology of ~hototemplates 111
5.6. Types of waste and ensuring photolithography -
quality , � 116 _
Test questions and assignments 118
- 87
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Chapter 6. Obtaining a Configuration for IC Film Elements
- by Using k'ree Masks 119
6.1. Free mask method 1.19
6,2, Free mask production technology for thin-film
IC's 122
6.3. Stencil printa.ng method ~27
Test questions and assingments 129
- Chapter 7. New Lithographic Methods 130
_ 7.1. Non-contact photolithography 130
- 7.2. X-ray lithography 134 -
7.3. Electron lithography 139
' Test questions and assignments 144 _
Chapter 8. Thin Film Deposition Methods 145
8.1. Thermovacuum deposition method 145
8.2. Ion bombardment sputtering 151
8.3. Thermal oxidation 159
8.4. Deposition of films from the gas vapor phase 161 -
8.5. Anode electrolytic oxidation 166 ~
8.6. Deposition of inetals from electrolytes and
~ solutions 169
= Test questions and assignments 171
Chapter 9. Epitaxial Growth of Semiconductor Layers 172
9.1. Principles of epitaxial processes 172
9.2. Methods of epitaxial growth from the gas vapor
phase 178
9.3. Other epitaxial methods 182
9.4. Heteroepitaxy 186
9.5, Local epitaxy 190
9.6. Doping of epitaxial layers 191
9.7. Defects in epitaxial layers 193
9.8. Checking of epitaxial layers 197
Test questions snd assignments 200
Chapter 10. High-Temperature Diffusion 201
10.1. Principles of the high-temperature diff usion
- method 20i
10.2. Features of diffusion in planar technology 209
10.3. Ways of performing diffusion 210
_ 10.4. Defects and checking of diffusion structures '?i
Test questions ~:.~~d assignments
- d8
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,
Chapter 11. Ion Dopi.ng and Other Methods of Obtaining
Semiconductor Elements 222 `
11.1. ~rinciples of'ion doping method 222 .
- 11.2. Distribution of impur~,ty density in ~,on-doped
layers 22~
11.3, Techniques for th~ ion doping process 236
11.4. Advantages and dra~tbacks �:o~ i,on doping 236
11.5. Other methods for obtaining semiconductor elements238
_ Test questions and assingnments 243
Chapter 12, Metallization of Silicon Structures 245
12.1. General information 245
12.2. Single-layer aluminum metallization 247
12.3, Multilayer metallization 253
12.4. Mulilevel metallization 25~
12.5. Metallization of hinged active elements 260
12.6. Defects and checking of inetallization quality 263
Test questions and assignments 26~
Chapter 13. Techno logical Processes for Manuf acturing ~
Structures for Bipolar Microcircuits 26g
- 13.1. Design and production features of bipolar
microcircuits 26g ~
13.2. Production technology for b~.polar IC structures
with insulation by the p-n junction 273
13.3. Production technology for bipolar IC structures
with dielectric insulation 278 -
13.4. Production technology of bipolar IC structures
with combined insulation 285
13.5, Production technology for matched IC structures 289
Test questions and assignments 290
Chapter 14. Technological Processes for Manufacturing
MDS-IC Structures � 2g1
14.1. Design and Production Features of MDS-IC 291
14.2. Production technology for tr~in-oxide p-channel
MDS-IC structures 2g4
14.3. Production technology for metal-thick oxide-
semiconductor IC structures 297
14.4. Manufacturing technology fo~ MDS-IC structures
with fixed gates 299
, 14.5. Production technology for silicon MDS~IC
structures 303
14.6. Ways of improving MDS-IC quality 309
- 14.7. Protecticn of semicoizductor structures 313
- 14.8. Che~king dielectric films 317
Test questions and assignments 320
- 89 ~
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Chapter 15. Producti.on Technology for Thin-Film -
Mi,crocixcuit Structures 321
15,1. General information 321
15,2. Typical circuits and basic stages in the manufac-
_ ture uf thin-fi.J.m mi.crocircuit structures 325
15.3. Production technologx of thin-film microcircuit
structures with the use of free masks 330
15.4. Production technology of thin-film microcircuit
structures with the use of photolithography 334
15.5. Production technology of structures for thin-film
tantalum microcircuits 338
15.6, Production technology of thin-film microcircuit
_ structures with beam treatment 340
15.7. Rate fitting and protection of film elements 342
15.8. Checking the production of thin-film microcircuit
structures 344
Test questions and assignments 349
Chapter 16. Production Technology of Thick-Film HIC
Structures 350
16.1. Gener~.l information 350
16.2. Basic stages of the production technology for the
passiti~e part of. thick-film HIC structures 355
16.3. Checking the production of thick-film
- microcircuits 363
Test question,s and assignments 365
_ Chapter 17. Assembly of Microcircuits 366 ~
17.1. Separation of plates and substrates with prepared
- structures 366
17,2, Basic assembly methods 372
17.3. Assembly of cry.stals and plates 375
~ 17.4. Wire diagrams 37`%
17.5. Wireless diagrams 389
17.6. Checkin g the assembly process 393 -
Test questions and assignments 394
Chapter 18. Hermetization of Microcircuits 395
18.1. Microcircuit housing 395
18.2. Hermetization methods in the housing 400
18.3. Hermetization in different kir~ds of housings 4C ~ _
18.4. Non-housing hermetization 4J~ '
18.5. Quality control of hermetization 41==
18.6. Final operations in microcircuit production 417
Test questions and assignments 419 ~
~0
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- Chapter 19. Ensuring Production EfficiencX and Micr~o-
circuit Quality 420
19.1. Basic trends and problems ~n microelectronics
_ during the current f~,ve-year plan 420
19.2. Ensuring the effi.ciency and quality of micro~
electronics at the pzesent stage of development 422
- 19.3. Non-destructive testing and improvement of ~
technology 426
Test questions and assignments 430
Conclusion 431
Test questions and assignments 436 -
= Bibliogra~hy 437
- Subject index 439
COPYRIGHT: Izc~atel'stvo Energiya, 1980
- [268-9370]
9370 ~
CSO: 1860
~ -
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rv~~ va�rl~,irw u~r: V1VL1
~
SCIENTIFIC ARTICLES ON ANTENNAS
Moscow ANTENNY: SBORNIK NAUCHNYKH STATEY (Antennas: Collection of Scientific =
Articles) in Russian No 27, 1979 signed to press 9 June 79 pp 2-3
- [Annotation and table of contents from book edited by A. A. Pistol`kors et -
a1., Izdatel'stvo Svyaz', 5000 copies, 184 pages]
[Text] This volume addresses a ntunber of important problems of modern -
- antenna technology: investigation of high-frequency breakdown in radar an-
tennas, synthesis of director antennas by directive gain maximum, holo-
graphic methods of ineasuring antenna radiation patterns, mod2rnization of
~ the radiation pattern control system of the North-South antenna of the -
- DKR-1000 radio telescope of the Physics Institute imeni P. N. Lebedev of
the USSR Academy of Sciences, and theorerical investigation of the noise
temperature of the RATAN-600 radio telescope. _
The authors devote attention to the problem of optimal synthesis of linear
antenna arrays, including unequally spaced, and calculation of the reflec-
tion factor from the open end uf a microstrip line.
This volume is intended for scientists and radio engineers working in the
- area of antennas.
Contents Page
~
_ E. N. Kaplan, Yu. A. Lupan. High-Frequency Pulse Breakdown in -
- Radar Antennas 3
- 13, V. Braude, N. A. Yesepkina. Theoretical Investigation of
- Noise Temperature of the Antenna System of the R~TAN-600 Radic �
Telescope 14 _
Ya. S. Shifrin, V. A. Usin. On Accuracy of Holographic Metn~ds of ,
Measuring Antenna Radiation Pat*_erns 26
S. N. Ivanov, Yu. P. Ilyasov, V. T. Solodkov, V. Ya. Shcherbinin. ~
Modernization of the Radiation Pattern Control System of the ~
North-South Antenna of the DKR-1000 Radio Telescope of the
Physics Institute imeni P. N. Lebedev of the USSR Acadeny of
Sciences 38
92 C
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~~GU~T _ ~ F~UC~ c~~ ~ - ~ ~

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B. M. Mizkovich. Circular Aperture Radiation Patterns, Optimal
According to the Root-Mean-Square Criterion in the Region of
Side Lobes 46
. L. I. Byalyy. Optimal Synthesis of Linear Antenna Arrays 52
- L. I. Byalyy. Characteristics of Unequally Spaced Linear Arrays 60
V. M. Baryatinskiy, V. I. Klassen. On the Problem of Reducing
_ the Fringe Radiation Level of Anterina Arrays With Distance
Between .T.'.adiators d> a 68 ~ '
_ V. N. Rudenko, A. P'. Mantula, V. S. Shapurov. Mutual Im-
pedances Between Antennas of Arbit rary Polarization With
Various Radiation Patterns 73 -
V. P. Narbut. Influence of Asymmetry of the Amplitude or Phase -
- Patterns of an Antenna Exciter on the Polarization Structure
of Radiation of Axisymmetric Dish Antenr.as ~g
. I. A. Gorshkov, L. N. Zakhar'yev, R. A. Petrova. Some Results
- of Computation of a Homogeneous Dielectric Cylindrical Lens 89
Yu. V. Vaysleyb, L. A. Sobchakov. Dipole Near the Plane Inter-
face of ~ao Media 98
' Ye. A. Sternopolo, L. A. Matveyeva. " Blind" Zones in Radiation
of Dipole Phased Antenna Arrays 109
V. A. Mashkov, A. D. Shchukin. Synthesis of a Director Antenna
by Directive Gain Maximum 113
B. M. Levin, V. P. Razumov. Ground Loss Resistance 125
M. I. Astrakhan, V. P. Akimov, N. V. Koroleva. Reflective Ac-
tion of Flat Wire Screens Parallel to the Earth's Surface 133
Ye. G. Past~chenko, V. V. Tilchonov. Input Impedance of a Ver-
tical Loop Antenna Located Above S emiconducting Soil 144
V. M. Maksimov, S. M. Mikheyev, N. S. Ostroukhov. Synthesis of
s Feeder System Scattering Matrix f or a Re-Emitting Antenna
_ Array 151 -
N. N. Gorobets, A. V. Zhironkina, A. G. Zdorov, L, P. Yatsuk.
~ Asy~etric Cruciform Slot Radiators at Waveguide Ends 159
R. I. Perets. Adding Signals in Multigle-Arm Directional
Dividers and "Noise" Characteristic s of Re~eiving Antenna
Arrays 166
Article Resumes 179
_ COPYRIGHT: Izdatel'stvo "Svyaz'," 197 9
[ 226-3024 ]
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UDC 681.58 -
SMALL SIGNAL MODULATORS
Leningrad MODULYATORY MALYKH SIGNALOV iii Russian, 2d edition -
1980 signed to press 4 Dec 79 p 2, 200 -
LTitle, annotation, and table of contents of a book by Boris
Andreyevich Kalinchuk and Oleg Aleksandxovich PicY?ugin, Energiya,
7800 copies. 200 page~ _
- (Text] This b~ok discusses the conversion of small signals `
�~ith a dc low-frequency electric current into ac signals.
- The second edition differs from the first, which was published -
in 1972, in that a number of new methods for constructing mo-
_ dulators that have been developed recently are considered; the
sections on the calculatiox~ and design of phot~- and transistor -
modulators, along with those an the utilization of modulators
- in technology, are expanded.
- The book is designed for specialists studying the enh~ncement
of small signals with dc and low-frequency currents;,it
will also be useful for graduate students and students at
institutions of higher education.
Table of Contents -
' Introduction 3
Chapter 1. Basic Definitions; Modulator Classi.fication
and Parameters 4 -
- 1.1. Basic concepts 4
1.2. Classification of modulators 6
1.3. M~dulator parameters 9
- Chapter 2. Electromechanical Modulators 57
2.1. Contact modulators 57
2.2. Capacit~nce modulators 122
94
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= FOR OFFICIAL USE UNLY
= Chapter 3. Modulators with Uni~o~.ar Tr.ansistors 127
- 3.1. Characteristics of uni.~ola~. modu7.a~ors ] 27
- 3.2. Analysis af bridge ci.rcuits for modu].ators 1.31
3.3. Parame~ers of modulators with uni~4l,ar trans~stors 140,
Chapter 4. ~hotoresi.stive Modulators ~58
4.1. Characteristics of optron modul.a~:ing elements ~.58 -
= 4.2. Analysis of cir.cuits for photores~stive modulators 160
Chapter 5. Methods for Testing Modulators 163
5.1. General information 163
5.2. Methods for determining the etectrical parameters _
_ of contact modulators 165 ~
~ 5.3. Methods fo~ determinin.g the parameters of
capacitance modulators 174 _
5.4. Methods for determining the parameters of contact-
less modulators of tne switch.~ype 17~ ' _
_ Chapter 6. Applications of Modulators.to Measurement -
rechnology and Automatior~ 183
Bibiography 198
. COPYRIGHT: Izdatel'stvo "Energiya," 1980 _
L.7.67-937~
9370
CSO: 1860 ' ~
. ~ 95
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r~x urrtutt~ u~~, ULVLY
r.
SPACE-TIl~ PROCESSING OF SIGNALS, COLLECTZON OF ARTICLES ANNOUNCED
Gor'kiy IZVESTIYA VYSSHTKH UCHEBNYICH ~AVEDENTY, RADIOFIZIKA in Russian
No 4, 1980 pp 505-506
[Annotation and table of contents of inter-WZ collection of articles
"Prostranstvenno-vremenna}�a obrabotka signalov, vypusk 2" [Space-Time
= Processing of Signals, No 2] edited by I.Ya. Kremer, Izdatel'stvo
~ Voronezhskogo Gosudarstvennogo�Universiteta, scheduled for first quarter
of 1980, L.5 quires]
[Text] In this collection are discussed questions relating to the crea-
- tion and analysis of systems for processing space-time, time and vector-
time signals against a background of noise. An investigation is made of -
the characteristics of systems for the space-time processing of signals -
and of ~he advisable principles of their design. The generalized cl.iarac-
teristics of processing sys':ems as space-time filters are discussed, along
with questions relating to the creation of such filters. A study is made
- of the optimal space-~ime filtering of random fields and of an evaluaLion
_ of their parameters. The results are given of the salution to problems
;in detecting space-time and time signals both with known and par~ly un-
known noise statistics. An analysis is made of optimal and quasi-optimal -
algorithms for the detection of signals with unknown parameters and of
non-Gaus~i~n signals. An investigation is made of the characteristics of
acousto-nptical equipment for processing radio signals.
CONTENTS -
Shmelev, A.B. "Nonlinear Filtering of Random Fields," USSR Acaciemy of
= Sciences Radio Engineering Institute.
' Korostelev, A.A. "Generalized Characteristic~ of Precision and Resolu-
tion," Leningrad Mechanics Institute.
- Mel'nik, Yu.A. "Estimation of the Resolution of Coherent Multiparametric
- RLS's [Radar Stations]," USSR Academy of Sciences Main GEOphysical Ob- ,
' servatory.
96 -
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Reshetov, L.A. "Application of the Discrimination Approach in Designing
Space-Time Filters," Tndustrial Radioelectronic Systems Labora~ory,
Leningrad. _
- Lukoshkin, A.P. and Shatalov, A.A. '~iethods of Designing Multibeam -
Systems for the Concomitant Scanning of Space," I,eningrad Institute of
~ Aviation Instrument Making. .
Markov, L.N. "Probability Charactsristics of the Phase Coordinates of
Spatially Distributed Systems."
e
_ German, A.M. and Na.khmanson, G.S. "Detection of Space-T3.me Signals
Through Quantized Phase Selection," Voronezh State University.
Pon'kin, V.A. and Romanov, A.D. "Analysis of a System for Receiving
Signals with Holographic Subtraction."
Potapov, N.A. "Feasibility of Employing Acousto-Optics in Processing .
Signals in the Fresnel Zone," Voronezh State University. -
Khromykh, V.G. and Zuqev, S.A. "Optimal Atgorithms for Space-Time Pro-
cessing of Doubly Quantized Signals," Voronezh State University.
- Chulyukov, V.A. "Estimating the Variance of a Nonstationary Random
Field," Voronezh State University. ~
Makarov, V.F. and Trusov, V.S. "Space-Time Processing and Optimal
Sounding Pulses for Detection,'� Tomsk State University. =
: Dragan, Ya.P. and Yavorskiy, I.N. "Statistical Processing of Space-
Time Signals with a Rhythmic Structure," Ukrainian SSR Academy of Sciences _
L'vov Physicomechanical Institute.
Pervachev, S.P. and Perov, A.I. "Comparative Analysis of Radar Range-
finders," Moscow Power Engineering Institute. ~
Marshakov, V.K. and Trifonov, V.P. "Detection of a Signal with an Un-
known Energy Parameter," Voronezh State University.
- Meli~itskiy, V.A. "Statistical Characteristics of the Polarization
Coefficient of a Partially Polarized Signal in the Presence of Normal
NO].S2. ~v
Boyko, I.F., Marchenko, B.G. and Shutko, N.A. "Problem of Nonlinear
Transforma.tions of Linear Random Processes," Kiev Institute of Civil
Aviation Engineers.
Biletov, M.V. and Vassershteyn, I.S. "Optin~al Detector of Stationary -
- Non-Gaussian Signals," Voronezh State Pedagogical Institute.
- 97
- FOR OFFICIAL USE ONLY
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1'VL\ VL'L' LlilllL UJL' VLVLL
Zil'bershteyn, A.M. and Natkovich, Yu.S. "Solution of One Problem in
Detection Unde~- Conditions of Tncomplete A Priori Information," All-
Union Scientific Research Institute of Automated Metrology Systems,
Tbilisi.
� Senatorov, A.K. "Detection of Objects with an Unknown Effective Scatter-
ing Area by Means of a Maximum Similitude Detector," Voronezh State
University. ~
Radchenko, Yu.S. and Buteyko, V.K. "Analysis of the InfluencP of a
Smoothing Filter on the Accuracy of Estimating the Time Status of a
Complex Signal," Voronezh State University.
Galun, S.A. "Characteristics of a Quasi-Optimal Algorithm for Detection
of a Radio Pulse with a Square Envelope Against a Background of White
- Nofse," Voronezh State University.
_ Fedorov, V.I. "Reliabilit}~ of Estimating a Signal Parameter Wtien
Using a Thr.eshold Resolver," Voronezh State University.
Zyul'kov, A.V. "Optimization of the Preselector When Receiving a Radio
Signal Against a Background of White Noise," Voronezh State University.
Pozin, P.A. "Optimal Reception of an Elliptical Polarization Optical
Signal," Voronezh Polytechnical Instituta.
Kitayev, Yu.I., Yepifantsev, Yu.F. and Konstantinov, M.B. "Broadband ~
Ceramic Piezoelectric Transducer for Systems for the Space Proce~sing
of Signals," Voronezh State University.
_ Golub, V.A. "Characteristics of the Detection of an Unknown Radio Signal
with an Acousto-Optical Receiver Against a Background of Noise,"
Voronezh State University.
_ Konva~v, A.D. and Shul'zhenko, S.N. "Certain Characteristics of the
Effectiveness of the Transmiss~un of Messages Through Magnetoactive
Media," Voronezh State University.
Orders are to be sent to the following address: 394000, Voronezh, pr.
- Revolyutsii, 33, magazin "Kniga-pochtoy."
~OPYRIGHT: IZVESTIYA VYSSHIKH UCHEBNYKH ZAVEDENI�, RADIOFIZIKI`., 1980
[246-8831]
8831
CSO: 1860
98
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QUANTUM ELECTRONICS
- .
UDC 62i.378.325
CALC ULATION OF ANGULAR CHARACTERISTICS OF LASERS WITH UNSTABLE RESONA~ORS
Kiev IZVESTIYA VUZOV SSSR - RADTOELEI~RONIKA in Russian No 3, 1980 pp 93-94
Article by N. Ye. Sklyarov, Yu. A. Timofeyev, N. N. Petrov, and V. A. Pat-
sayeva, subniitted 23 Jan 1979]
_ [Text] In order to calculate angular characteristics of unstable resonatars
_ [1], it is possible to use Tang and Statts' multiwave generation model for
parallel-plate resonators. In this case, the equivalent length Leguivalent
of the parallel-plate system is determined for each type of unstable reson-
ators which are being examined under. the condition af th~ equality of their
diffraction losses.
The criterion of the appgicability of the garallel-plate resonator theory
can be written in the following form
(~11~) ~ 1/N~
where Q L-- maximum dif.ference of the optical path ~n the resonator; !1,
radiation wave length; N-- number of Fresnel zones.
- Tberefore, the Tang-Statts model satisfactorily describes time-averaged angu-
lar characteristics of laser radiation in the case of perfect active models
and resonators.
For a telescopic resonator (Figure 1), Lequivalent can be determined in the
followin~ way. The value of diffracti~n losses of the resonators is deter-
mined by the number of Fresnel zones. For a telescopic resonator,
N = 2k/,~, .
, where h-- sag of the output mirror. In the case of a para11e1-plate reson- ,
ator,
N = Da/4L~B~�
Key: 1. Equivalent
where D-- diameter of the active element; LEquivalent ieng�~h of the re-
~onator.
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rv~. VL'L'1L1t1L u~r, vara.~
From the equality of the Fresnel numbers of two resonators, we obtain
Z3,ce = Da/8h. -
By using the condition of the cofocal nature of the mirrors R1=-(2L+R2) and -
the expression for the enlargement factor of the telescopic resonator M=
I Rl' /RL, we obtain
' D~(M-1) -
( ) ' 1
~ca 16L (1 - ~ 1 - Dz 16MaL2 a) ( >
\
where L-- gpometrical length of the telescopic resonator.
When performing computations, L in formula (1) should be replaced with _
Key: 1. Effective L~_L_~e,+ ~e ~ _
_
where la length of the active element; n-- refractive ir~dex of the ac-
tive substance.
The dive.rgence 9 in the case of the multiwave approximation [2] ~
em = /Ji~A , -
where m-- number of excited angular types of oscillations;
- s~: ~/D.
- The number of the transverse types of oscillation under the condition 61A -
- 6o is defined by the expression [2]
~
3 m3 2m' QA (1- n I.
Ql . p /
S
where 60 = 2 ln M-- unselective losses of the resonator; 2(~D'"B _
\
diffraction losses of the first transverse type of oscillations; np
excess over the pumping power threshold..
~ c~10~�oa rad
R~ R~ 5 2
~ ' 3 _
~ . y
o � ~
- 3~� 7 3 M -
Figure 1 Figure 2
- 1G0
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- Consider}n~ the annular extraction of radiation from a telescopic resonator,
. the final expression for the val�e e`_- the angular divergence 9 with respect
~o tha half-intensity level can be wri,tten in the form of
( 2M
6=~Alm+ M-1)'
Figure 2 shows the curves of the computed dependence of the angular diver-
gence of radiation from the coefficient M for various levels of pumping:
_ 1-- n~,=4; 2-- np=3; 3-- nP=2; experimental values of 9 for np=2.
The cum~uration of diver~?nce was done for a laser using neodymium glass
with 1a=62 cm, D-4.5 cm, L-100 cn~. As can be seen from Figure 2, there ex-
i.s~s an optimal value oi M at which angular divergence is minimal,
Experimental checking of this laser showed that the value of angular diver-
gence corresponds satisfactorily to thE computed values (Figure 2).
- Bibliography ~
1. Anan'yev, Yu. A. "Unstable Resonators and Their Applications" in the
collection "Kvantovaya elektronika [Quantum Electronics], Moscow, Sovet-
- skoye radio, 1971, No 6, p 3.
2. Mak, A. A., et al. "Solid-State Lasers", UFV [Achievements of Physical
- Sciences], 1967, 92, No 3, p 373.
COPYRIGHT: "Izvestiya vuzov SSSR - Radioelektronika," 1980
[?52-10,233]
10, 233
CSO: 1860
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