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JPRS ID: 8896 TRANSLATION MULTIPROGRAM WIRE BROADCASTING BY V. YA. DZYADCHIK, S. A.ZASLAVSKIY, B.N. FILATOV, A.V. SHERSHAKOVA

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CIA-RDP82-00850R000200040065-4
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297
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November 1, 2016
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APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 1 MUL BY ~'R. DZYADCH I K, S. R. ZASLR~JSK I Y ~l JRNUARY 19~0 B. N, F I LATO~, R. ~J. SHERSHAKO~A C FOUO ) 1 OF 4 APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY J~'RS L/8896 31 January 19@0 Translation Multiprogram Wire B~oadcasting ey ~ V. Ya. Dzyadchik, S. A. Zaslavskiy - B. N. Filatov ,~A. V. Shershakova F~IS ~OREIGN BROADCAST INFQRMATION SERVICE FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 NOTE JPRS publications contain information primarily from foreign newspapers, periodicals and books, but also from news agency transmissions and broadcasts. Materials from foreign-language sources are translated; those from English-language sources are transcribed or reprinted, with the original phrasing and other characteristics retained. Headlines, editorial reports, and material enclosed in brackets are supplied by JPRS. Processing indicators such as [TextJ or [Excerpt] in the first line of each item, or following the - last line of a brief, indicate how the original information was processed. Where no processir.g indicator is given, the infor- mation was summarized or extracted. Unfamiliar names rendered phonetirally or transliterated are enclosed in parentheses. Words or names preceded by a ques- _ tion mark and enclose~ in parentheses were not clear in the original but have been supplie3 as appropriate in context. - Other unattributed parenthetical notes within the body o~ an item originate with the source. Times within items are as given by source. The contents of th is publication in no way represent the poli- cies, views or atti*udes of the U.S. Government. - For fsrther information on report content call (703) 351-2938 (economicl; 3468 (political, sociological, military); 2?26 - (life sciences); 2725 (physical sci~nces). - COPYRIGHT LAWS AND REGULA.TIONS GOVERNING OWNERSHIP OF _ MATERIALS REPRODUCED HEREIN REQUIRE T~~T DISSEMINATION ~ - OF THIS PUBLICATION BE RESTR.ICTED FOR OLFICIAL USE ONLY. APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 ~ FOR OFFICIAL USE ONLY JPRS L/8895 31 .7anuary 19 8 0 - _ MULTIPROGRAM WIRE BROADCASTING Moscow MNOGOPROGRAMMOYE PROVODNOYE VESHCHANIYE in Russian 1974 signed to press 17 Sep 74 pp 1-303 Book by V. Ya. D~yadchik, S. A. Zaslavskiy, B. N. Filatov and A. V. Shershakova, "Svyaz" Publishers, 11,600 copies CONTENTS PAGE Foreword 2 Chapter 1. Multiprogram Wire Broadcast Systems 4 _ 1.1. Basic Characteristics of the MPB Systems 4 = 1.2. MPB System Using Physical-Artificial Lazge-Capacity Cable Networks 5 1.3. Multiprogram Wire Broadcast System over the City T.elephone Exchan~es g - 1.4. Switchboard Type Multiprogram Broadcast Systems Based on the Television Distribution Network 20 1.5. Multiprogram Wire Broadcasting in Foreign Countries 24 Chapter 2. Triple-Program Wire Broadcast System (TPB) 26 2.1. Structural Diagrams of tine City WB Networks 26 2.2. Basic Principles of Constructing the Low-Frequency City Networks 33 2.3. Basic Principles with Respect to Creation of tlle - MPB System 36 2.4. Nu~ber of Programs, Carrier Frequencies atid Type of Modulation 38 2.5. Determination of the Initial Voltages of High-Frequency Signals ir. the WB Channel q2 ~ 2.6. Structure of the High-Frequency Channels of a TPB System 46 2.7. Structure of the.Station Part of the High-Frequency Channel 46 _ 2.8. Structure of the Line Part of the High-Frequency Channel 60 ~ - a - [Z - USSR - F - FOUO] FOR OFFICIP,L USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY 2.9. Structure oi the Receiving Part of the High-Frequency Channel 64 2.10. Interference in the TPB System 69 2.11. Methods of Decrtasing the Interference with the liigh- Frequency Channels of the TPB System 79 2.12. AM Signal with Regulatable Carrier and its Application 88 ~ 2.13. Stereophonic Broadcasting in the TPB System 101 2.14. Basic Principles with Respect to Equipping Links of the TPS system 104 Chapter 3. Introduction of Narms for the TPB System 1.18 3.1. General Information 118 3.2. Introduction of Narms f~r the Low-Frequency Channel 118 3.3. Introduction of Norms for the High-Frequency Channels 119 3.4. Determin~tion of the Through Channel 120 3.5. Definition of the Normalized Parts of the Through Channel 121 ' 3.6. Qual~cy Indexes of the Through Channel and Parts of It 122 ~ 3.7. Introduction of Norms for the Tr.an;~mitters and Repeaters 126 3.8. Introduction of Norms for Receivers 129 3.9. Introduction of Norms for High-Frequency Devices and Lines ~ 136 Chapter 4. Transmitters and ~tepeaters 145 4.1. General Information 145 4.2. Automatic Gain Control of the Car*-ier Frequency 148 4.3. UPTV-200 and UPTV-400 Transmitters 153 4.4. UPTV-60 Transmitter 161 4.5. Connection of the Transmitters to the TPB Circuit 162 4.6. Ztao-Channel Intermediate Repeater (DPU) 168 - 4.7. Prospects for Improving Transmitters and Repeaters 176 _ Chapter 5. Receivers 178 5.1. General Information 178 5.2. Riga Type GT 181 ~ 5.3. Avrora Triple-�Program Speakers [GT] 183 ~ 5.4. GT with Low-r'requency Channel Gain (Fig 5.5) 186 - 5.5. GPTV-3 G-~up Device 187 Chapter 6. Measuring Devices and Instruments 196 6.1. General Information 196 6.2. Modulation Attachment 197 6.3. Lineman's Indicator 199 6.4. Comp~ex Resistance Meter (IKS) 202 6.5. High-Frequency Oscillator (VI~3) 205 _ J _ b _ - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 _ FOR OFFICIAL USE ONLY 6.6. Fault Detector (IPTV-1) 210 6.7. ITPV-2 Type Triple-Program Wire Broadcast Pulse Meter 212 6.8. Monitoring Receiver (KPU) 213 6.9. Channel Monitoring Device (UKT) 22p - 6.10. Test Signal Pickup (G-78/120) 221 6.11. Measurement Panel of the Distributing Feeder Frame (PI-STR) 223 6.12. Problems of Introducing Meters 227 Chapter 7. High-Frequency Processing of the Line Part of a Channel and High-Frequency Line Devices 229 7.1. High-Frequency Processing of Lines 229 7.2. Bypasses 230 7.3. Compensators 232 ~ 7.4. Matching Devices 234 7.5. Band-Elimination Devices 237 7.6. Devices for Connecting Transmitters 23g %.7. Transformer Substation Switching Devices 242 Chapter 8. Tuning and Measuring the Parameters of the Devices, the Lines and t~~e Channels for Three-Program Wire Broadcasting 246 8.1. General Inforiaation 246 ! 8.2. Electrical Measurements of the Transmitters 247 8.3. Electrical Measuremen;.s of the Group Receivers 254 8.4. Tuning and Electrical Measurements of the High-Frequency Devices 25g 8.5. Electrical Measurements of Intermediate Amplifiers 265 8.6. Electrical Measurements of the Lines 267 8.7. Electrical Measurements of Quality Inde~oes of Aigh- - Frequency Channels and Parts of Them 270 Appendix 1 2~~ Appendix 2 � ~79 Appendix 3 2g1 Appendix 4 2g2 Bibliography 2g3 - - c - FOR OFFICIAL USE ONLY � APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 ~ FOR OFFICIAL USE ONLY ~ PUBLICATION DATA English title : MULTIPROGRAM WIRE BROADCASTING ` Russ ~an title ; MNOGOPROGRti ~II~IOYE PROVODNOYE VESHCHANIYE Author (s) ; V. Ya. Dzyadchik, S.A. Zaslavsk3y _ et al. _ Ed:itor (s) , Publishing House , "Svyaz " Placc of Publication , Moscow Date of Publication , 1974 Signed to press . 17 Sep 74 ~ - Copies . 11,600 COPYRIGHT , Izdatel'stvo "Svyaz 1974 - d - F OR OFF IC IA L US E ONLY - APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY r~ UDC 654.195.2 , MULTIPROGRAriLJIRE BROADCASTING ~ ~ i'r~ - Moscow MNOGOPROGRAMI~NINOYE PROVODNOYE-VESHCHANIYE in Russian 1974 signed to press 17 Sep 74 pp 1-303~ - [Book by V. Yz. Dzyadchik, S. A. Zaslavsiciy, B. N. Filatov, A. V. Shershakova, Svyaz', 11,600 copies] [Text] A study is made of va~ious multiprogram broadcasting systems combined - with other forms of communications; the ac:vantages and disadvantages of the - various methods of creating triple-program broadcast channels based on the existing overhead wire broadcasting networks are analyzed; a study is made of the problems of interference and standardiza~ion of the quality indexes of the channels and in3ividual devices; a description is preser~ted of the station and subscriber equipment, monit~ring ar:d measuring instruments and high-frequency devices. The book is designed for Qngineering ar.d technical workers involved with the design, introduction, operation and maintenance of the triple-program broadcast system. - 1 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFTCIAL USE ONLY FOREWORD _ In the Soviet Union, the triple-program wire broadcast system (TPB) has been - introduced in all large cities. In spite of the rapid development of radio and television broadcasting, multiprogram wire broadcasting will in - the future be one of the prospective broadcast media. The TPB system was developed by the Scientific Research Radio Institu*e in in 1960. The system has recentlq received further development. Can~sidering _ the operating experience and the results of the investigations, new improved transmitting and receiving devicps have been developed, a set of m~onitoring ' and measuring instruments has been built, and new high-frequency c~evices for the wire broadcast networks have been developed. - However, the future development of the wire broadcasting network (WB) will be greatly influenced by modern civil construction distinguished by the fact that instead of the continuous construction of buildings of equal height, local microdistricts w3th high-rise complexes of varying heights are being organized. This is changing the structure of the WB network. The overhead lines running on supports on the roofs of the variable-height buildings present problems in construction and maintenance. Difficulties will also be encountered in taking the line from one local micrndistrict to another as a result of the wide outside thoroughfares and streets. A way out of the situation which. is already realizable in practice is partial - or complete conversion of the distribution network to cable construcCion using the city telephone exchange lines, the basements of buildings, service corridors and the introduction of cable inserts in the overhead lines. Accordingly, the question arises of rebuilding the WB networks and creating new layouts for the city broadcast networks. It is possible to propose that the development of a city wire broadcast system will proceed along the path of combining the system with other communication networks. In this book a study is made of the problems of building multiprogram broad- - cast systems combined with other forms of communications. The advantages ' and disadvantages of various methods of building the TPB channels based on 2 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ~ the existing overhead WB networks are analyzed, the problems of interference and standardization of quality indexes of the channels and individual devices are investigated, descriptions are given of the station and subscriber - equipment, the measuring instruments and high-frequency devices, and a study is made of the measurement techniques and methods of tuning the devices. The chapters and divisions of this book were written by the foll~wing: Chapter 1, ��2.1, 2.2, 2.14, 4.6 by V. Ya. Dzyadchik; ��2.4, 2.5, 2.10-2.13, 4.1-4.5, 4.7 by S. A. Zaslavskiy; Chapter 3, ~�2.3, 2.6-2.9, and Appendices 1-4 by V. Ya. Dzyadchik and S. A. Zaslavskiy jointly; and Chapters S, 6, 7 and 8 join~ly by B. N. Filatov and A. V. Shershakova. The book is designed for engineering and technical workers of the maintenance enterprises, the workers of the design organization~ engaged in the introduction of the TPB system and it can be used as a tea!t for students in the middle and higher - communications schools. The authors express their deep appreciation to the reviewer of the book L. Ya. Kantor and the responsible editor V. I. Shanurenko for valuable recommendations and suggestions. Comments on the book shuuld be sent to Izdatel'stvo Svyaz' (101000, Moskva- Tsentr, Chistoprudnyy Bul'var, 2). 3 FO}f OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 I FOR OFFICIAL USE ONLY : CHAPTER 1. MULTIP't20GRAM WIRE BROADCAST SYSTEMS ~ 1.1. Basic Characteristics of the MPB [Multiprogram *+1ire Broadcast] Systems _ The wire broadcast system is the set of devices designed to shape and amplify~broadcast program signals and distribute them by means of a wire distribution network to the subscriber receivers with subsequent conversion of the electric signals to acoustic. A riecessary element determining the technical essence of such a system is the lines and line equipment, the , purpose of which determines the name of the given wire broadcast system. Accordingly, the MPB systems can be based on the following wire distribution networks: telephone communications, collective television reception systems, the domestic broadcast network, and on the basis of an autonomous low-freque-~cy signal-program broadcast system. Depending on the method of transmitting the broadcast program signals, two versions of the MPB systems are distinguished: low-frequency and high- _ frequency. In the low-frequency version the signals of all programs are transmitted in the initial low-frequency spectrutu. In the high-frequency version, the program signals are transmitted in the - - form of modulated high-frequency signals. - With respect to methods of construction and use of the distribution network the MPB are separated into the following: uncommuted systems using one physical network to transmit the broadcas~ signals and other types of - information, the cot~utation type systems using one physical network to _ transmit the signals of all programs and the commutation type systems using _ several physical circuits for transmitting the broadcast systems and other types of information. Each system is characterized by another quality class and number of channels, the frequency band used by the modulation method, the type of receiver and . tthe technical-economic indexes. 4 . FOR OFFICIAL U5E ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE O1~LY 1.2. I~B Systems Using Physical�and Artificial Lar~e-Capacity Cable Networks The structural diagram of the system using a multiprogram cable is illuatrated in Fig 1.1. On the transmitting side thE broadcast signals are fed to the line at comparatively high voltage (60 or 30 volts). On rae subscriber side, the simplest receiver is used. This type of system is ~~lia~le, convenient in cperation and maintenance, but it requ~.res a large nusnber. of physical circuits in the cable equal to the number of transmitted programs. ,yilLl.'!!IllW7i~AlQA ~ . . ~ ~ ~ ~l) Pesr.ve~~onr.~ASrmo sem~ (5) ~ ~ _ -f2~ ~ ~ D , . . . e ~I ~ i : ~ ed b (3)'~d,~ ~ y~ . 4 ~p ~ . ~o'E,? ' _ ~ ) 1 nv 1\ ~ ~ ~ a 3 d~ g~ - J - 4 y ~'G~a~ ~ 6) ~ r~h~N. 6) . . y~,'~ ' Ut~Q Figure i.l. Structural diagram of the low-frequency MPB system Key: : 1. Repeater station 5. Distribution network 2� Iprogram 6. Subscriber sets 3� IIprogram 7. To other subscriber sets 4� Illprogram In practice the version of this system is used where along with the physical networks artif icial, so-called phantom networks are used (see Fig 1.2). Th~ operating principle of this t}~pe of system consists in the following: th~ signals of four programs are transmitted from the repeater station to the distribution network. Three programs are f ed to the subscriber network over three physical circuits. Program IV uses the physical networks of = programs II and III, and it is connected to the midpoints of the secondary windings of the transformers Tpl. On the subscriber side the signals of program IV are picked up from the midpoints of the primary winding of the TPZ transformers. In order to create the phantom circuit chol:es are more frequently used. With a complete equivalent circuit from the point of view of symmetry and equality of the halfwindings of the transformers TP2 and Tpl - the magnetic fluxes created by the signals of program IV and the voltage as a result of asymmetry are equal to zero in the circuits of programs II and III. The subscriber network is made up of a four-pair cable. In each subscriber - set a pro~ram switch I is provided by means of which the corresponding _ program is selected~ Ho~wever, considering the high signal voltages in ' such a system, careful symmetry is requirec~. Asymmetry of th~ circuits caused by deterioration of the state of the cable (for example, as a result 5 ~ FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED F~R RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 ~ FOR OFFICIAL USE ONLY . l~aameaax~ ~ (2) ' ~ . . . . . . ~ . - . ~1) ava,~~rru Pccipat~amrn~~c~ anK ~ ' : . ~ -~3~ j~, p ~ . . . ~ ~ ~ ~ . . ~ ro, (4). l,'v D ~ ! I 1 _ i ~5>" t,~ , ' . ~ . ~ ' � ~ TP~ ~ Tps - . c~) ~rA,,.~. ~ . a y ~ : ~ b - I , . . _ , ^ ~ - ' ~ ~ . : : . ~ (7 } A1ds~~~R eu n~ b ) . . . : . _ _ : Q . f. ~ ~ - - ~ ~ ' ~ i{~ . a ? . Figure 1.2. MPB system using physical and artificial large- - capacity cable networks - Key: 1. Kepeater station 7. Subscriber sets _ 2. Distribut~ion network 8. Subscriber network , 3� Iprogram 4� IIprogram 5� IIIprogram ~ 6. I~program _ of a change in insulation resistance) and also failure of the transformers will lead to a decrease in the crosstalk attenuation betweQn them. An important difference between the phantom circuit and the physical circuit is that they have different primary equivalent parameters. By comparison with the physical circuit, the resistance of the phantom circuits is approximately half; the inductance is approximately a third, and the - capacitance of the line is approximately threefold. This leads to the fact that the frequericy characteristic of the phantom circuit is worse than that = of the physical circuit. In addition, as a result of increasen capacitance, - overleading of the terminal stages of the program repeaters is possible. 6 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED F~R RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFI~IAL USE ONLY Fig 1.3 shows a version of a phantom circuit which eliminates the indicated - def iciency. ~ ~ 9'cvaamt~Eyarv cma~~ (1) ~ ~ . . . _ - r~ g a ~ . 0 . ~ . , ~ ~ . I _ . _ ~ ~ L--- . . ~ . . . ~ ~ c2) (2) . , . . . . . . . . ~ � ~QP ~tP ~ � . . . _ . ~ : ~ ~ � . . _ . : . � po~ 3 0 0 : ~2 ~2~ ~ - - - ~ c'. . ,4p. _ ap_ P~ . , . _ ~ ~'a~a ~'r � s0� ~ ~ n d. - . p~ , .~1 ' lr a6oHaMm~~rrrr 7~, - qcnporiomlaN (4) _ Figure 1.3. Version of the MP'B s~stem using the phantom circuit Key: 1. Repeater station 2. Choke 3. Transform~er 4. To the subscriber sets The signal voltage at the beginning of the phantom ci:cuit is cut in half by comparison with the ordinary circuit, and on the receiving side at the subscriber their level is equalized. This is achieved by selecting the corresponding coefficients of the output and subscriber transformers. As - a result, favorable operating conditions are created for the repeater, the frequency characteristic of the phantom circuit improves, which now is - loaded on both ends by a corresponding lower load resistance. In the given = _ system the phantom circuit is created by using four chokes with midpoinLs, and the signals of program III are transmitted through it. As illustrated in Fig 1.3, programs I and II are fed to two subscriber sets A and B. When selecting programs I and II, the voltage is fed from the - volume control Pr to the entire winding of the subscriber transformer Tpab 7 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY (positions 1, 2 of the swirch II). In the case of selecting a third program - (position 3 of the switch II) only part of the primary winding of the trans- ` former is connected to the volume control. As a result, the~subscriber does not notice the difference in the voltages, independently of which ctrcuit is used, although only half the signal level is fed through the phantom circuit. The practice of creating phantom circuits indicates that the stable crosstalk attenuation does not exceed 50 decibels (with a requirement of to 70 decibels). Tt must be noted that the indicated version of ths system can be used for the single-element networks in the repeater-subscriber section. Its applica- tion also on the existing distribution network is possible when it is - necessary to increase the number of programs transmitted to the subscriber distribution network. In this case only the subscriber network will be = changed, and the distribution lines will be kept the same. 1.3. Mult~program Wire Braadcast System over the City TelepY~one Exchanges General Information Inasmuch as the MPB system is based on the city telephone exchange, measures must be adopted to see that they are completely compatible technically = and organizationally. When building the MPB system, the following require- _ ments are imposed on it: - 1) Introduction of it nust not interfere with the telephone circuitry or have any noticeable effect on the quality of the telephone conversations; 2) The MPB system equipment must not interfere with privacy of the tele- phone conversatior?; ~ _ 3) The MPB system must be designed so as not to introduce significant changes into the telephone and office equipment. Commutation Type MPB System - Inasmuch as each subscriber line is used little in ~:ime, the idea has come up to use the telephone system to transmit broadcast programs. In order ` to create such a system, low-frequency repeating equipment has been installed at the automatic telephone offices [12] for each WB channel, and _ station switchboard equipment l:as also been installed. A receiver made up of a program selection unit, low-frequency repeater and loudspeaker is installed at the location of che telephone network subscriber. The program is dialed si.milarly to how this is done in telephone communications, as a result of which the subscriber telephone line is disconnected from the telephone distributing fr~~C a~~u ii. ~onnected to one of the broadcast repeaters. By using tr~is technique, the telephone network is used both for telephone conversations and for broadcast jointly, but not simultaneously. ' In order to eliminate the interf erence of the broadcast program sign,als on other telephone circuits the voltage of the broadcast signals is _ 8 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY _ kept small, ar_d their ~amplification occurs in the subscriber receiver. - However, the gain of the receivar must be so smull that it does not inter- fere with privacy of the telephone conversations. The danger of hearing - telephone conversations increases with a decrease in the crosstalk attenua- tion between the .:able circuits. A significant disadvantage of this system is the fact that the subscriber is offered the possibility of using the network to obtain only one type of informatiion in each time interval: when a telephone call comes in the sub3criber must int~rrupt the broadcast - transmission. Fig 1.4 shows a system which implEments the indicated MPB system. This version of the system was proposed in the USSR in the 1930's by A. V. Vinogradov, but it was not implemen~ed at that time as a result of a number of technical deficiencies. - � AODNCNG9~ 1 ~ , : . . , ~ ~CrMhCf~,YDM,y flCl?7?ll1WIM ~ 6 ~ _ { r ~P (3) ~ . . , " ~?~8 4~ , . r r~va- ~i~B'3 ~ llnpe~sm~ f ~ . . ( pI1C~4F ~ ~mel16 ~Rpr. ~ ~ - .~DCS~G ~ ~M/IB~I~ I PUt 0 Op'! .~QA?N rM/!Bd yNy ~(12~ ~ ~8) ' . ~ ~ : . . _ 1 ~ ~ ~ . . : . ~ . ~ ~ . . ~ j. i r r ~ - ~ ~ ; d~~ur~mrnac npc~pa,~M /IB g � - ~ . . _ Figure 1.4. Schematic diagram of low-frequency WB over a telephone .line with program selection Key: 1. Sub~criber 8. Program selection relay 2. Telephone line 9. WB program repeater 3. Telephone 10. MPB receiver 4. MPB 11. Low-frequency repeater 5. Mode of operation relay 12. MPB program switch 6. To the connector _ 7. To the preselector _ High-Frequency MPB System The procedure for us.ing the telephone network for each system consists in = transmitting the broadcast programs on the high-frequency band. - 9 ~ FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY Let us consider the factors which must be considered i?z creating such an MPB system. First, it is necessary to consider the possibility of broad- - cast interference from the telephone systems as a result of the station switcliing equ:ipment and the subacriber dials. Low-rrequency filterfi cc~nnectecl on botli encle muat uttenuntQ the effect of Chiy tnCErrCerence in t}iQ occupied broadcast band. - Second, interference is possible from the radio broadcast stations, the level o� which determines the minimum signal voltage at the subscriber. Thirdly, it is necessary to consider the different attenuation of the side - frequencies causing noticeable nonlinear distortions. For eff icient use of the AM repeater power, all of the lines connected to the telephone office are grouped depending on the length of the line, and each group has the - requirQd level of high frequency signals at the input to maintain a suff icient signal level at the end of the line [12]. I The schematic illustrating the principle of the construction of a high- frequency wir.e broadcast system is prQSented in Fig 1.5. Tra~smitters each with its own program, are installed at the telephone office. Tr~e _ broadcast programs can reach these transmitters from the informaiion soiir~es - by various paths. 'Che l~ign-frequency signals from the transmitters are fed to common bust.s and by means of the station connection filters (SCF), to the subscriber tele- phone lines. The station connection filter contains high and low-frequency ~ filters cormected in parallel. The low frequency f ilter does r.ot pass the - MPB si~nals, and it also eliminates the effect of the interference caused by the commutation devices of the station. The high-frequency filter prevents penetration of the low-frequency signals into the high-frequency equipment. The subscriber f ilter (SF) is installed at the end of the subscriber telephone line. It is also made up of high-frequency and low- frequency filters having analogous purpose. The terminal receivers are connected to the corresponding output. In order to simplify the station connecticn filters and the subscriber filters, inasmuch as they are an - = important element of the system, the fr~quency band occupied by the MPB signals must be selected as far as possible from the frequency band occu- � pied by the telephone channel. Considering the admissible damping on the city telephone exchange lines and the possible use of radio broadcast ` receivers, the frequency of the long-wave band is selecred from 150 to 350 kilohertz. - Fig 1.6 shows the structural diagram of a six--channel MPB system. The six- carrier frequencies are modulated in the transmitters by the corresponding signals of different programs, and they are transmitted through the filters Cl-C6 to the wide-band high-frequency repeater or channel repeaters KY if greater power is required. The carrier voltage of each broadcast channel is about 5 volts. When using signal-channel repeaters, it is _ 10 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ~ � 7b~orm? sa,~a,rq~ Po~rx~4~v?[2~ ASonrHm ~3~ . ' - . ~1.~ a.vs;:s~a ' - ' { ' ; . ~.W~r1/~ % 1'6 ~ ~ ~ , . ' ~ I I ~ ~ ~ 6//~ ~ " � ..E4~ ~ ' - ' ~'vc~re~m ~5) ~ I ~sv ~ ~a' ~ (7) /ru~NAT ~ ~ r ~ . . . . - ~ ~ . F . ~ ~ ~ ~ ~ ~ ~ - ~ . , . ..-1. . _ � ~ ~ ~ I ~ ~ c8> . n, ~ . . ' ~ ~HVr9 I ~ . ~ ' c-~ l ~ . . . . ~ ' _ . . . ~ ~a ~ . � i f .._:I . . ~ , ~ ~ � ~ ~ naFy~N . ~ . . ~ :3 a6oae~ra,rr~v~ ~ ~ ~ , ~ ~ . _ - . . . . n.~- ~ (].1) ~ . - I . ; . : , . . . . . . . ~.f~~.~ . . . . . . ~ ~ ~ . - ~ ~ (1~)a B OG,~ae ~rab?~i Ar,~eBM~. ~i~ . ~ . ~ ~ . , . � . Figure 1.5. Structural diagram of the high-frequency MPB system based on the telephone network Key: 1. Telephone office 2. City telephone exchange distribution iines 3. Sub~criber 4. To the automatic telephonE of�ice selectors 5. Station connection f ilter 6. High-frequency filter 11. To the other subscribers 7. To the MPB receiver 12. Co~on buses in front of the MPB 8. To the telephone set 13. 2~B transmitters 9. Low-frequency filter 10. Subscriber filter possible to obtain a volta~e of about 25 volts at the output of each channel. Dep~ending on the length of the line, one wide-band repeater can feed up tn several hundreds of subscriber lines. 11 FOR OFFICIAL USE ONLY I APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ~ "o�~ cl> . . - . . ~ - ~ - " i ~ , = ~ . . IPacnpcdenvsmend' C~11dN1(UONNIJLI - ~ ~ N~c u~~rNd ~r~a6mp ( ) ~ 3 . . . ~ . � . v E - _ ~ . _ ~ iE . , . . . . ' . - ~ ~ . , . ~,t - . ' _ ~ _ ~z ~ . : " ' . ~ . ~ , ( ~ . ~ . . _ ~Iep-~r~t M ,~r~rmo- ~ par - - - S/ ~ X~ I ~ ~s-mcnrc v . - e~ ~1d~S~ ~p~~. . D D ~ ~ ~ ~,J g I ~j ~ o - . D ~a , ~ . _ ' ~ a ~ ~ E: b "~t D ~ D (i3) � ~ ~rly~'R 8 Qy ~ _ :r~ D 9� . : ~ ~ ~'i ~ I ~ . . _ ~ . ~1~i D ~6 _ . � � 3y0 ~ ~ $ : � ' ~ ~ . = . ; ~ ~ p ~ . ~ ~ ~.:Il~~il~ , . . . . BXO~ NY ~ ' . ~16) . ~ (1.5 ) . . ~ Figure 1.6. Schematic of low-frequency MPB - Key: 1. Telephone network distributing frame 9. Repeaters 2. Distribution buses 10. Filter outputs - 3. Station filter 11. Wide-band repeaters 4. To the switchboard equipment of 12. Distributing transformer the telephone offices 13. To the other telephone offices 5. Transmitters 14. kilohertz 6. Modulators 15. Low~frequency input 7. Filter inputs 16. Channel repeaters ~ 8. ~ = filters 12 - FOR OFFICIAL USE ONLY - APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFYCIAL USE OIdL~Y ~ , � _ . ~ ~ . ~ ~~~,~6x~ y~~,~~~ . ~ - . ~ ~l>> . � cls) Tq c qcnr-E~it dirA nco~Qdre~ (ig) . ~ ~ ~ N~ nc~eX � Ap ~~a- ~ y~mp~ricm0o . �NrmeA~ ~ AodX/liOilON(dp I ~ j"- ~p-~ . ~ (20). ~ ' (22) I ~21~ L._. r ~ ~ T!! . - ~ ? u�n m,~o ! ~ ~ c~I.~o ~ ~ . , ~ ~ - dna0br-. ~23). " 0~ ~ ( ~ u j 1-- - n~~ �ap~,uwb~ _ . ~ Mns . L. c22~ , ~ ~ ~ ~ Ilar,~ymQmop~~25~ ~ j_ _ Coanacya ~e ' ' � ~ . . . w w , yc~%pou~cm~o (26) - . ~ I ycmpcucmOo nadxn~yen?ua ~ L; . J ~zz~ Mna ~ . . /y mp p~ � . PuducnpueM . � � . - (30) i 29)~ ~ ~ . /Ip-~ ~22~ - - . . - ~ ~ ~ ~ L. . . ~ ~ ~ . . . . . . ~ ~ i . . , i - ~p_~~22> - . ~ . ~ . . ~ . ~ - , . . . . r� ~ . . . . - . ~ ~ ~ ~ ~�~-,~c22~ . . . . . . . . _ . of the city telephone exchanges Key: 17. Subscriber line 25. Switchboard 18. Subscriber sets 26. Matching device 19. Telephone with interference 27. MPB connection circuit = suppressor 28. Radio receiver 20. Fuse 29. MPB 21. Device for connecting the MPB 30. High-frequency transformers 22. Receiver 23. Telephone with MPB program selection device 24. Input filter 13 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY The complex made up of six single-c}.iannel repeaters can be serviced by several thousands of subscriber lines. On the receiving side the MPB signal~s can be picked up on a special receiver or a long-wave band ratio broadcast receiver. Fig 1.6 sho;as versions of the u;ae oF an ordinary radio broadcast receiver as - the receiver. It is connected to the MPB network by a device made up of a symmetric transformer and switch per.mitting conversion from reception over the MPB network to radio reception by coaxial cable (the subscriber line 1). - It is possible to connect several receivers tu one subscriber line through the matching device (line 3). If part of the sutscribers use the services of the MPB system of the switchboard type, and it is necessary to send high-frequency MPB signals over the same subscriber line, then in addition to the matching device it is necessary to connect the low-frequency input - filter in front of the telephone sets of the subscribers using the switcl?- board type system (line 2). - A special MPB receiver having high acoustic fndexes can also be used. It is constructed by the direct repeating scheme and is made up of filters tuned to fixEd frequencies, a detector and repeater. - Co~isidering the organizational principles of the MPB system over the telephone network it is possible to note that the filters introduced on both ends of the Iine are important elements providing for the absence of - influc~~ce of the systems on each other (tne telephone and broadcast systems), - The introduction of the filters increases the ohmic resistance of the lines for the telephone systems with centralized feed, it increases the damping of the low-frequency telephone conversation signal. The attenuation in the low-frequency f ilters must not be more than 0.2-0.25 decibels. In this case the quality of the telephone conversation transmission will not be negatively affected. On the other hand, as was pointed out earlier, privacy of the telephone conversations must not be disturbed. In Fig l.b it is obvious that the voltages of the high-frequency signals are fed to a common bus to which the high-frequency station filters are connected. Thus, the subscriber lines connected to this bus are connected to each other ' through the low-freauency station filters, and there is a danger of intelli- gible crosstalk. In order to avoid mutual influence betwepn the subscriber lines, the equivalent resistance of the distribution transformers on these frequencies is made small. The attenuation on the low-frequency station filters on the order of 90 decibels is entirely sufficient to guarantee i.mpossibility of hearing intelligible telephone conversations even with the help of repeating equipment. It is possible to hear conversations only in an emergency when all of the low-frequency f ilter coils are short-circuited. 14 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY . ~ 1) ~l~ ~4TC f ~ � ' i ~ . i ' - ~ i ~ , ~ ~ ~ ~ ~ . ~ t~ / ~ . ' , - . i _-t~ , - ~ . t ATC _ . : . ~9TC Figure 1.7. Structural diagram of the construction of the MPB system over the city telephone exchange lines _ (without junction formation): 1-- central wire broadcast station; 2-- terminal wire broad- cast station; connecting lines of the city telephone w exchange used for MPB; connecting lines of.the city - telephone exchange u~ed only for telephone communications Key: 1. automatic telephone office Depending on the structure of the city telephone exchange, two versions of constructing the high-frequency MPB system are possible. The first version is for division of the city telephone exchanges into districts constructed by simple junction formation by the principle of "each-to-each" couplings between the automatic telephone offices. The second version is with . complex junction formation of the city telephone exchanges of large cities with several simple networks of district city telephone exchanges. The structural diagrams of such MPB systems are presented in Figures 1.7 and - 1.8 respectively. The MPB system uses frequency multiplexing of the connecting lines between the automatic telephone offices and the siibscriber telephone lines in both versions. The multiplexing of the connecting lines is provided for over a separate pair in the interoffice communications cable isolated specially for this purpose. The subscriber lines are used _ simultaneously for MPB and telephone conversations. In the first version a central wire broadcast station is set up at one of the automatic telephone offices, for example, 1. The broadcast program signals are fed to this automatic telephone office from various sources: the radio broadcast equipment r.oom; from local studios and isolated receiving stations. In the second version the central wire broadcast station is equipped either at an automatic telephone office or at the incoming communications junct3.on (3,4). The terminal wire broadcast stations which service the subscriber network of the given automatic telephone office are set up at the remaining auto- matic telephone offices (2). The structural diagram of the equipment for the central wire broadcast station is presented in Fig 1.9. It includes the following: program - sources 1, a transmitter complex 2 made up nf modulators for each program; 15 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ~NLY band filters 3; multichannel repeaters 4 and high-frequency matching transformers 5. The multichannel repeaters can be installed to feed several connecting lines or one having high attenuation. In a~.dition, terminal wire broadcast station equipment with single-channel repeaters 7, with band filters 3, station subscriber filters 6, the number of which is equal to the number of multiplex subseriber lines, is set up to f eed the subscriber lines of the given station. ' ~b~ RTt t (b) ~PJr J . . - ' I ; - . : ; . i ~ s y ~ ~ ~s ~ ~c '~c~ y~C ~ ` ~ _ (b) ~a~ ~b ~ : . 9BC ` yHC ~ ; . ~ . ~ i~~~ _ ` i i % ~ ~ ' i - i . ~ i . - ' ~ ~ . � ; _ . ~t qfCt ~ . ~b ~ ~tc ,vrcl ? . Figure 1.8. Skeletal diagram of the MPB network over the city telephone exchange lines (with junction formation): 1-- central wire broadcast station; 2-- terminal wire broadcast - station; 3,4 intermediate wire broadcast stations; connect- - ing lines of the city telephone exchange used for MPB; connecting lines of the city telephone exchange only for telephone ~ communications Key: ~ a. low frequency b. automatic telephone office c. UIS outgoing comm~~nicat~_ons junct~on; WS incoming communications junction - With respect to the isolated physical circuits (the connecting lines) - between the automatic telephone office from the repeaters 4 to all other _ ATS-2 [automatic telephone offices] high frequency broadcast prog.ram signals are fed. In order to equalize the broadcast signal attenuation in the different channels, equalizing circu~ts are installed at the ead of - the line. The structural diagram of the terminal wire broadcast stations is presented in Fig 1.10. After correction (the equali.zing circuit 1) the high-frequency signals go through the band input filters 2 to the - single-channel repeaters 3 where they are repeated to the required level and are added by means of the signals in a common load in the form of high- frequency transformers 4. Then after grouping, the signals are fed to the station subscriber filters 5 for distribution over the subscriber lines - running to the automatic telephone office distributing frame. 16 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY , _ ~1~ ~ + ~ -=C/l . ~2~ � A?~rr~d7uoyKOy ' � il~,rydo0arup~l~ . 3 . . y 0 ~ ~ pp~ (3) I n' ~ . ~ '(5) �v (4 - D ti ~ d ~ , - ~ n ~ D ~ ~ ' D ~ . p .Y- D ~ s 6 ~A~6~ . r n ~ D ~ - B n ~ J r t~~ a p f ~ Figure 1.9. Structural diagram of the equipment for the central wire broadcast station for MPB over the city telephone exchange located at the automatic telephone office - Key: 1. connecting line 2. to the station equipment of the automatic telephone office 3. automatic telephone office distributing frame 4. low frequency 5. high frequency 6. subscriber line 7. program For the city telephone exchange with complex junction formation (Fig 1.8) where the junctions for the incoming and outgoing communications exYst by means of which communications are realized between the groups of district automatic telephone offices located in various junction districts another station object is introduced the intermediate wire broadcast station which is organized in the incoming or outgoing communications junctions. The structural diagram of the intermediate wire broadcast ~ station equipment is presented in Fig 1.11. The high-frequency amplitude- modulated signa.ls are fed over one of the interstation communication lines in tandem through the intermediate wire broadcast station to the frequency equalizer, and af ter repeating they go over the connecting lines to the automatic telephone office or to the communication ~unctions. 17 FOR OFFICIAL JSE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY . � ~ ~ . ^ ~ . " (3) A'cr.~a,rqreHyca~/- ~ ~ . . . : ~PYIoB ~rtax~ . _ : _t~ ~ : _ . ~ . ~ . . . . : . ~ ' ' : . . . . (4, t~ ~ Nv (5~ . . . , . . . . , . : ' ~5~ Ny ~p~l . . ~ D 6 a . ~ p ~ ~ s I ~ ~q . . ~i~ - ~ f ~8~ ~ C/I ~ D y eK ~ D ~ ~ y s 'RJI(~~ - ~Z j . . _ ~ ~ ~ ~ ~ D ~ ~ � ~ - . . ~ D ~ . . � _ ~ a a s ' ~ ~ a" ~ ~ . . ~ Figure 1.10. Structural diagram of the equipment of the terminal WB station for MPB over the city telephone ~ exchange located at the automatic telephone office Key: 1. connecting line 2. switch 3. to the station equipment of the automatic telephone off ice 4. automatic telephone office distributing frame 5. low frequency 6. high frequency 7. subscriber line ~ 8. subscriber - When the equipment of the central wire broadcast station is located at one - of the communications junctions, the structural diagram varies, and only the terminal wire broadcast station is set up at all of the automatic telephone offices. . ~ . . _ , U ~ 2 . QP ~1~ . � . . j ' ~ . . . . I[fl Ay (3) ASI Ay . ' ' ' ~V - f . � t Blt ~ ~1> 2 i ~1~ . ~4~ - : . ~ ' ~ ' . . . . . . `n (5> TA (6) - U"" % - ~ - . ~ . . Figure 1.11. Structural diagram of Figure 1.12. Circuit diagram the intermediate wire broadcast station of the receivers equipment placed at the outgoing communi- Key: 1-- group rectifier; cations junction (incoming communications 2-- subscriber set; 3-- junction) low-frequency filter; 4 Key: 1-- connecting line high-fr equency filter; 5-- 2-- switch ~ connecting line; 6-- telephone 18 - FOR OFRICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY From the investigation of the indicated diagrams of the MPB system it follows that it turns out to be rigidly connected to the telephone communications system. Common station and line equipment are used. However, in order to receive the MPB broadcast program aignals it ie necessary to be a telephone network subscriber. As was demonstrated in Fig 1.6 there is a method of f eeding the broadcast _ signals to several subscribers over one telephone pair. The subscriber uses an individual receiver with autonomous feed as the receiving set. The system using the subscriber line for simultaneous f eed of the high- frequency programs and feeding the subscriber sets from a common rectifier is also of interest. This type of system is presented in Fig 1.12. For simplif ication of the subscriber set under new conditions when semi- conductors are being widely introduced, it can be expedient to use the group rectifier and the autonomous network for simultaneous feed and supply of the MPB signals. As is obvious from Fig 1.12, the MPB signals are fed from the automatic - telephone office over the connecting line to the telephone. Simultaneously, this line is also used for telephone communications; here the telephone is - connected by the usual method. Through the special device the high- frequency f ilter shown in Fig 1.13 - the MPB signals are fed to a common autonomous network into which the feed by direct current is also input. Requirements are imposed on the high-frequency f ilter to connect the two networks electrically and not pass low-frequency speaking signals and call signals to the autonomous network. The direct current feed goes to the autonomous network from the group rectifier through the low-frequency filter (Fig 1.14). The rectifier is fed from the household electric net- work. iw ~ ~ ~ I I. L 1)_~B~ ' i . - _ Figure 1.13. Filter circuit ~ gram Key: 1. high-frequency f ilter For reception of high-frequency MPB signals, the subscriber set is used, the simplif ied schematic diagram of which appears in Fig 1.15. The high- frequency signals are fed through the high-frequency input filter to the detector and the low-frequency repeater. The constant feed valtage is fed to the repeater of the subscriber set through the low-frequency filter which does not transmit the MPB signals inasmuch as it has greater attenua- tion with respect to high frequency. The attenuation is insignfficant for 19 , FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4 FOR OFFICIAL USE ONLY _ direct current. The expediency of creating the investigated autonomous network is especially obvious if the repeater in the subscriber set is macle from transistors. It is necessary to have only one voltage rating _ for operation a DC voltage to 50 volts is sufficient. The networlcs with this voltage simplify the satisfaction of the safety engineering conditions, . and therefore they can be made of cheaper materials. On the ~ther hand - the receiver is also simplified. It does not contain circuits under dangerous voltage, and the feed unit is absenC in general. As a result, the structural design is simplified, and the ~ubscriber set becomes cheaper. In the subscriber set designed to receive several programs, a switch is used. A deficiency of the investigated system is dependence of ' the operation of the MPB receiving network on the state of repair of the autonomous feed network. _ L ar ~ ~4~ ~ - .~1) -.i ~ ~ ~ ~ I ,Q. yNy - 1 . ~ ~ ~ � ~ . ~ ~2~ ~ , 1 ' . � ~ ~ I " . ~ ~Ny (2) ~ - i ~ _ ~ Figure 1.14. Diagram of a group Figure 1.15. Structural diagram rectifier of the receiver Key: Key: 1. group rectifier l. input 2. low-frequency filter 2. low-frequency f ilter - 3. detector 4. low-frequency repeater 1.4. Switchboard Type Multiprogram Broadcast Systems Based on th e Television Distribution Network At the present time in the ~oviet Union and abroad there is a great deal of interest in cable television systems. This is connected with the fact that the problem of improving the quality of television broadcast and increasing the number or programs is diff icult to realize as a result of "crowding of the airwaves." In addition, microwave television f inds it difficult to get along with the new civil construction with its multi- story complexes of different heights constructed from reinforced concrete, as a result of which the so-called "television shadow zones" and multiple - repeated reflections of the high-frequency television signals appear. 20 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4 FOR OFFICIAL USE ONLY t in addition, the movement away from individual antennas is connected with the esthetic requirements of arch~.tecture. Collective cable television - systems are appearing on the scale of the individual buildings, the individual block and microdistrict of the city. Fig 1.16 shows the structural diagram of a WB system constructed on the basis of the television distribution network made of a large-capacity symmetric cable for transmitting low-frequency broadcast signals. Tt is designed for simultaneous transmission of the broadcast signals and the - television signals to a large number of subscribers over one physical network. Ncmoyxu ' . ~ � ~ . � !n~/lCBt[3. Qm uC1170 HIUfCB I1lC~1~DlL3(LON.907J (1) cuzHr.nod ~ 3ByKOBOdO OCIL(0/Ae/ldN6/X G1fltNQQOQ - ~r ( 3) Pacnpedenume~~Har~ cem~ . J Om ucmoyau- 1 ~r4~7 30 ~~46i L,- . ~ y n n~i ~Z ~t ~~t ~t ~ Z G, Be~~TC~a- ~ I ! I ~ ' N6!X C!lzXd/M~~ J ~y~ ~ (4) c6) ~ c6 . � ~ NrN c~rrt y� po~2r,m a /fcmOVN OCUd~UA , ~ " � H~n~ (5) /ra0o~eam,cxuM ycmpotit~Od~ ' . (S) meneovd~~v~ ~ ` Figure 1.16. Structural diagram of the low-frequency MPB over - the television. distribution network Key: ~ ' 1. Source af television signals - 2. From the television and sound broadcast signal sources 3. Distribution network 4. From the sound broadcast signal sources ~ 5. Source of broadcast signals 6. Subscriber connection circuits 7. To the subscriber broadcast equipment 8. To the subscriber television equipment The investigated MPB system must provide for transmission of television - and broadcast signals along the distribution line without noticeable attenuation and absence of their mutual effect. In additian, the great difference in frequency simplifies its realization. At the beginning of the line only the sound broadcast signals are f ed to one pair in the dis- tribution network made up of a large-capacity cable, and the television and wire broadcast signals are fed to the others by means of the connection circuit which in the simplest case can be made up of an induction L1 and a capacitance C~. ~1 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 " FOR OFFICIAL USE ONLY The subscriber connection circuits which can service one or several subscribers are used for connection to the distribution line. The inclu- sion of the subscriber connections increases the attenuation of the ltne; therefore the requirement of decreasing the effect of the low-frequency devices on the television signals and vice versa is imposed on it. ~ The diagram of the subscriber connection circuit iF depic;:ed tn Fig 1.16. It contains the inductance L2 and the capacitor C1. For low-frequency signals the resistance of the inductance of the subscriber connection circuit is of significar~e. For high-frequency signals the device is a high-frequency transform This type of device provides for connecting one or several subscribe~ sets without a significant increase in losses to the high-frequency lines. Each indivi3ual pair of the large-capacity cable has its own sound broadcast and television program transmitted over it. For selectionof the program a multiposition switch is used on the subscriber ~ - end. The use of individual circuits for transmitting each program offers the possibility of transmitting television signals of different programs on - one carrier frequency, getting along without selective circuits it makes it possi~-le to simplify the receiver and to use an ordinar~ nonspeaker For the sound broadcast programs. Thus, the advantage of the switchboard system is the possibility of using relatively low-frequsncy symmetric cables and simpler subscriber sets. This type of MPB system has found appli- cation in England. _ ' The investigated MPB system makes it possible to use the simplest broadcast receivers without amplifying (active) elements in the channels, and it offers the possibility of using coaxial cable as the distribution line, for example, to create a matched te~evision and WB network in an apartment building. There are MPB systems which provide for the possibility of all-around use not only of the distribution network, but also other elements and ~unctions of the system, for example, transmitting station equipment and receiving subscriber sets, as a result of which the system elements, and in particular, the receiver, are simplified. A version of such a system is depicted in Fig 1.17. The distribution network is made up of the 1,2 large-capacity cable. Two - different television programs are f ed to two physical circuits shielded _ from each other, on the same frequency; the sources of the sound programs which can be sound accompaniment of television programs and simply broad- - cast programs, are connected to the circuit simultaneously. The station equipment of the system includes the carrier frequency generator I' on 6 megahertz. The output of the generator is fed directly through the - buffer stages to two modulators to which the signals come from the video program sources in the range from 0 to 3 megahertz. The modulated signal 22 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ~ ~ ~ ~ � 3 . � . � ~ ' � ' . . . . � r ~ , . . . C~S O t'+ . � . � ' 1~ O ~ ~ ' . ~ ~ ~ ~ O f~-i ~ I _ ` q� I .n o�10 ~ . e cv ~ ~ ~ o ^ v g ~ j V�~" ' O i Q~~t ~ N N t~ I ~ j ~y~ 'o i ~y ~ b ~ ~ ~ I ~"t ` I~ � j I o 0�1o u i i Q~ ~ ~ . ~ ~ ~a ~n ~ __J ( j R~ ,.~.1 ,N-t u~i ~ ~ ~ N ya ~ ~ ~ ~ ~ ~+I I~' ' eat~ I ! = y= Q ~ ~ w ~ .~E ~ ~ ----J ~ � ~ x s~ ; � . u i m ~ ~ b _ ~ ~ ~ . � , , � ~ ~ y ' ' o p ~ j v a ~ a ~ a v~ . i.i O~ ~ 1~ tU M Ol (!1 r'~ ~ r'~ v ,r~ ~ ',i~ � ~ �w u~ b u ~ ~ aa �~a~i~ F ~ ' ~ . ~ i - " ~ � . ~ . ' u r~~ u ~ � - 1'~ ~ ~ . � ' ' - ' y � ~ 3 O ~ ~ _ . ~ . Oal r~l ' v ` 4-~1 G~! I ,I , i ~-''~i 1~ y'~ ~ i = ' ,~3 aa'i ao ~ L _ f"1 _ . o cv - ~ ~ ~ w ~ � . � _ ~ I ~ N ' L G! I CCl � ^ },i v ~ ~ ^ , ~ ' , ~ r. . . J~J N i-1 C~.+ iJ . ~O ' ~ ' . � . � O rl ~ . a v ~ ' ~ v~ � ' . i _ ~ N LS GaJ F+ U I (2) . I (4) . . (6) Ay Ay ~6> ~ ~ . Figure 2.1. Functional diagram of a wire broadcast system Key: 1. Source of broadcast programs 2. Preamplif iers 3. Broadcast feed channels - 4. Powerful repeaters and transmitters 5. Wire distribution network - 6. Subscriber receivers Thus, the wire broadcast system has three distinct sections (Fig 2.1). The first section I is characterized by low broadcast signal levels. The formation of the program and the transmission of the signal to the second section II takes place in this section with given quality indexes. Basic repeating (obtaining of the defined power) of the broadcast signal takP~ place in section II with minimum distortions for the low-frequency outgotng signal and commutation of it to the distribution network. - 26 FOR OPFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY The third section is the fastest section III. This is the wire distribution network which realizes distribution of the broadcast signal power over the cable or overhead line networks to the subscriber receivers, without intro- ducing noticeable distortions into the quality indexes of the broadcast signal. - The receivers are passive subscriber units loudspeakers, which convert - the electric signals to acoustic signals, or special receivers with active elements. The subscriber sete are designed for the use of a defined power of broadcast signal and reproduction of it with given quality (acoustic) indexes. There are several versions of constructing the city WB networks. They all have the above-enumerated functional sections, but they are distinguished by the volumetric indexes: the number of service subscribers, the nur~ber of program feed channels, the extent of the connecting lines for the first , section, the number of stations, the power of the repeaters;and transmitters and their nu;nber, the presence of passive power distribution elements and the number o~f transformer substations, the different types of distribution lines and their volumetric indexes for the third section and also types of subscriber sets used. The investigation of the development of the WB [wire broadcasting] in the cities indicates that the first and third sections have changed little. Great changes have occurred in section II. The basic purpose of these changes has been most advantageous distribution of the active elements of the network over the territory and insurance of mutual redundancy of the _ active and passive station equipment [3, 4, 5, 7]. Depending on the structure of the station and line installations of the WB network, they are divided into several types distinguished by their - structure. It is necessary to point out two types of indexes which determine each WB network. The first type characterizes the electrical data of all the elements and assemblies ir. the final analysis influencing the quality of the electroacoustic parameters. The second has no influence J on the quality, but characterizes the structure complexity of the net- work. Let us assume that the electroacoustic data must not depend on the type or complexity of the network and must be insured in equal measure for.the subscriber. This is insured by calculating t~e elements according to the recommended procedure and the electrical design standards. Let us consider ~ only the volumetric indexes characterizing the structure. _ The simplest diagram of the city network is presented in Fig 2.2. The following are indicated in the diagram: = YC WB repeater station. The complex of repeating, transmitting and commutation equipment (the transmitters of programs II and III of the TPB networks) is characterized by the type of repeating equipment and the complexity of the commutation equipment; 27 - FOR OFFICIAL USE ONLY ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY - P~ the distribution feeder line. The number of distribution feeder lines depends on the number of service points and density; AT subscriber transformer. The number of subscriber transformers depends on the number of service suhscribers and the density of the load; H~ intrabuilding distribution network char~cterized by the wire length and number of. subscriber sets; AY subscriber set; uCn~ central wire broadcast station realizing preamplification of the broadcast program signals, feed of them to the repeater station and providing for the functions of monitoring the entire WB network. It is combined with the WB repeater station. Tlxus, the structure of the network is characterized. by the following data: - the number of connecting lines of the central wire broadcasting station to the repeater station; the number of repeaters (transmitters); the operating power P required to service all of the subscribers; the number ~f distribution feeder lines; the number and power of the subscriber trans- formers; the number of service subscribers N. - , --1 ~ - r qcna ~ c ~ . . . ! ,5 ~I . ~ ~ ~ - ~1~AT ~n ~ ~ P~ ~2 (2~- yG~6 J . . . . . . . . (2) pT AT (1) - . . AT ' 7 ) - Ay . . I . 1~c ~ ~ ~ Ays~~ . . c~~ Figure 2.2. Diagram of the centralized WB network Key: 1. Subscriber transformer 6. Repeater station 2. Distribution feeder line 7. Subscriber set = 3. Central wire broadcast station 8. Intrabuilding networks = 4. Program feed connecting Zine 5. Remote control and remote monitoring connecting line 28 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 _ FOR OFFICIAL USE ONLY ~ qcne~ (1) . I I c2~ �I ( ~~L _ . I y (4 ) (3) ~ N~3r ~ ~6~ - T/l, TIh T/!r 7 ) i: i i i 1 ~l p': ~ p'~? ~ j''~ - Figure 2.3. Diagram of the centralized WB network with two-step power distribution - Key : l. Central wire broadcast station 2. Remote control and remote monitoring connecting line 3. Transformer substation 4. Repeater station ' S. Distribution feeder line - 6. Ma.in feeder 7. Transformer substation This type of wire broadcast network is called a centralized wire broadcast network. It is characterized by the fact that the equipment performing the function of the central wire broadcast station, as a rule, is in the same facility with the repeater equipment and the switchboard equipment of the repeater station. The network has only one active broadcast signal power distribution junction. Fig 2.3 shows a more complicated structure of the network in ~ich the following are indicated: ~ C~T~rIrI - program feed connecting line; nwnber of them depends on the number of programs and the number of repeaters and transmitters of the auxiliary high-frequency programs installed at the repeater station; C.1ITK _ remote control and remote monitoring connection line; the number of lines is determined by the number of controlled ob3ects. In the given case with invariant active station part of the system, the form of the power distribution varies. The power of the broadcast signals from the repeaters and transmitters of ~ the repeater station goes to several local distr{bution networks via the passive distribution junctions of the transformer substations. 29 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY - The line connecting the active distribution junction of the repeater _ station to the passive ~unction of the transformer substation is the main feeder line. The transformer substation is the station passive equipment complex which is used to transmit the power to the distribution feeder lines. The power of the transformer substation is determined by the number of distribution lines, their structural specifications and magnitude of the load. In order to control Lhe remote monitoring of the operation of the transformer substation, connecting lines are used. Tt~e distribution network remains unchanged and is similar to the distribution network of the system in Fig 2.2. Inasmuch as all of the notation adopted previously is kept f~r all layouts of the network and the distribution network is identical in structure, hereafter it will be designated simplified. The wire broadcast network is called centralized with two-step power distribution when it has one active power distribution junction and several passive distribution junctions. The central wire broadcast station is _ territorially combined with the repeater station, which is illustrated in _ the diagrams by the dotted line. Since the main feeder line operates with increased transmission voltage, the range of the system is expanded. The voltage is stepped down at the transformer substation using special transformers. Additional indexes , appear in this network: the number of transformer substations, the main feeder lines, the remote control and remote monitoring connecting lines. Fig 2.4 gives che diagram of the WB ~network in which its station part is altered by comparison with the greviously investigated one (Fig 2.2). In the given case the power Pop required for normal operation of the entire network is distributed among several objects of the repeater station with different value of it. In this system the network structure is characterized by two additional indexes: the repeater station power and the number of repeater stations, and it is called the decentralized network. The powerful repeaters are installed separately in several territorially separated repeater stations which receive the broadcast program signals over c~nnecting lines from a single centralized repeater station (the - centralized wire broadcast station) which can be combined with one of the repeater stations. Here the WB network has several active station power distribution junctions in its makeup. Fig 2.5 shows the layout of the network with further complication of the structure. The broadcast program signals from the central wire broadcast station (as a rule, isolated) are fed to several reference repeater sta- tions at which they are repeated to defined powe and are distributed by means of the transformer substations throughout the serviced territory. � 30 FOR OFFICIAL USE QNLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY : ~ : ~ucne ~ (1) ~ ~ _ ~ . _ c2~ cnnn nr~r c3) . c~rx) cnra~cn~; (4) yCi ~ ~IGZ ~ yC~ - (S) p ` 1 P ads ~ p~di L 111 ' ~it ~ 1:~ ~ ~6~ . ~P~~ .~,P~~ Figure 2.4. Schematic of a decentralized WB network ~ Key: _ ~ 1. Central wire broadcast station 2. Program feed connecting line 3. Remote control and remote monitoring connecting line 4. Repeater station 5. Pop 6. Distribution feeder line . (1 . 6~11Yf T/1 � _C/1TIf Tll . ~ � - qcne . ; ~ cann ~T~ 1 c~nn T"~ . ~ 2~ OyC, \ LO!!C J/~ OyCt . . \ ' P% ~~~o ~!!9; M~ : . ~3~ j ~-~r.Q,p , T/1, T/Ij (4) T/l, Tllt . ~ , ~ ~ ~~~j (5) ~ sA; ~ ~ . Figure 2.5. Schematic of the decentralized WB network with two-step power distribution Key: 1. Remo~te control and remote monitoring connecting line of the transformer substation ~ 2. :;eference repeater station 3. Main f eeder 4. Transformer substation - 5. Distribution f eeder line - 31 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY In this network layout there are main feeder lines which connect the transformer substations to the adjacent repeater stations of the re�erence repeater stations. This method of transmitting the signals to the trans- formers eubstation is called two-way feed of the transformer substations. On Eailure of the main f eeder which is feeding the transformer substation at the given time, the distribution network of the given transformer sub- stations switches to another feeder which has been in reserve up to this tune. On failure of the reference repeater station, the transformer substation switches to other reference repeater stations. At the repeater stations provision has been made for additional power Preserve both in the form of a~eparate powerful repeater or transmitter and in the form of a reserve of installed power of the repeaters or transmitters ~f the reference repeater stations. Continuous operation of the network is insured in this complex structure. The city network constructed by this principle is called a decentralized network with two-step power distribution of the broadcast signal; in practice it is frequently called the improved three-element system. The network has several active and passive power distribution junctions. The - WB distribution network for this structural layout remains unchanged in theory. In the investigated WB network, several other indexes are being added: the number of repeater stations of the reference repeater station; the number of reserve main feeder lines; the powers of the repeaters of the reference repeater station operating and auxiliary (used for reserve for the repeaters in the given station or the rep eaters of adjacent reference repeater stations). Each investigated layout of the network has its own advantages and dis- advantages. The advantages of the centralized networks can include the following: the construction of the station in one location (where it is easier to insure an uninterrupted power supply), simplification of the _ ~edundancy of the active station transmitters, monitoring devices, power- ful repeaters and their maintenance. - Deficiencies include the following: complexity of the distribution network, longer lines and less eff iciency correspondingly, less operating stability of the WB network as a whole. The advantages of decentralized system include the following: high operating stability under emergency situations with high eff iciency of the d~stribu- tion network, simultaneous simplification and shortening of the distribu- tion lines and improvement of their operating reliability. The deficiencies include the following: greater complexity of the: operation 32 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY and maintenance of the station devices and difficulty in insuring autonomous power supply sources. However, the last deficiency is felt less and less in practice, for the reliability of the city power supply has increased. '1'I~~~ modern city WB network.g are aimilar to those deacribed, and, as a rule, ll~c~y ar~~ Ln tl~~ Lorm oL a set of the deacribed eysteme und v~ry in AccordAncc with the development of the given city. It must be noted that unfortunately there are no strict calculated bases for the selection of one version or another, and the remaining, it would appear to be obvious, principles frequently turn out to be contradictory. Thus, centralization of the active station objects is convenient for opera- tion and maintenance, but it implies the application of long distribution lines having increased attenuation and frequency distortions. The applica- tion of one powerful, high-power repeater is more advantageous with respect to expenditures of equipment and maintenance than several low-power repeaters. However, in a number of cases, considering redundancy, this - leads to an unsubstantiated increase in the installed power of the repeater stations. Therefore, the choice of the optimal WB system must be preceded by technical-economic calculation of several versions of the station and line structures. 2.2. Basic Principles of Constructing the Low-Frequency WB City Networks The modern WB network in the cities is built consirlering optimal economic and operating indexes in ac~:ordance with the specific conditions, dimensions, configuration of the city, the number of population, and the prospects for civil construction. ~ In the ma~ority of cities in the USSR with a popula~.ion up to 50,000 (wit~ a number of points to 10 to 15,000) predominantly centralized wire broad- cast networks are being built with two-element distribution network. In - this case all of the repeater, re~eption and switching equipment is concen- trated at one station. The f irst: element of the network is the subscriber lines which feed the subscriber ,~ets, and the second el~ement is the distribution feeder lines to which the building networks and subscriber lines are connected through the step-down subscriber transformers. The rated low-frequency voltage for the city feeder lines is 120 and 240 volts. In larger cities (population to 150,000), centralized wire broadcast networks are being constructed with mixed construction. In such networks, as a rule, there is one WB station in which the basic power of the low-frequency - repeaters is concentrated. Several distribution feeder lines (from 5 to 20) go out from the sta*,ion to supply the subscribers flf . the main residential area of the city and une to two main feeder lines with simplif ied type transformer substation to feed the network located in remote parts of the _ city. Sometimes high-voltage rural type feeder lines with a voltage of 480 to 960 volts are built to supply the network of adj acent populated areas or the suburbs. 33 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4 FOt~ OFFICIAL USE ONLY In cases where the construction of the main feeder line is connected with large expenditures or technical disadvantages, to feed the network of the remo;e part of the city a repeater substation is constructed with remote control and monitoring and program feed from the basic station, that is, - a decentralized network is created with two-element distribution network. In the republic and the ma~ority of oblast centers decentralized WB networks are being built. The station powers are distributed with respect to several ref erence repeater stations. Each reference repeater station feeds several ,transformer sub- stations with a sound frequency power of 5 or 7.5 kilowatts each through the 960 volt main feeder lines. At the transformer substation the voltage _ is stepped down from 960 to 240 or 120 volts and goes to the distributing feeder lines which feed the subscriber network of the part of the city serviced by the given transformer substation. Redundancy in which each sound frequency transformer substation receives two-way feed from two reference repeater stations over two main feeder ~ lines is characteristic of the system. Each of these lines can be operating or reserve. When there is damage to one of these lines the automation response, deenergizing the damaged line and the feed of the transformer substation is automatically switched to the main line from the other reference repeater station which is in a state of repair. In case of any emergency taith the reference repeater station (deenergizing, damage to the connecting line or equipment), its load (tranaformer substation) is remotely switched from the central wire broadcast station to the ad~acent reference repeater station by remote control equipment. When it is impossible or economically inexpedient to build a reserve main line, the reserve f eed of the transformer substation located in a remote = part of the city is provided from the substation block in which the existing repeater equipment is most frequently us~ed. The program feed to all the reference repeater stations, repeater stations and substation blocks, the remote control of them and monitoring of their operation and the operation of the transformer substation are centralized Erom the central wire broadcast station over the so-called connecting lines, for which the telephone pairs of the city telephone exchange especially corrected and selected in the large ~anacity cables are used. _ In Table 2.1 values are presented from the basic volumetric i~dexes of the city WB networks, excluding Moscow and Leningrad. The analysis of the volumetric indexes of the city WB networks indicates that for the majority of the city the average number of reference repeater - stations and repeater stations does not exceed 5. The average number of - main feeder lines (operating) emerging from one repeater station is equal to three, and only in an emergency, on total failure of all of the �repeaters of the adjacent ref erence repeater station or the electric power supply 34 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4 FOR OL FICIAL 'JSE ONLY Table 2.1 Values of index Namc of. index Minimum Medium Maximum Units of ineasure ~Power of the repeater � - station 5 14.2 35 kilowatt Operating power of the 2.4 4.4 5.2 kilowatt transformer substation Number of transformer sub- 1 3 6 pieces stati^.ns connected to one re~Pater station in - the operating mode _ L2ngth of the main op~rating 1.7 4.4 7.6 km f eeders Length of the main reserve - - 13.0 l:m ~ - f eedei Length of the distributing 1.5 - 6.0 km feeder Number of subscriber trans- 5 - 40 pieces ~ formers per km of line Load of the subscriber 22 f3 97 radio pointsl = transformers � [1Translator's note: the Soviet name for a loudspeaker connected to a _ local wire broadcast network.] network feeding it, the number of simultaneously included main feedei� - lines can reach 6. The cases of a larger number are extremely rare. - In the cities with decentralized WB network and a three-element schematic for constructing its linear part, the required installed power of the reference repeater stations does not exceed 35 kilowatts, and in the minimum, 5 kilowatts, and the most frequentl.y encountered, 15 kilowatts. The reference repeater stations are made up of standard high-frequency repeaters - with an output of 15 and S kilowatts, the commutation and auxiliary - industrial output equipment. In Moscow ancl Leningrad, the reference repeater stations with a power of 60 and 30 kflowatts are widespread. They are equipped with repeater modules with an output capacity of 30 kilowatts of specialized manufacture. In the WB networks, light elements are used i~~ large quantity; a standard subscriber line armature has been built, all of the basic assemblies of the structures have been standardized, the rated voltages in the various elements of the channel have been established. The main distribution feeder lines, the subscriber lines and the household ~ circuits ars constructed on the basis of the specific planning and design. 35 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICTAL USE ONLY For construction there are c]ear technical recommendations. In Table 2.2 - values are presented for the attenuatiuns and the transmission coefficients with respect to the power of sections of the WB channel and with respect to the low frequency channel. Ilowever, Lhe c~ptimril solut tans f~r the single-program Wii networks obtained _ as a result of many years of generalization of experience, do not al~ays coincide with the requirements for the MPB system. Table 2. 2. Attenuation Transfer co- Segment of the channel of the ef.ficient with channel res ect to ower _ Output of the active circuit - input 1.5 decibels 0.9 of the distributing circuit Beginning-end of the distributing line 3 " 0.45 Primary winding of the subscriber 1/8 0.95 transformer output of the sub- scriber network (household network) Beginning-end of the subscriber 1 decibel 0.98 line (household line) of the network (at the end of the line) Total attenuation 4 decibels - Total power transmission coefficient - 0.38 ~ 2.3. Basic Principles with Respect to Creation of the MPB System The necessity for creating the MPB system in the USSR was caused first of all by the multinational structure of the population of the country, the - requirement of providing the WB listeners of the union, autonomous _ republics, autonomous oblasts with full-value natir~nal programs without loss of the union programs. In those parts of the country where broadcasting is in one language, the in troduction of MPB permits noticeable variation. of the transmission considering the interests of the individual population groups. - The creation of the MPB has required the consideration of the state of the technical level of the communication means and a number of social and - economic conditions arising at the beginning of the 1960's. These basic - principles are reduced to the following. A widely developed WB system has come about in the country with a multimillion fleet of simple, cheap single pro- _ gram receivers (by the end of 1962, there were 32 million of them). The - system has recommended itself as sufficiently reliable for information transmission, and it was for ma.ny subscribers the only source of operative information and high-quality broadcasting. At the same time the city _ telephone exchanges at that period were inadequately developed. Under these conditions it would be most correct to solve the problem of MPB in the USSR only by creating it on the basis of the single-program broadcast net- work using a low-frequency channel. ; 36 FOR OFFICIAL USE ONLY ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY The next argument determining the mass nature and popularity of the MPB system :[s ttie~�cost of the subacriber receiver. It must not eignif icantly ~+xr~~~~~i t I~t~ ruN~ ~~f rhe a In~IP-proqram .inudA~~tikar and muwt ~18 16flH thai~ tlie l.lit~ ~�lu~,i~~ r~ullu I?r~~~ei~IcuNt recclvcrr+ tliemd~lve~A. Unl.y unclrr Huch - ccmciltlonH 1H lt poRaible ~o count on tl~e mase production uf tl~e MPB aystem. - According to the economic requirements the MPB system must be introduced with minimum capital expenditures and not cause significant additional operating expenditures. The end of the 1960's is chdracterized by broad application of electrovacuum devices in all the technical means of air and wire broadcasting and the beginning of use of transistors in the individual equipment developments willi I~?w nut~~ul ~~~~w~~r, rt~latively nan-~w hand nf re~rndii~thle fre~uettries :in~l I~iw c~uotl.lly Iii~IE`XE'f~. Use of the single-program broadcast networks as the base for creating the MPB system required mutually matched decision ma.king between the existing low-frequency channel and the auxiliary program channels of minimum possible mutual loss for each of them. The WB networks developed in the cities are different, and the MPB system must be inscribed with minimum devi~ations in these versions of building the networks. Requirements of insuring higher quality indexes than the indexes achieved during radio broadcasting in the long and medium wave bands, guarantees of given auxiliary program signal levels at all of the subscriber WB points for various types of wires (bimetallic and steel), in the presence of cable entries, for the distributing network of different con- figuration (with different number of f eeders, different extent of the distributing feeder lines and different density of the subscriber trans- formers) are imposed on the MPB system. - In addition, it is necessary to insure sufficient mutual, protection between the air broadcast and the WB systems. The introducti~n of the MPB system _ based on the single-program WB network requires the development of the remote control and remote monitoring systems. It is necessary to provide the MPB system with additional high-quality, reliable sources and channels for transmitting the broadcast programs. The discussed basic principles were adopted as the initial prerequisites when creating the Soviet MPB system. When creating the MPB system it is necessary to determine the following: number of transmitted programs, the carrier frequencies, the type of modu- lation, the levels of the high-frequency signals in the WB channel consider- - ing electromagnetic compatibility with the radio broadcast and communications � - systems, the versions of constructing the MPB system for the various ' structural layouts of the WB network; the quality class of the high-frequency channels of the MPB system and standardization of them. ' 37 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY = 2.4. Number of Programs, Carrier Frequenciea and Type of Modulation The indicated characteristics are completely determined by the possibilities of the single-program wire broadcasting system and obtaining the minimum cost of the subscriber receiver. The transmission of the low-frequency signal at high levels over the overhead wire network determines the possible range of frequencies for creating additional channels. This frequency _ range is bounded below by the frequency spectrum of the low-frequency pro- gram with upper normalized frequency with respect to quality class I of - 10 kilohertz, and it is bounded at the top by the beginning of the long- - wave band a frequency of 150 kilohertz. Considering the high signal levels of the low-frequency program and, consequently, the significant levels of the harmonics of the low-frequency signal, it is necessary to " separate the spectra of the high--frequency signals from the low-frequency signals. Theoretically, considering the possible filtration of the harmonics of the low-frequency signal at the output of the low-frequency repeater of channel I, it is possible to use the frequency range beginning with 30 kilohertz. In adopting the frequency range to the beginning of the long-wave band of 10 kilohertz, it is possible to consider that for fre- quency multiplexing of the WB system there is a frequency band of 30-140 ki.lohertz. When transmitting programs with two-band amplitude modulation _ in this frequency band with a reproducible frequency band of ~F=6 kilohertz corresponding to quality class II of All-Union State Standard 11515-65 and with frequency clearance between the channels of 3 kilohertz, the number of possible transmitted programs n determineifrom the condition 140 - 30 = 2A F n-}- 3(n -1), ~ 2,1 ~ is potentially seven. The obtained number of MPB channels is potentially possible on their recep- tion on the superheterodyne type receiver which similar with respect to - cost to the radio broadcast receivers. Actually, the number of possible _ transmitted programs with the WB network decreases significantly in - connection with a reduction in the actually admissible frequency band for the MPB purposes. This reduction on the part of the lower part of the frequency band is caused by the presence of significant additive interference fram the low- frequency channel sufficiently noticea.ble in the frequency band to 100 kilohertz although this interference could be appreciably reduced by installing the corresponding low-frequency filters at the input of the main and distributing feeder lines connected to the low- frequency repeater. - The most significant obstacle to the use of low-frequency part of the free frequency band is significant increase in the multiplicative i?ter- ference from the low-frequency channel increasing with a decrease in the - carrier frequency. The cause of the appearance of this interference is - 38 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY the presence af distributed and concentrated nonlinearities in the WB channel which tlie steel wire and poor contacts have. The solution to ti~e problem of modulation and demodulation with the simplest ~w~~-I~anJ Ampill�uclc ?nodululion preaents known diFficultie:~ with a low rutto of ttie carrier and tlie modulating frequenciee. In addition, a further diff iculty in the use of this part of the frequency band is the more notice- able difference with respect to the conditions of transmitting the upper fB and the lower fH side frequenciQS. The difference increases with an increase in the ratio ~ t~it~ = cto + Fa~c~o = F~. ~ ~ ~ ~ 2 . 2, where Fg is the higher modulating frequency; f0 is the carrier frequency. - With an increase in the carrier frequency the indicated ratio approaches one, which indicates the equal conditions of the transmission of the side frequencies of the AM signal spectrum. It must be noted, for example, that the transmission of the 15 kilohertz modulati.ng frequency band with - the least carrier frequency of 178 kilohertz over a uniform matched telephone pair in the Italian MPB system is simpler than the transmission of the 6 kilohertz modulating frequency band with a carrier frequency of 78 kilo- hertz over a, nonuniform, branched wire broadcast network in the Soviet TPB system, in spite of the closeness of the ratios fg/fH for the given cases. - As is known, increasing the difference in the transmission conditions of the upper and lower side frequencies corresponding to one modulating frequency leads to an increase in the nonlinear distortions of this modulating fre- quency on reception. The limitation of the actual frequency band for the MPB in the upper part - is caused by the greater damping of the WB lines in this frequency band and the nature of the appearance of mutual inferf erence with the radio broadcast long-wave bands. On the whole, the use of the possible frequency band with a frequency of f~X 140 kilohertz and fmin 30 kilohertz for the ratio of f~~/f~iri 4.7 presents significant difficulties from the point of view of insuring the optimal transition conditions for all the MPB programs, As an exa.mple it is necessary to note that the ratio f~ /f~in in the Italian MPB system on transmission of six programs is f~X~f~iri 358/163=2.2; in the Swiss system with this number of programs, with the reproducible frequency band of 10 kilohertz, fmax~fmin 350/165=2.12 respectively, at the same time as in the ~.dopted Soviet TPB system for two programs transmitted on the high-frequency spectrum and the reproducible band of 6 kilohertz, this _ ratio is 126/72=1.75. 39 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY Thus, the presented arguments indicate the necessity for constricting the frequency band for transmission of MPB programs and conversion of it to tl~e upper part (to 120-130 kilohertz. Un ~lie otlier t~and tlie requirements following from the necessity of creating - a simple, inexpensive subscriber receiver lead to somewhat different conclu- sions. The complexity, cost (C) of the receiver are related in a defined way to its input parameters: _ , 17 L' . r es fot rloi - ~ l~ 2.3 ~ \Vorz ~ foi ~ U ( ) oa / (2) - . Key: 1. input; 2. 0 input - where Zinput is the modulus of the input impedance of the receiver; UO in~ is the sensitivity of the receiver; fpl, f02 are the carrier fre- - quencies of two adjacent programs (here f pl ~ Thus, for further investigation of the process of the appearance of multiplicative interference, it is possible to take the following simplified model of the transmission channel (Fig 2.25), in which i~(t) is the low- frequency signal current in the line; ew(t) is the emf of the high-frequency signal source (transmitter), Zg is the wave impedance of the steel line matched at the end. For the circuit it is necessary to determine the voltage uw(t) at its output: um~~ Z~~ ~Q~t)].-~-zs e~~t~~ ~2.10) i.~~ ZA~liQ lt~J . ~ft,, . . - ~ Za ti . Figure 2.25. Equivalent diagram of the steel line for determining the multiplicative interference 72 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 _ FOR OFFICIAL USE ONLY As the initial signals let us zake the voice-frequency, low-frequency - signal: . iQt~=lQcosS~,~t ~ (2.ii> and the amplitude-modulated signal with modulating frequer~cy SZ2: em = E~ tl m cos S2s ~ cos ~a t. ( 2. i2) Considering that ZR is proportional to the length of the line, and Zg is constant, and consi~ering the cases where the lines are sufficiently long and the interference is large and also considering the different nature of the resistances ZRW close to inductive and Zg close to active, it is possible to consider Z~w�ZB and neglect the value of ZB in the denominator (2.10). Using expressions (2.9), (2.10), (2.11) and (2.12), we obtain ~ . � . - u~, = Eo (1 -i- m cos S?~ t~ cos cuo t .Z, - . . . . ..1 ~ : ~ ~ ~ . ~ ' . ~ . ~ ~ � . ~ a bIQ coss Ql ! ' . = E�'Z, ra (1 -I" m cos Sts ~-f- Z bIQ (1 oos 2SZi t~-~- ~ : -I- 2 bmlQ c~os St, t I bmlQ cos(2S?,~-~- . . ~ ' ' . 4 - -I- S?,~ t -F- ~ 1 bml ~ cos (2St1- 52~ f cas.~ t ~ - . . . _ 4 , . . . . . . , . (2.13) , Expression (~.13) is an AM signal, modulated, in addition to the useful frequency 522, by the frequencies connected with the frequency of the low- frequency signal: 2521, 2S21+S22, ( 2S21-SZ2 The obtained AM signal spectrum at the output of the investigated channel is presented in Fig 2.26. The noise/signal ratio at the output of the receiver for interference with a frequency of 2521 ~ � ~ b1Q _ v~s~ = 2 1 ~ ~ (2.i4) - � ~ . . . ~ Ca + Z. b~~ ! 73 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ;~nd fur inter~erence with �requencies of ~ 2S2L+S~2 ~ ~ � - 1 8d~ � . � . . . , : . ' Il/S = 4 . � ~ . . - : (2.15) . ~ . ~ : . ~ . a -E- 2 b!Q - . . : : . . , . , . . . = , ' . ~ : � . _ . , ~ . . ' . . , _ . ~ . ~ ~ _ . . - . . _ . � , . ~ . . . - . � - . ~~~*Q~ ~r p~i ~i~~ ~~~t ~i ' ~'Qt ~+~i ~s~ ~if2Q~ Cv,K1Q~+~~ ~ > ~ /lDaex~c (1) /laoa.~we~~i c~raNQ~ (2~ ' /Icwe,~r~c ~3~ Figure 2.26. Spectrum of the AM signal formed on joint transmission of the AM signal with the carrier frequency wp, the modulating frequency SZ2 and the low-frequency ' signa.l with frequency SZl over steel wires Key: 1. Interference 2. Useful signal 3. Interference For high nonlinearity, when (1/2)bI~�a, the exp~essions (2.14) and (2.15) acquire the following form respectively: ~N/S 1 ~ . ~ (2.16) and ~ ~ - ~M - ' .`~~S = ~ . (2.17) . 2 . Expressions (2.16) and (2.17) must be considered as the maximum worst value of the N/S ratio. In r~ality, for steel wires it is posaible to consider the nonlinearity small, for it in practice does not create nonlinear dis- tortions of the low-frequency signal, that is, it is possible to set a� (1/2)bI~ and the exgressions (2.14), (2.15) assume the form: ~1/S - 2 ~ ; . : (2.18) 74 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY N~S = 4 a ~s . (2.19) Thus, the noise/signal ratio depends on the nonlinearity b/a and sharply (by a quadratic law) on the low-frequency current (interf ering current) of the signal, and it does not depend on the amplitude of the AM carrier signal. The magnitude of the interference with frequency 2521 does not depend on the presence of the useful modulation, the values of the inter- ference with. frequenc~es of ~2StL�S221 are proportional to the depth of the useful modulation. Therefore, for frequencies of 2SZ1 the noisei signal ratio and, consequently, the noticeability increase with a decrease in depth of the useful modulation (Fig 2.27) and in the useful signal interval it will be the worst case, and for frequencies of ~ 2S2L+SZ2I the noise/signal ratio remains unchanged (Fig 2.28); the interference disappears together with the signal in the interval. The pres.ented arguments indicate that the interference with the frequency 2St1, especially in the useful signal interval presents the greatest danger. The investigated noise/signal ratio pertains to all the levels of the useful signal in the dynamic range, - for it permits estimation of the noticeability of the interference for any levels (depth of modulation) of the useful signal. ~ - ~ C ' ~ : 1 7 _ . . . ~ . . . _ . . . � . ~It ~ . � ~ . . . p . 1 01 . , ; . - �1 ~ . _ . . . Figure 2.27. The noise/signal ratio Figure 2.28. The noise/signal rat,io as a function of depth of modulation as a function of depth of modulation m of the useful signal for the m of the useful signal for inter- interference with a frequency ference with the frequency of 2St1 I 2~~~2I . Hereafter the given noise/signal ratio will be called the instantaneous ratio; in contrast to it, the assumed normalized ratio of the interference in the useful signal interval to the rated magnitude of the useful signal _ will be called noxiaalized (N/S)n. 75 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4 FOR OFP`ICIAL USE ONLY The ratio (N/S)n 0 for interference with frequencies of ~ 2St1+St2 but this does not indicate tha actual noticeability of this type ~f inter- ference. . For interference frequencies of 2St1 ~ , ti~i'S)n = 2 Q~~ ~ . (2.20) - Key: 1. max ~ . . ~1~ - Zk,m . _ . ~ t,~#~ . . . - - . . . i . . . I ~ . . . _ . . ; . - ~ . ' . � , . ' . . _ . ~ . . . � - ~ S j T'~,'~i t ' � ~ P' . . ; . ~ . - - M' ~w Figure 2.29. ~ Variation of the Yine resistance with respect to _ high-frequency under the effect of a low-frequency signal current The graphical representation of the origin of the interference with a frequency 2521 is illustrated in Fig ~.29. In one period of variation of the low-frequency s~gnal current the resistance ZQ~(t) varies twice as frequently as a result of symanetry uf the function Z~w (I) Uith respect to ~ the y-coordinate axis. This modulation of the resistance ZQW with double interference frequency also leads to the appearance in the AM signal spectrum of interference with a frequency of 2SZ1. Thus, it is possible to consider the process of the appearance of multiplicative interference in steel wire the result of parametric modulation by variation of the resistance ZQW by the law , . . . ~ ~ Z~ _ - z � . _ a~+ ~'~s ~t~ . The presented process of the appearance of multiplicative interference with a number of simplifications reflects only one energy ~spect. On the whole, , 76 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4 FOR OFFICIAL USE ONLY the multipld.cative int.e,~forence of the steel wire must be defined as the f unc tion N/ S= IQ ~ l~ Fl ~ where k is the length of the line; Fl is the . ~ fo low-frequency si~*nal frequency; f~ is the given carrier frequency. The analytical representation of the dependence of tlie magnitude of the non- linear crosstalk interference on the ratio of the low-frequency and high- ~ frequency signal frequency presents great complexity; it requires determina- tionof the frequency dependence of the ferromagnetic properties of the steel wire and at the present time has not been obtained. The experimental dat~ obtained clearly indicate the dependence of the relative 'level of the crosstalk interf erence (N/S)n on the low-frequency signal current,and the frequency ratio (Fig 2.30) also confirms the quadratic dependence of the crosstalk interference on the low-frequency signal current. The noticeable dependence of the nonlinear crosstalk interference on the length of the line is manifested under the condition ZR~>ZB; therefore, it is possible to consider that for steel liaes ~aith load at the end, the _ magnitude of the crosstalk interference increases proportionally to the lize length (for a length of more than 1 km). For the ma~ority of actual _ distributing fe~der lines with distributed load on the line the crosstalk interference does not increase proportionally to the length, for in each subsequent section the low-frequency signal current decreases ~~d at the sas.e time the increment in the interference with respect to the ui~- branched li~e decreases. _ ~1jG/~ : . , - ~ , 1~p6 . 1 ' ~3~ . . . ~ ~�~r- . 4~~1 ~ fM - y6nl~ (4 ) fQ~7BKtq ~5) / ..4~ j � f ~?OO~q ~6 ) 2) ~ - ~1 oC~' ! . _ ~p ~ ~i a / . ~ - / ~ ~1 i . / ~ i~ ' !7l ~ i ~ .~.~i�~- _ 0 -as ' ~0 I~,A Figure 2.30. Relative level of the crosstalk interference on steel lines for ordinary amplitude modulation ~ (line length 4 km, load at the end, steel wire 4 mm) Key: 1. (N/S) ; 2. 4000 hertz; 3. F1=1000 hertz; 4. f01=46 kilohertz; _ 5. f~2=7~ kilohertz; 6. ~1=200 hertz; 7. I~, amps 77 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY 'I'lic CCUHHCFIIIC interference thnt nrises betwc~en tht~ lilgii-frec~uency 9tgI1A1.A as ~l result of nonlinearity of the wires is negligibly small as a reault - of the small currents of the signals. The line trarisformers in practice do not introduce crosstalk interf erence, which is explained by the weak influence of the ferromagnetic material of these transformers on the transmission coefficient on the carrier frequencies. - Another cause of the appearance of nonlinear crosstalk interf erence in the - lines is the poor contact .at the points of connecting the wires having nonlinear properties. The mechanism of appearance of multiplicative inter- ference in the poor contacts is analegous to the appearance of cross- _ - modulation in the nonlinear elements (tubes, transistors). The devices in which muZtiplicative interference occurs include the trans- mitters and tandem (intermediate) high-frequency signal repeaters. In the transmitters the nonlinear crosstalk interference occurs in the output _ stage, as a rule, between the high-frequency signals by crossmodulation in the nonlinear amplifying elements or f erromagnetic high-frequency trar~sformers. In the tandem repeaters this , ~e of interference occurs in the input and output amplifying stages. How~;*er, the interference level created by these devices is 1ow and can be reduced by increasing the selectivity of the input - ~ and output frequencies separating circuits. _ _ Ti?e additive interference in the WB channel can occur as a result of direct incidence of the outside signals in the low-frequency signa.l spectrum, incidence of the foreign signals in the AM signal spectrum; reception of ~ foreign signals not entering into the spectrum of the useful AM signal, with insuff icient selectivity of the receiver. The additive interference with direct ir..cidence of the outside signals in the spectra of the useful low-frequency signal can appear in the low- frequency program feed channels at the WB statior by line crossovers between adjacent lines. On the receiving side, this type of additive interf erence can appear as a result of the incidence of the low-frequency program signals from the input of the receiver at the input of the low- frequency repeater of this device. Thus, this type of additive interference appears before and af~er the multichannel TPB channel. The second type of ad~?itive interf erence incident in the AM signal spectrum appears in cases where the WB network recei=-es (the antenna effect) signals of other services operating in this frequency spectrum. In addition, this interf erence is also manif ested as a result of the low-frequency signal harmonics incident in the transmitted spectrum of the AM signal. As a rule, this additive interference is unintelligible. The third type of additive inter�erence is manifested only in the channel ~ _ of the receiver and can be expressed in the form of hearing adjacent channels of the TPB system and also the WB stations. 78 ' FOR OFFICIAL USE ONLY - APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY _ 'I'li~~ lnt~~rfcren~~~~ c~l tl?~~ hiickhround un~ no~yi~ lypr oi~ th~~ htglrLrequcncy cl~auiiels is maniLested only in tlie AM signal receprlon nnd tranamiysion devices. In th~ receiver the background and noise appear basically in the low- frequency channel. Considering the quite high signal levels of the TPB system, the noise level can be neglected and the background level con- sidered. - 2.11. Methods of Decreasing the Interference with the High-Freq~sency Channels of the TPB System The procedures for decreasing the int~rferance of the high-frequency channels are determined depending on the nature of the origin of the interf erence and the location of its occurrence. The most important role in the existing TFB system is played by multiplicative interf erence from the low-frequency channel to the high-frAquency channels occurring basically in the li:ne part of the WB channel. .The necessity for decreasing this nonlinear crosstalk interf erence is deter~ir~ed by the fact that its magnitude greatly exceeds the other types of interf erence, and the methods of decreasing it are not simple. The physical process of the origin of this interference was investigated above, and by using some simplifications, the analytical expressions were derived for the noise/signal ratio (N/S). The magnitude of this interference basically determined for ~he steel lines by the low-frequency signal current, the line length, the frequency ratio of the low-frequency signal and the carrier. Consequently, the decrease in nonlinear crosstalk interference from the low-frequency signal can be achieved by decreasing the indicated paramefiers. The simplest and most obvious means of significantly decreasing the nonlinear crosstalk interference would be replacement of the steel aires by bimetallic wires, which would lead to a decrease in attenuation of the high-frequency signals. However, this replacement would require great expenditures of copper and means on rebuilding the WB network. Hereafter it is proposed that the WB networks be converted to cable lines, and the situation with nonlinear crossta.lk interference will improve significantly, but in the first stage of introduction of the TPB system an~i at the present time the steel feder lines are a reality, and this reality will exist for a significant time to come, Therefore, other solu- tions to this problem are needed. _ - The dependence of the crosstalk interference and the attenuation of the high-frequency signals on the line length proposes the problem of reducing~ 79 1 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY - tlie length of the steel lines. Ttiis solution would require rebuilding the TPB network in the direction of increasing the number of such station sites ~s tl~e tranaformer substations with A reduction in the service radius of cacli substation. tt ls natural ttiat tl~le solution too would require lurgc expenditures of ineans and time of its implementation. Thus, the solutions with respect to redesigning the WB network in one form or another, in spite of the radical -improvement of a number of indexes of the TPB system could not be adopted, for ~hey would.require significant - ma~erial means, capital investments, reconstruction operations and time. Therefore, the search for the solution of the given problem will be aimed at electrotechnical measures. - Considering the significant dependence of the given crosstalk interference on the low-frequency signal current, a solution to the problem can be a decrease in this current. This is achieved by using the low-frequency GT repeater for amplifying the low-frequency signal ("active version"), which permit~ a significant increase in the input impedance (to 30 kilohms) of the GT when receiving the low-frequency signal. The effectiveness of applying the "active version" is determined by the volume of its introduction. - In addition to the solution to the problem of reducing the low-frequency - signal current in the overall WB network, the introduction of the "active version" will permit a decrease in this current in the individual sections of the subscriber network, which, in turn, will lead to a reduction in the nonlinear crosstalk interf erence in these sections as a result of poor contacts. The noise/signal ratio for the basic interference with a frequency of 2521 - according to (2.18) will be defined by the expression s/N. _ 1 6 Js ~ ~ 2 am Q~ ~ Consequently, on reducing the low-frequency signal current I~ by n times the N/S ratio decreases by n2 times, and the normalized signa/noise ratio expressed in decibels (S/N)' = S/N + 401g n, (2.21) where S/N is the initial signal/noise ratio, decibels, before decreasing the low-frequency signal current. Thus, if we take S/N=30 decibels, the value measured on the steel lines, as the initial ratio, then assuming potentially n=10, it is possible on steel lines to obtain a value of (S/N)'=70 decibels, which corresponds to . the class II requirements of All-Union State Standard 11515-65 for channels with respect to the signal/noise ratio. 80 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ~ 'Cl~r m~~tlwJ:+ ut cl~.creusing thc cros~tulk luterference Kucli ~A tite upplleatiott of Lrequency modulation and single-band modulation without carrier, increasing the carrier frequency, the introduction of frequency distorti.,:.~ on the transmitting side were investigated and partially tested. The application of frequency modulation required significant expansion of the transmitted frequency band to 60 kilohertz for one channel. A decisive deficiency of the frequency modulation and signal-band modulation without a carrier is complication of the subscriber receiver. Increasing the carrier frequency of the high-frequency signals permits a reduction in the level of the crosstalk interference in connection with an - increase in the service effect for the high-frequency signal current and correspondingly a decrease in the magnetic i~teraction in the stee~. wires _ of the low-frequency and high-frequency signals. However, a significant increase in the carrier frequencies of the high-frequency signals is impossi- ble as a result of an increase in the attenuation and limited na*_ure of the free frequency range before the beginning of the radio broadGast range. Some increase in the signal/noise ratio can be obtained by a~a increase in depth of modulation according to the expression (2.18) on frequencies in sound range having reduced level, that is, by introducing distortions in the form of a rise in the level of the upper modulation frequencies in the transmitter with the corresponding reduction of it in the receiver. The effectiveness of this method is highly limited with respect to magnitude, on the order of several decibels, and with respect to frequency spectrum above 2-3 kilohertz modulating frequencies. Under these conditions the most acceptable turns out to be the method of decreasing the cross talk interference by using amplitude modulation with an adjustable carrier frequency amplitude proposed by L. Ya. Kantor when developing Soviet TPB system [1]. Decrease in the Nonlinear Crosstalk Interference by the Application of an AM Signal with Adjustable Carrier Level The basis for this method is the proportional dependence of the crosstalk _ interference at the output of the receiver as a function of the carrier _ frequency level. Beginning with expression (2.13), the amplitude of the interf erence _ , envelope with a frequency of 2521 1 z . U~a = 2 bIQ~Z.Eo. ~z.z2~ Consequently, decreasing the amplitude of the carrier frequency E~, it is ~ possible to obtain the corresponding decrease in the crosstalk interference at the aitput of the receiver. 81 FOR OFFICIAL USE ONLY i APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY However, this should not be understood as a decrease in the initial rated voltage with constant carrier frequency voltage, for in this case, according to expression (2.18) no gain takes place with respect to the nai4e/signal ratio. A decrease in the noise/signal ratio with ad~ustable carrier frequency voltage can be achieved with respect to the constant voltage of the carrier under the condition that all the levels of the useful broadcast signal at the output of the receiver remain the same as for constant carrier voltage. Inasmuch as the signal at the output of the receiver is determined for linear detection by the magnitude of the AM signal envelope Uenv, in order to reduce the constancy of this value it is necessary that the following condition be satisifed for any signal level: Uor ~~IltpUp = 1rizUpx, ~2. 23) Key : 1. env where mp is the depth of modulation corresponding to some level of the broadcast signal, with constant voltage of the carrier frequency Up; mX is the depth of modulation corresponding to the same broadcast signal level with unchanged carrier frequency voltage UOx� From expression (2.23) we have the basic condition of proper voltage regulation of the carrier freque:~cy: Uo m~ . U~~ - ~ (2. 24) The noise/signal ratios for some level of broadcast signal with constant carrier voltage (N/S)p and variable carrier vol'tage (N/S) X can be represented in the form: . � (N/S) = 1' b J2' Vo - ~ 2 a maUo . (2.25) ~y~a = 1 6 ~ U�r X 2 a~' mxUox ~ ~ 2. 26) ~ Consequently, a decrease in the noise/signal ratio with adjustable voltage of the carrier UpX with respect to the constant voltage level ' ~~/S)X/ ~N/S~~ _ Uox ~ ~Uo (2.27) 82 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY The signal/noise ratio expressed in decibels for any voltage of the carrier frequency UOx _ ~s ~ `~5~-~ ~o~ - yl + g ~ . c2.28> : o uc Inasmuch as the initial voltage of the carrier frequency with maximum broadcast ;signal remains uncl:anged and is maximal, the degree of increase in the ratio (S/N)X is determin~3 by the decrease in voltage for the reduced le~vels of the broadcast signal. Graphically the function (S/N)X= `~~UO max~UOx~ is presented in Fig 2.31; the crosshatched region corresponds to the additional gain with respect to the signal/noise ratio. _ (~)X a6 . . _ . . . cl~ ~ ~~)o ! . . ~2~ , . . . . _ . . . . . 1~.:. 6 ~ . . . 10 ~ - � _ � - . ox Figure 2.31. Signal/noise ratio with relative reduction in carrier voltage Key: 1. (S/N)~, decibels 2. ~S/N)0 3. Up max~UOx It is necessary, however, to note that the adjustment of the carrier frequency voltage does not permit a decrease in the second type of interference with the combination frequencies ~2S21�SZ2~. This form of interference is propor- _ tional witil respect to its magnitude to the amplitude of the envelope AM of the signal mXU~X which remains invariant with respect to the condition (2.23) for any level of broadcast transmission on variation of the carrier voltage. Cansequently, the noise/signal ratio for this interference remains unchanged when regulating the carrier frequency voltage. The regulation of the AM carrier signal voltage beginning with what has been stated cannot be accomplished other than as a function of the level of useful modulating signal U~. In general form the law of this regulation " UO - ~ ~UQ~ (2.29) can take any form when observing the condition (2.23) and the condition - 83 " FOR OFFICIAL USE ONLY - ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ~;~X. The gain with respect to the transition interference for any level of broadcast signal would be determined by the form of the regulating function (2.29); therefore, it is important to discover the limiti.ng form of this function given the greatest gain with respect to the crosstalk inter- ference. According to (2.28), the gain with respect to the interference is proportional to a reduction in the carrier voltage; consequently, it is necessary to determine the maximum possible voltage of the carrier frequency for any value of U~. On making the transition from the constant carrier to variable, the voltage of the variable carrier ~for any level of the broadcast signal ' Uos - m jJo, (2 . 30) - Considering that with the DC carrier m~=nU~, where n is a proportionality coefficient and that for the greatest decre~:~e in voltage UpX it is ~ necessary to observe the condition mx=mmaX const and also considering the initial unregulated voltage UO=U~ ~X, we obtain ~ ~o t~exc U jf~ = s, ~2.31> Key : 1. max , - that is, ~ U~ = kUQ~ (2. 32~ where k = ~0 ~~'x~ � ~.+rucc (1) . Key: l. max Thus, the most advantageous witti respect to interference is the rectilinear function U~X(U~) known as amplitude modulation with constant modulation coefficient (C:~IC). In Fig 2.23 and 2.33 graphs are presented for the functions Up=~(U~) and m=~,(U ) for the AM signal with constant carrier and CMC, where UO rated~ mrated~~S2 rated are the rated (maximu~ values of i:he carrier frequency voltage, the d~pth of modulation and the low-frequency ~ signal voltage at the input of the receiver respectively. After obtaining _ the optimal relation for the carrier voltage as a function of the modulating _ signal voltage, it is possible to compare the function (N/S)X f(U~) for the AM signal with DC carrier and CMC for interference with the frequency of 2521. For constant carrier . ~ r1 _ 1 blQt_ l~b~`~ ~ _ ( S ` Z ant 2 a . ' ( 2 . 33 ) ~ 84 ~ FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 _ FOR OFFICIAL USE ONLY thal iy . � � . N ~ ~ (~}o =,U~ � (2.34) . where N=(1/2)(b/an)I2S21 is the generalized proportionality coefficient. ~ . . ~ . ~ ~ ~ _ . U i � u,~ - . , ~ ~l m ~ ~ - - . ~ ~ : . . , ~ .o - . ~ ~ ~ : ~ ~ ~.1) Figure 2.32. Depth of modulation as a function of the magnitude of the modulating signal with constant carrier Key: 1. rated � - - . ~ � . ~ , ~ . ~ � . ~ : . - � U~ . . (1) m ~ . m,r,~, _ (1) , $ ~ ~ : I . ~ _ . . ~ . . . . . : ~i~. Figure 2.33. Carrier voltage as a function of the magnitude of the modu3.ating signal with a constant modulation coef f icient Key: ~ 1. rated ~ For a:variable~carrier - t b U~ ~ 1 b ~Q r~ 1 � CL.35~ ~1s a.~' ~z~1os 2 a f~j knetu ~ . . . - 85 FOR OFFICIAL USE ONLY ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OF~ICIAL USE ONLY Consequently � ~ s t((JQ~~ a COI1St. (2.36) cs . ~ - Thus, whereas with a constant carrier the N/S ratio and the noticeability of the interference increas~s with a decrease in the broadcast signal level and reach a maximum in its interval, with CMC the noise/si~naZ ratio re- ' mainds unchanged. In Fig 2.34 the functions N/S=f(U~) are presented for constant carrier and CMC. ~ : . . . ~ _ . . . ' � m~~'On~st - ~ ' ~ � � - , - ~ � . ~ Figure 2.34. Graphs of the noise/signal ratio as ~~unction of _ the magnitude of the modulating sigaial with constant carrier (U~=const) an3 CMC (m=const) Key: 1. U~, kilohms - The total magnitude of the noise/signal ratio for all interference with _ frequencies 2521~ 2S21+S~2~ ~2St1-SZ2~ With CMC do~s not depend on U~, and it is determined by the following: . ~ (i) ~ (1) - _ - _ (t7 ~ - . ~~,�+C ~ s + .C ~_Q a. . . . ~ , \ II~ , ,I . . . ~ z~ c~~ ~2~ ~ a r2~ JQl I b~i 1 b~' ~ ~ . , : ` ~ ~4 a , . C4 a ~ . ~ ~ b ~ . 1 ~ . ~ . 1 ~ a j~! ~ m ~ � . . (2.37) Key: 1. N; 2. S The total value of (2.37) exceeds the noise/si nal ratio for the basic ~T interference with a frequency of 25~1 by oniy 3/2-1.22 times (1.85 decibels) for a value of m=1. 86 ~ _ FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY The normalized ratio of the rated signal to the interference in the broad- cast transmission interval r-s- ~ 2~:Cr.uc Ue Nnclo (2. 38) bJQ U~ m ~2) . Key : 1. max ; 2. min where U~ ~n is the carrier voltage in the broadcast signal interval. In the existing TPB system the ratio U~ ~/U~ m~=10, which permits an increase in the (S/N) ratio by 20 decibels and bringing it approximately from 30 to 50 decibels for steel lines up to 6 1~ long. In spite of the fact that the indicated method of decreasing the nonlinear crosstalk interference was obtained on the basis of investigating the interference in steel wires, it is also applicable to any type of nonlinear interference occurring in the TPB system whether from the low-frequenny signal to the high-frequency signal or between high-frequency signals, at poor contacts, at the output of the transmitters, and so on. This is explained by the fact that in the majority of cases the spurious modulation takes place with constan*_ modulation coefficient which does not depend on . the amplitude of the carrier frequency. With a decrease in amplitude of the carrier, the amplitude of the noise envelope decreases proportionally. In the worst case of noticeability of the interference in the broadcast transmission interval the suppression of the carrier and, consequently, suppression of any nonlinear interference reaches the highest value. This ~ conclusion is also applicable to modulation of the carrier by the background in the transmitters and repeaters, which simplifies the structural solutions of these devices. In addition, the introduction of the adjustable carrier increases the efficiency of the powerful repeaters and facilitates the thermal conditions of their operation, which is especially noticeable for transistorized systems. ' Methods of Decreasing the Additive Interference The types of additi.ve interference and the causes of their appearance were investigated above. The methods of decreasing this interference are determined by the nature and location of its appearance. The interference which falls directly in the spectrum of the low-frequency signal in the connecting feed lines of the programs can be decreased by insuring sufftciently high crosstalk attenuation between the connecting lines of all the p rograms. A decrease in the same type of interf erence in _ the receivers is a~hieved by small coupling between the input of the receiver and the input of the lo~-frequency repeater of the receiver. The interference incident in the spectrum of the AM signal in the multi- ~ channel transmission channel can be decreased by reducing the level of , the harmonics of the powerful station low-frequency amplifiers in the 87 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY frequency band of 70-130 kilohertz and also improving the syQUnetry of the TPB lines under the effect of wireless interference. Some symmetrizing of the subscriber transformers is achieved by applying the device in (2.35), the series LC circuits of which are tuned to the external interference frequency. In order to exclude the transmission of the interference to the subscriber network over the "two-wire-ground" system, the subscriber transformer can be used with electrostating shielding between its I and II windings. These methods permit a reduction in the level of wireless inter- ference by 10 to 12 decibels. The use of carrier regulation with suppression of the carrier in practice to zero permits us to obtain suppression of this - interference in the receiver detector by 15-20 decibels in the useful signal interval. Obtaining the given ir.terference level between the adjacent high-frequency channels is possible by using the corresponding selectors in the receiv~rs. ~ (1) P~Au~wr _ c C _ L _ qT ~2~ ~ Figure 2.35. Circuit diagram for suppression of interference _ from a radio station ~ - Key: 1. distributing feeder line 2, subscriber transformer 2.12. AM Signal with Regulatable Carrier and Its Application The application of the AM signal with regulatable carrier permits us to reduce the crosstalk interference for all levels of the broadcast signal ; less than rated and especially significant in the most critical case, in - the broadcast transmission interval. Let us now consider the AM signal - with regulatable carrier, its characteristics, the relation of these - characteristics to the quality indexes of the high-frequency channel and _ the operating peculiarities of some of the devices for the given AM signal. The usual AM signal can be represented by the expression ~ ~L a Up ~ 1-{- U~ CC5 ~ t~ C~3 (~,~p ( 2. 39 ) where Up is the carrier amplitude; c is the proportionality factor betw2en the amplitiide of the modulating voltage U~ and amplitude of the envelope. 88 FOR OFFICIAL USE ONLY - ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPR~VED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY Correspondingly, the AM signal with slowly varying carrier amplitudes Up(t) and modulat~ng signal U~(t) can be expressed as (1 UO (l) 1-{- (t~ COS Sa t COS t. ( 2. 40) L Vo J For simplification let us assume that the amplitude of the modulating signal varies according to a harmonic law with angular frequency S~A from US2 min tO U~ (Fig 2.36). Then the variable amplitude Ua = UQ uQ~~ ~ v~ ~~1-~- cos S~A t~. (2 . 4~.) . � Key: 1. max; 2. min ~ ~ ` . . ~2~ ` ~ � ~ . ~ ~ , ~ - . ~irnN ~ ~ + ,,~Si� . f ~ t . ~3~ . - . ~ . , , . ~ . ~1) . ~ T Z~ ~r~ ~nuQ ~ ~~r ' As ~ C![E~Q/!a~ ~ Figure 2.36. Variation of the amplitude of the modulating signal with respect to harmonic law Key: 1. Envelope of the modulating signal 2. USZ max 3. U~ min ~ For U~ miri 0 expression (2.41) is simplified: U ~l~ ~Q = Q~ se r 1-}- COS SZ~ t~. ( 2. 42 ) l Key: 1, max The given expression is the envelope of the modulating signal. 89 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4 FOR OFFICIAL USE ONLY For the AM signal with CMC the amplitude o� the carrier must vary also bj? law (2.42), and the expression (2.40) acquires the following form: - - u (1) ? . _ , c a= k= ~1 -f-.c~s~A t~ ~lj-f-'~-k cos 52t~~~at,- (2.43) Key: 1. max where k is the proportionality factor between Up and U~. ~ Comparing expression (2.43) with the expression for the ordinary AM signal (2.39), it is easy to see that the signal obtair.ed is an AM signal with variable carrier amplitude (kU~ ~X/2)(1+cosStAt) and constant modulation coefficient m=c/k. The product (kU~ ~x/2)(1+cosS~At)coswpt of the expression (2.43) gives two components on conversion of the term (kU~ ~X/2)cosSZAtcoswpt; U ~1,~ u ~1~ k s 4 c~~~o +~A) t: k Q,~~ cos (~o - S~~) t~ Key: 1, max analogous to the side frequencies of thc~ ordinary AM signal. Inasmuch as in the ordinary broadcast signal the frequency S2A G ~ ~ ~n a,~ v,~ o w oo cv ~ i~+ a~ oo ~ , ~i?�~v~iafl// ' ~ . ~ . . N t~ 3 s~ o ~ ~ ~ i b ~ ~ u~i ~ ~ ~ ~ a ~ ^ _ ' a~ t i cu a~ ~ a~ a? o~+ v~ ~ u~ , ~ _ . , . ' . a~ i i i s~ o ~ ~ i s~ w o v . � - R! � , , _ ~ ~ 3 U ' U ~ ~rl N ~ I I f: ~rl ~ ~ j . . . . oo ~ a~ ~ aG i i cv a ~a a � � o a~ ~ ~ ~G .n o r.. ~ ~ a~ o a~ ~ ~ F:+ 4~ C+' P0 G~~ �r~ U'r~i .t I~ i.~ q 4a N 106 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 i FOR OFFfCIAL USE ONLY , o e~)1 I~ i I~ . - ~ r i ~ v ~v ~ ~ ~ ~ I ~ b ~ . Gl O;�~tI ~ Q~b ' �G I~ I~ ~ ~ II ~ . ~ ~w I ~ ~ ~ ~~t o ~ ~ - - - 3 1 A ~ ~ ~ ~ ~ v ~ ~ ~ trf I 0 . 6 ~ ~ ~ ~ `I ifl 4-1 ~ ~ t ~ , a ~ ~ � ~ _ ~ ~ ( a ~ U ~ . ~ ~ E' I . a ~ ~ ( i~ a 0 ~ ~ ~ ~ a~i ~ I ~ ~ y ~ 1~ ~ H � ~ ~ I I ~ , c~ ~ e ' ~ ~ " I w a~+ ld .a a' o a ' ~ \ I ~ ~ ~ v~i ~ ( ' I - & ~ I . L__~o~ J ~~o~ � 1 . ~ ~ ~ ~ aaa3�~ ~ ' ~ ~ ~I~ ~ ~ d o~ ~ ~ ~ 11 ~ , ~ I ~ ~ ~ t ~ ~ ~ ~ ~ i ~7 ~ . ~l I~~ , ~ o ~ ~ ' ` o~ oao ~ 4-t i~ N U . ' r~s '~+f a ~O a o [a-~ ch v _ ~ N ~I - ' p ~~.+OH - ~ ` . v ~ d.C v~l ~ i ~ ~ . ~I N ~ ~ ~ ~ ~ ' ~ C b ~ ~g W 'Ud 0~l ~ ~ ' Q � tC 'd O ~ V ~ . ~I O~ N f~+ G~l ~.3i ~ a ~ ~ , ~ ~ ~ �n w ~ . ~ I ~ ~ ~ ~M I 00 ~r ~ C~1 ~ - r~l r~l 3 ~ ~~-1 ~ Q v~ A~ t~1 c0 ~ U ~ ~ C ~ d I N u1 ~ CV c~ V N J.~ 1.? .p _ v ~ ~I ~ ~ tA ~ ~ ~ ,`.~~J~ ~ � , ' ~1 O GJ rl U7 ~ u ub 4' ~e a ' a~ ~ i i~ ~ . ---~,vnWtr~n1L , . ' . ~ ~ ~ �o � ~ , ~ ~ . : - \ ; : , , : . . , ~ N x 107 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY The UUP-2 complex makes it possible to control twu re�erence repeater = - stations or UP, BP in the preyenceli�ier andetransmitters)ntrol objects in each of them (low-frequenc amp , The UUP-1 set also controls two rereater stations in the presence of each of them af no more than three control objects. The WP-1 and UUP-2 complexes are designed for operation over the connect~zg lines the telephone pairs. When using the WP-1 the central wire broad- cast station must be connected to each reference repeater station by tlines. - connecting lines, and when using the WP-2 equipment, four cor_necting In order to transmit the control commands, individual strands of the connect- ing l~nes are used. The programs are set by simultaneous feed to the 80 volt DC pulse (defined polarity) and alternating current line. Noise- proofness of the system is achieved in this way. The com~nand DC mess~ounds - fed over the "conductor-ground" network, and AC, over the "two-wire-g network. The command message is the switch; on return of the switches to the initial ~ position the voltage of the command message is picked up from the line. The command output is accompanied by obtaining a verification of execution. 511 connecting line is used only to sheathe the low-frequency programs; S12 is a reserve line. Over the "strand-ground" S13 line a control command is transmitted for one low-frequency module; over the circuit made. up of the other strand to ground", the control circuit for module II is low frequency. A command is transmitted over the S13 line for modules III and IV or for control of the transmitters of programs II and III. The return sound monitoring with respect at the reference repeater station, of the low frequency repeaters installed the PP, UP and the telephone service co~nunications are realized over the S13 and S14 telephone pairs. With respect to individual circuits (f ifth and sixth) from the APU-3 No 2 and APU-3 No 3(Fi~ 2.50) the transmission ~ of the signals of two additional programs to the transmitters of several reference repeater stations. 3, The equipment of the UKTP type [transformer substation connection circuit] for remote monitoring and control of the sound transformer substations and monitoring of the distributing feeder lines. The equipment is designed for the control of 6 and 12 transformer substations equipped with SGR and SGP bays. For this purpose the central wire braadcast station is connected to each ~rinS~h~eresenceaof~feederWlinesrforfoutdoortsoundephone exchange li~es, and P systems (FUZ), three pdirs. 108 ' FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 - FOR OFFICIAL USE ONLY 4. The reserve pragram sources are special r~ceivers for re~eiving AM and ultrashort wave broadcast stations, a tape recordar, sound pickup and microphone. :he following types of equipment are instal:led at the reference repeater - stations: 1. Low-frequency amplifier with output power of 5 kilowatts, type TU-5-3, TU-5-4, UPV-5 or 15 kilowatt type UPV-15. In Moscow and Leningrade more powerful 3mplifiers are used (by 30 and 60 kilowatts). At the newly designed reference repeater stations up to four repeate~s of the TU-5 (OUS1) type are installed; at the ind?vidual existing reference - repeater stations up to six TU-5 repeaters or two UPV-15 repeaters [OUS4 (Fig 2.50)] are installed. The quality indexes of the repeaters correspond to the requirements imposed on the first quality class (All-Union State _ Standard 11515-65): rigid output vo?_tage 240 vc~lts; total power intake - by the repeater from the feed network in the rated output power mode, UPV-15, 33 kilowatts; UPV-5, 13 kilowatts. In the UPV-15 repeater the tubes have forced cooling by an exhaust fan. _ 2. The servo semimodule is a bay of the :JPI-�2 or UPI-1 type from the set of remote monitoring`and control equipment of the WP-2 or WP-1 type - (previously produced by industry) for reception and execution of control and sending return verf iciations and also for preamplif ication of the pro- grams :.oming from the ceutral wire broadcast station to the reference repeater station or the servo semimodule of the TU-TK-TS equipment developed for the TPB networks. In the UPI there is a device for automatic mutual redundancy of the TU-5 repeaters. The input level of preamplification of the UPI is zero (0.775 volts): The UPI-2 bay is designed to control four controllable ob3ects, azd the UPI-1 bay, three. 3. The SVK-2 type output commutation bays are equipped with voltage step-up transformers on sonic frequency coming from the output of the low- frequency amplifier, from 240 ta 480/960 volts and transmission of it to _ the main feeder. In one SVK bay there sre two independent cells, each of which is designed to connect one main feeder. Each SVK cell contains a 5 kilowatt feeder transformer; the switching ele- ment; protection and signalling. _ 4. The set of UPV-200 transmitters made up of two program II and III transmitters. - For TPB, a device is installed in each SVK cell for connecting the trans- ' mitters of programs II and III (UPP) to the main feeder line. The _ 109 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR QFFICIAL USE ONL`1 reference repeater station for insuring unint~rrupted operation requires special ventilation units and electrical equi~~ment and the laying of power cablea. Other types of station sikes are encountered in the cities where the repeating equipment is installed. These include the sut~station block Bp and the L'SPV repeater stati~ns. The substation block is a transformer - substation connected by the main feeder to one reference repeater station - and equipped with a reserve repeater (instead of a second main feeder). - A simplified device is required for monitoring and control for it. In the BP [substation block], as a rule, the TP-STR and STP equi:pment is installed, and for the TPB, the UPTV-200 transmitter. The wire broadcast repeater station is designed to feed a two-~:lement or mixed city network or remote region (Fig 2.52). The USPV is set un by analogy with the reference repeater station. As the output switching equipment, the STR bay is installed from the transformer subst~tion complex with two-element network or the.AVK type bay designed for con~:er.ting 10 distributing feeders and two main feeders. The transformer substation is � designed to st.ep down the audio frequency voltage and distribute the low- frequency and high-frequency power of the distributing feeders. Two bays are installed at each transformer substation: STP-1, STR-3 or STP-2, STR-4. In the STP-1 bay there are cells for connecting two main feeders: operating and reserve. In each cell the 5 kilowatt feeder transformer is instal;led - which steps down the audio frequency voltage from 480/960 to 120/240 volts. Each transformer substation can feed up to 12500 subscriber units. Over the ma.in feeder lines connecting the SVR and the STP equipment, an audio frequency is transmitted from the reference repea.ter station to the trans- former substation. The control commands for the system for starting the _ given main feeder line are transmitted over the artif icial circuit of the "feeder line wire to ground." The STR-3 or STR-4 bay is designed to connect 10 distributing feeder lines and two feeder lines for the outdoor sound system. The automation elements for remote control transformer substation are located in the bay. The transmission of the signals of the high-frequency channels to the distributing network takes place through the bypass of the step-down transformer, for which a transformer substation connection circuit (UPTP) is installed at the transformer substation, including the following: _ a) ZFM and ZFR blocking circuits (for the main feeder and distributing - network respectively) for the high-frequency currents. The coils of the filters air executed from quite thick wire to insure minimum attenuation ~ of the low-frequency cu~rents going through the coils; - 110 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY b) The by,ass for the OUTP to create a bypass of the high-fraquency _ transformer f~r the high-frequency cu*rents and matching of the load of the main feeder (the distributing network) with the wave impedances of the main feeder. The transformat~on coefficient of th~ standard OUTP is 3.15; it ia assumed here that on~ tnain feeder line feeds 10 distributing ~ f eeder lines. The high-frequency voltage st the input of the nistributing network (on the _ - STR bay) must be within the limits of 20 to 30 volts. - As was stated above, the remote monitoring and control of the operation of the transfor`mer substation, the diatributi-ig feeder and the FUZ are realized on the UKTP bay of the central wire broadcast station using two - or three connecting lines. A structural diagram of the connection of the UKTP-1 bay to three trans- former substations is gi�~en in Fig 2.53. The Sli connecting line is used for resnote monitoring and control of the main f eeder. The control, monitor- ing and signalling of the main fe~der are realized over two artificial sll channels formed by each wire of this line and the ground. The wires of this line are used for return sound monitoring from the buses of the transformer substation and telephone communications TsSPV [central wire broadcast stationJ with the transformer substation. _ S12 is used for monitoring and control of the feeders of the outdoor sound system over the same artificial circuits as in the sll connecting line. The pair of s12 wires are used for return sound monitoring of the FUZ. The S13 connecting line is provided for emergency signals (that the fuse~ are burned out at the entrance of each distributing feeder of the STR) and remote monitoring of the voltage from the ends of each distributing feeder line. In the mixed network for areas with small load (2500 to 5000 radio points), a simplified type transformer substation (UTP) is installed with one-way feed without remote control and monitoring (see Fig 2.52). The repeater stations and substations OUS, UP, BP and TP,as a rule, are " placed in the facilities allocated by the local admissible organizations - in the residential and public buildings. In a number of cities, especially newly built ones, the plans call for the - location of a central wire broadcast station ~ointly with the reference repeater station [OUS] in the same building with the ATS, MTS. In the majority of cities the central wire broadcast station is pla~ed in the same facility with one of the OUS [reference repeater stations]. ~ _ 111 - - FOR OFFICIAL USE 013LY - APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY . . . . rn~ (4) oyc, s~ - ~ ~ . ~ crn M~, . ~ l f ES 9) ' ~ crP ~ ~ . , . ' j f ~P~ ~ . ' . , . . . ~ . . � t~ . 1 ~ � : . . - (1) ~ 1 - ~ - ~ ~cn~ ~ ~ , ~ . . ~ T~s - i ; O~IC= . . c~,.(3) crn _ ~~x1'11~ c.~t ~ M~~ 1 r CB~f ~ ~ ( 2 ~ ~ CTP i j _ : ~ , A/4~ ~ . . . ~ ' . . w . � . ' ' . 4~~ ' . . ~ - � r,~ . " . � _ / . ' ' 1 1 ~~9Ca . . � ~l1 s T,7a ! 1 ~ . ~ I 1 ' - . . � . . . ' . � L7i7 ~ ' CB : . � . , . . : Ill~Aj . . ~ : GTP . Figure 2,53. Structural diagram of the connection of the ~ UKTP to the transformer substation Key: _ 1. Central wire broadcast statian 7. Ma.in feeder line 2, UKTpl 8. Reference repeater station 3. S1 1 connecting line 9. SVK - 4. TP1 [transformer substationJ ' 5. STP 6. STR For powerful OUS 30, 60 kilowatts special work areas are built, in which there is a whole set of stations including power equipment and ventilation. Line Structures The line structures are a responsible part of the WB network. The introduc- - tion of the TPB system on the existing WB networks imposes additional ' requirements on the lines considering the application of the high-frequency channels. ~ ~ In large cities the main feeder line is a post and more rarely, pole line. ~ The wires, as a rule, are bimetal, 3, 4 mm in diameter or steel, 4 mm in 112 ~ FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ~ diameter. The line length is from hundre~s of ineters to 10 kilometers. The ~�rerage length is 4 km. The inputs to the amplifying and transformer substations are cable. Along the path of the line, cable inserts are used which are made up of the MRM type cable and large capacity power cable. - Tt~e rated low-frequency voltages are 480, 680, 720, or 960 volts; the transmitted power is up to 5 kilowatts. The high-frequency voltage is to 120 volts, the transmitted power 25-30 watts. The voltage attenuation along the low-frequency channel (at a frequency of - 1000 hertz) is 1-2 decibels. The attenuatio~n of the high-frequency channel is de}ermined by the expression a~in feeder-aR, and with a matched reg~me for tne lines without cable inserts it is within the limits of 1 to 10 deci- bels. In the presence of several cable inserts, depending on the type of cable used and the accuracy of matching the input impedances, the attenuation of the section can reach 15 decibels. The input impedance of the main feeder can diff er from wave (as a result of impossibility of insuring exact matching) by ~-20%. The dist.ributing feeder lines can be post, pole and cable. The wire material is bimetal an~ steel, 3 and 4 mm in diameter and copper, 1.2 mm in diameter. The attenuation on low-frequency (at a frequency of 1000 hertz) must not exceed 3 decibels; on high frequency it reaches 10 to 12 decibels. The distributing f eeders in the cities, as a rule, are lines with uniformly distributed load. The role of the latter is played by the subscriber transformer, the input impedance of which on high frequency is from 5 to 20 kilohms, and ~.he transmission coefficient is 0.01 to 0.1 depending on the = power of the subscrib er transformer .and its load. The subscriber lines post or pole are made, as a rule, from steel wires. Their extent is from 100 to 200 to 700-800 meters and more rarely 1 km. The load of the subscriber line is the subscriber inputs ending in a subscriber 'set. The attenuation of the high frequency voltage of the long subscriber lines can reach 10 decibels. The layout of a subscriber line with single program loudspeakers (OI') and three program loudspeakers i_s presented in Fig 2.22. The last section of the city WB network, as a rule, is the building networks. By the building network we mean the network fed from one subscriber trans- former. The most typical subscriber networl~ for the cities are the intra- building networks of large apartment builaings. The building network is - made up of attic and staircase wiring lai3 in the vertical shaft of the building (sometimes called a"riser") and made as a~�ule of PVZh type wire with a strand diameter of 1.8-2.5 a.n~ intraapartment wirinb made of the PTPZh and PTVZh type cables. The Input im~ec?ance of the building net- work on the low-frequency channel is determined by the number of speakers connected to the network, and on the high-frequency channels, in addition, by the parameters (primarily, the capacitance) of the wiring. _ ~ 113 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 ' FOR OFFICIAL USE ONLY On the carrisr frequencies of the TPB system the building networks acquire new electrical properties they become electrically long lines, and ir~ a number of cases require matching to avoid th~ wave processes. The magnitude of the input impedance of the building network on the multiplexing frequencies fluctuates within the limits of 20-100 ohms (for 5 to I6 story buildings) and attensation to 6 decibels. As an example, in Fig 2.54 a circuit diagram is drawn for the length of the building network of a 16-story building. ~e m ~ ~c ~n ~a r~ ro ~p 3S J1 ' dt �~3 J9 30 30 3~ , ~ y~~,,. ~Lh ~ e,~ '.~c (2) . rrs~dmc (3) .1 ~ - 1 i � 0' s Np ~a ~ 5~ Figure 2.54. Schematic of the staircase wiring of a 16-story residential building Key: - l. attic 2. 16th floor _ 3. 2d to 15th f loor 4. lst floor 5. NN sections In the WB networks, single-program speakers of third or second quality class are used as the subscriber sets. They have input impedance~in the frequency range from 50 kilohertz to 10 kilohertz correspondingly of 3-12 kilohms and a phase angle of 30 to 25�. In the high-frequency band these speakers have an input impedance with respect to modules on the order of 5 to 7 kilohms and a phase angle of 60 to 70�. The Avrora and Mayak type three-program speakers that are manufactured have an input impedance within the range of 2.5 kilohms, and on the high- - frequency channel the modulus of the input impedance to 4.5 kilohms and a phase angle of about 40�. Additional specialized high-frequency devices are used on the TPB networks to correct the WB lines, a description of which is discussed in detail in - the following sections. 114 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY Program Sources, Connecting Lines ~or Feeding the Programs, Remote Monitor- ing and Cont7ol The basic program source is the radio broadcast equipment(RVA) and in - individual citief;, the interurban broadcast channels or the eegregated recciving sl-ations (VPP). The union central broadcasting progrms obtained over the interurban cable lines reach the central wire broadcast station most frequently via the RW, but in individual small cit{es they go directly to the central wire broadcast station. The local program sources are professional specialized AM and ultrashort wave FM receivers of the radio broadcast stations or tape recorder and sound pickups of the local broadcasts studios. At all of the ref erence repeater stations, UP receiving programs from the central wire broadcast station, professional receivers and tape recorders are installed as the reserve sources. In ~rany cities the central and oblast broadcast programs of the wire broadcast station a~e received by the professional receivers. The programs are fed from the RVA to the central wire bro~dcast station in tandem over special cables with shielded strands or with a connection to the automatic telephone office distributing frame in a common cable in the central wire broadcast station to automatic telephone off ice section. The length of the cable lines in this section is from 0.1 to 3 lan. A multipair telephone cable, most frequently type T with strands 0.5 mm in diameter, a capacity of 150, 100, 80, 50 and 30 pairs, tne most different length from hundreds of ineters to 2 1~, is laid between the central wire broadcast station and the closest automatic telephone off ice. Between the automatic telephone office and each object of distribution of the reference repeater station, BP, UP and TP telephone pairs are used in the cable lines of the city telephone exchange. In these sections are used with strands 0.5, 0.6, 0.7 and 1.2 mm in diameter. The skeletal diagram of the connect- ing lines for the decentralized networks in the cities is presented in Fig 2.55. For the existing TPB system and standard remote control and m~nitoring equip- ment, the following number of telephone pairs of the city telephone exchange are required: 1. Between the central wire broadcast station and the reference repeater station at 2~ kilowatts, 8 pa~rs, including considering the reserve, 4 pairs for feeding the programs and 3 tor remote monitoring and control of the low-frequency amplifiers and the UPTV-200. ~ 2. Between the central wire broadcast station and the reference repeater station at 15 and 30 kilowatts (with two UPV-15), 7 lines; of them, 4 are for feeding the programs and 3 for resote monitoring and control. 115 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 _ FOR OFFICIAL CJSE ONLY 3. Between the central wire broadcast station and the transformer substation - three lines in the presence of FUZ and two if they are absent. 4. Between the central wire broadcast station and the substation block, 4 for program f eed and 4 for remote monitoring and control of the substation block. At the present time a system and equipment for pregram feed, monitorii~g and control are being built for the city TPB networks using modern remote control _ methods, in particular, the frequency coding systems insuring high reliabil- ity and noiseproofness [21]. This equipment has great possibilities for operative remote control, remote monitoring and obtaining broad information about the condition of the remotely controlled ob~ects using only one telephone pair in all. The diagram - of the equipment of the TPB system for the decentralized networks appears in Fig 2.51. - For the new remotz monitoring and control equipment (TU, TK) between the central wire broadcast station and each OUS [reference repeater station], UP or BP [substation block] 6 telephone pairs are required, of which considering the reserve, 4 are for the program feed and 2 for TU-TK; there are 2 pairs between the central wire broadcast station and the transformer substation. . The connecting lines in ~he sections from the central wire broadcast station to the reference repeater station, substation block or UP have a length ' from 2 to 25.3 1~, and in the TsSPV-TP section, from 2 to 26 lan. In the TsSPV-OUS section 67% of the lines have a length of up to 12 km, and in the TsSPV-TP section, 78% of the lines. It is necessary to install the inter- mediate repeaters on the connecting line for the program feed on cable lines with strands 0.5 mm in diameter, and with a diameter of 0.7 mm, 19 km long and more. The existing remote control equipment operates with a loop resistance no more than 4000 ohms, which corresponds to a cable length of 21 l~ with strands - 0.5 ~ in diameter; with strands 0.6 mm in diameter, 30 km long and 0.7 mm in diameter, 37 km. The voltage level of the broadcast transmission at a - frequency of 1000 hertz at any point of the connecting line must not exceed +17 decibels. The minimum admissible voltage of the sound broadcast trans- _ mission on the load resistance at the end of the line must be no less than 0.775 volts. The crosstalk attenuation between each pair of cables used for broadcasting and other pairs of the same cable measured on a frequency of 1000 (800) hertz must be no less than 78 decibels for the two pairs used, no less than 80 decibels for 6 pairs and no less than 85 decibels for 7 or more pairs. The connecting lines of the program f eed must correspond to the indexes of one or more quality class with respect to All-Union State Standard 11515-65. In order to improve the frequency characteristic of the telephone lines when using them in the sections of the WB channels, correct- ing c ircuits are used which are installed on the ends of the line. 116 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02108: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY i o . - ~ ~ ~ . r- ' ' � � a � ~ ~ ~ � ~a Qi I . ~c � g ~ ~ I ~c v 'c~ � ~ ~ r, ~ ~ a a~ w r~l 1J ~ ~ Cv ~ ~ ~ ' ~ a~ a1 . w ' ~ . vy cd cti . ~ O O ~ N ~ u - . ~ . . - ~ v'~ ~ . a ~ v~i a - E ~ ~ o ~ ~N ~ E , ~ ~ �1 ~ . ~ - z . . y 'b ~ i 0 a ' 0 e~ . W~ N ir1 Q v C~ . ~ c~o D, ~ ~ ~ ~.~i A ~ ~ . ~ ~ > ~v ~ H ~ o O e 'd ~ _ C 1~ b0 tA j~Arl - - ~ Cti ~o . e r~l 00 N~ A~ ~ . ~ Q d.C ~�Tl f~' U . � O ~ . O ~ rl G! ~J r-I . ~a C V ~ ~d .f~ ~ - _ a~ c0 u! U � Q e i~..i .C y�i . ~ ~ ~ a a~ I o~~ � y � _ cri ~ ~ ~ Q P. . ~ v 'v ~ ' cd ~ r, 1.. ~ T N . ' Q ~ ~ ~ ~ ~ ~ V . a C~' ~ �rl U v W ~ ~ ~ ~ V ~ ~ ~ N O ' ' � ' ~ ~ ,C S~+ v ~ ~ " e ~ ~ W ~ i~ ~ ~ \ . ~ Cl C! � ~ ~ . . ~ ~v H .~C 4~! ^ ' ' . ~ ,x v1 N Gal ~y � ~ ~ . ' . . (A e-~ C/I r~l i-1 @ ~ . . � ~p � ~ ~ O ~ ~ - ~ ' ~ ~ ~ v-I 't'I , , . . : . . . IC+~ N u r-1 c~ N p ` ~ ~ ~ ~ C'~ ~1! . . fd 1~ ~ � ~ . . . ' ~ ~ rl Q ~ ~ .5~+'~ - Fs.i ri . 117 FOR OFFICIAL L'SE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02108: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY _ CHAPTER 3. INTRODUCTION OF NORMS FOR THE TPB SYSTEM 3.1. General Information The introduction of norms for the TPB system consists in establishing - norms for the low-frequency and high-frequency channels and also individual devices and lines entering into these channels. The introduction of norms for the high-frequency channel is at the present time complete from the _ point of view of the presence of materials on standardization and design. - At the same time the introduction of standards for the high-frequency - channel and the devices entering into it is in the state of development and improvement; therefore, primary attention will be given in this chapter to the problems of introducing norms for the high-frequency channel, its ' devices and Tines. _ 3.2. Introduction Qf Norms for the Low-Frequency Channel - The introduction of norms for the low-frequency WB channel is defined by the All-Union State S~andard 11515-65 "Radio Broadcast Channels. Classes. Basic Quality Indexes." In accordance wit~ this standard, the amount of introduction of norms for the low-frequency channel is determined con- sisting of the normalized objects (radio relayl channels of different types) _ and the standardized quality indexes (the reproducible range of frequencies), _ the harmonic coefficient, and so on). The introduction of norms for the _ low-frequency channels has been carried out in the following form: through, from the beginning of the WB channel to the end (for example, the input of _ the central wire broadcast station to the subscriber unit), and by parts, (for example, the central wire broadcast station and the reference repeater station separately). Here the standardized through LJ3 channel is electrically perfected, that is, a channel after which the electrical signal conversi:on~ capable of 1The name "radio relay" is presented in accordance with All-Union State _ Standard 11515-65. - 118 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000240040065-4 - FOR OFFICIAL USE ONLY ~ rtiu~ln~ u c:liung~ in I.tE; quulity indexes does not take pliice~ und the aound c~uallty afer tliiH cl~annel ia determined in practice only by the propertiee oC ll~e rrproclucLng sound Nyelem. Actually, between the end of the normalized through channel (subscriber roaette) and thp voice coil of the speaker there are only passive elements the line control and transformer enter- ing into the subscriber speaker. The beginning of the nomoalized through WB channels is the first station object of the WB service: the central wire broadcast station far the centralized WB network or tt.e WB junction station, for the centralized network. The through low-frequency WB channels belong entirely to the WB branch of the Communications Ministry and from the realizational point of view, the normalization and responsibility for observation of the quality indexes ~ are concentrated in their hands alone, which facilitates the solution of the problems of normalization and control. From the technical point of view the normalization of the through low-frequency channel and parts of it also present special difficulties, for in the entire ~hannel there is only one type of signal low frequency and all the channel elements from the - point of view of normalization belong to two types: the low frequency repeaters and the transmission lines, which determines the likeness of the norm~lized characteristics and the measurement techniques. The basic goal in introducing norms for the low-frequency channel reduces to optimal dis- - tribution of the normalized quality indexes by parts of the through channel. In addition to the standard, for tiie l~w-frequency channel there are standards for the repeaters, transformers and subscriber speakers. Thus, from the organizational and technical points of view the normalization - of the initial low-frequency channel presents no special difficulties. In contrast, to the low-frequency channel, the normalizati.on of the high-frequency channels~presents great diff iculties: organizational and technical. 3.3. Intro3uction of Norms for the High-Frequency Channels By ttie high-frequency channel of the TPB system we mean the entire set of devices and lines designe3 to obtain high-frequency signals, transmit and receive them. In the most complete form for the thr~e-el2ment WB network the high-frequency channel is presented in Fig 3.1. For determination of the volume of the introduction of norms for the liigh-frequency channel it is necessary to define the normalized ob~ects and the normalized indexes of these objects. The normalized objects of the high-frequency channel must be the through channel and parts of it as is assumed for other sound broadcast ~hannels - and, in particular, for the low-frequency channel and also individual devices and lines. l l.9 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ( p t;,dM~~u,r l1Q ~M~i~iuA~ Tli ( P~pUHIIA~ I AOONCI!/lICXGA ~ ~ ~ ~7~ ~ ~9~ ~ ~ , i ceme (11) nr,~ ~e i ~ i i ; : _ ~ ynn ynrn � ~ ' ~ ~ ~ ~i~~ ~~P.~zo ~ i i ~8~ ' i . i (~o) . i . i i i i~~ i , ~ ~ . I ~ ~ I i i AT ~ ~nre � - ' ~1 ~ ' ~i i i . . i i (13) . ~ ~ Figure 3.1. High-frequency channel of the TPB system for the three- ~ - element network Key: . 1. Connecting lines 8. Transformer substation connecting 2. WB station circuit 3. Trans. 78 9. Distributing feeder line 4. Trans. 120 10. Subscriber transformer 5. Transmitter connection circuit ].1. Subscriber network 6. Main feeder line 12, 3-program speaker 7. Transformer substation 13. Group-pr~gram speaker In accordance with the specif ic nature of the normalized objects, they can be divided into the following groups: 1) The through channel and parts of it; 2) The transmitters and repeaters; 3) Receivers; 4) High-frequency devices and lines. _ The normalized indexes are of two types: 1) Quality indexes; 2) Electrical characteristics. The quality indexes pertain to the introduction of norms for the through channel and parts of it and also the transmitters, repeaters and receivers. ' The electrical characteristics pertain to the introduction of norms for all the station, line and receiving devices, and they are det~rmined specif ically for .each type of device.and line. - 3.4. Determination of the Through Channel The through channel at the high-frequency channel of the TPB syste~ is defined beginning with the most complete identity and comparableness of the - - low-frequency and high-frequency channels among each other with respect to normalization. Beginning with these arguments, the through channel ends with the output of the electrical part of the individual receiver or the 1~0 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY subscriber rosette in the case of the application of a group receiver. With this def inition of the end point of the through channel, the complete ~~o:;5tbility oC comparing the low-frequency and high-frequency ciiunnels - umonb eucli otiier t:~ acl~teved, for in both cases the electric channels ure ~ perfected, and conve,rsion of the electric energy to acoustic energy takes � - place after them. In addition, the normalization of such a through channel offers the possibility of defining the norms for the receivers and the parts of the channel beginning with observation of only the basic norms for the entire through channel. In this case the guarantee of quality indexes is also insured with recording on a tape recorder which is done - from the output of the individual receiver. _ The input of the transmitter is taken as the beginning of the thro~igh high- frequency channel, for this device marks the beginning of the high-frequency channel, and the program feed cl:annel up to this point is normalized with respect to All-Union State Standard 11515-65. With possible variation of the structure of the station part of the channel in accordance with the diagrams investigated in Section 2.7, the beginning of the through channel naturally is carried over to the input of the first cnnversion unit for ~ converting the low-frequency cha.nnel to a high-frequency channel. The high-frequency tk~rough channel adopted in this way is the initial ob~ect of the normalization of the high-frequency channel and can be normalized considering the quality classes of All-Union State Standard 11515-65. The through channels for different types of WB networks are illusrrated in Figures 3.2 and 3.3. (1) 3rrc~nyama~uoHyuu mpaKm /1D ~ - . ~ ~ TP.X - . . _ , _ (7 ) p~a~rervmcxna ' r~er~niu- ~ ~ . pavcmKm ;~d~ru . _ ~ns~h~to- ~I~O11JM ' OGQu/n6eS ~,~bdyw~~ ynn ~ 6 m.K~~ . . yc~po~icr~ea ~ (4> . ~o a . ~8) ~ - Gmar~qc~,y,~~rA . Ppynno0ot ~ /I6~~~,vmcxuA vdcme m,~sKmd . nprre.~yge. ~ ~3~ . - ~ ' . ~ yc~Bo PaacmKCt , . � C~eoaXOi~ mpo~m . ~9~ _ . Figure 3.2. Schematic of the introduction of norms for a wire broadcast channel with a three-element line section Key: - 1. Operating WB channel 6. Suscriber transformer 2. Transmitter 7. Subscriber rosette 3. Station part of the channel 8. Group receiver 4. Transmitter connection circuit 9. Subscriber rosette 5. Through channel 10. Three-program speaker 121 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY , 3.5. Definition of the Normalized Parts of the Through Channel The normalized parts of the through channel are defined as follows: - 1) By the limits of operating responsibility of the WB services; 2) By the selection of the channel points for monitoring and operating measurements; - 3) The necessity for normalizing the individual devices. The normalization of all parts of the channel is carried out with one co~non origin the origin of the through channel and different terminal points. ~l) 9rcnnyumrt4~a~~d~ mpa~rm AB ~ ' " . 7pe,r- ~ . . AL~oNEHmc,ras? ~ , r,;ctGgli- ~ . . ~ L~Nb~L' po3amKa c .^'//!0- ~ p�'~mre ~9) ~dop:cm t i~ I._; c~'c~: l:s~ ynll y/1Ti1 msxrrr"t 12 ~ r:,:.~:;~u,n~~ mp~i+c- ~2) ~3) 4 ~'m v fpy,;n~Due lr~N[;U0.9N?A ~8~ /IpiltdlJ.'OC A6nyeHmcyrwl ~ 4acme m,~anma ~5~ . ycmporc- po3emKa - � cmBo (I1) y~cm~ mpoxm~ nepcdQ:arqee ycin;,oi~- ' ~ ~6~ cmBn-BeixvdTi7 . . (10) . - C~On3Ha~i m aKm ~ Figure 3.3. Schematic of the normalization of a wire broadcast channel with a two-element line section Key: 1. Operating WB channel 8. Subscriber transformer 2. Transmitter 9. Subscriber rosette - 3. Transmitter connection circuit 10. Group receiver 4. Transformer substation 11. Subscriber rosette _ connecting circuit 12. Three-program speaker - 5. Station part of the channel 6. Part of channel from the transmitter to the output of the transformer substation 7. Through channel The entire set of high-frequency devices and lines for which the WB services have responsibility is defined as the operating WB channel (Figures 3.2 and 3.3). In the case of a group receiver the through and operating WE channels coincide. The introduction of the concept of the operating channel completely makes the low-frequency and high-frequency channels united for the WB services with respect to degree of responsibility for them, for the channel data end identically with the subscriber _ rosette. ' 121-a - FOR OFFICIAL USE ONT.Y APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 F0~ OFFICIAL USE ONLY T~~o channel points are normalized inside the operating channel: the output of the wire broadcast station, that is, the output of the transmitter - (Figures 3.2 and 3.3) and the output of the transformer substation, that is, the output of th~ transformer substation connecting circuit (Fig 3.2). The introduction of the norms for the station part of the channel determines all the basic initial quality indexes and electrical characteristics of the _ AM signals at the beginning of the high-frequency channel and provides a basis for standardizing the transmitter and the transmitter connection . circuit. The monitoring of many of the quality indexes and the electrical characteristics at the WB station is simultaneously monitoring of these indexes and characteristics of the entire operating channel, which greatly simplifies the performance of the entire volume of ineasurements on the network. The introduction of norms for the indexes at the output of the transformer substation ~or the high-frequency channel is carried out in order to main- tain the quality indexes within the norms which can undergo alterations - on transmission of the AM signals from the output of the transmitter to the output of the transformer substation. All of the above-investigated channels and parts of the channels are fully or partially standardized in accordance with the adopted list of quality inde.~ces of All-Union State Standard 11515-65. A number of the elements of the high-frequency channel are normalized by simpler method: two or three electrical characteristics (the input impedance, the trans- mission coeff icient, attenuation). These elements include the lines and the high-frequency devices of the line part of the channel, the common purpose of which is passive transmission of the high-frequency signals without converting the spectrum. The normalization of the lines and the high-frequency devices with respect to electrical characteristics are carried out separately. . 3.6. Quality Indexes of the Through Channel and Parts of It _ When developing and introducing the TPB system it was established that the most realistic for the through high-frequency channel is obtaining a quality class close to class II of VTU 526-58 [29], beginning with a number of economic and technical arguments. Her.eafter when introducing the standard for the broadcast channels All-Union State Standard 11515-65 in place of VTU 526-58, the norms for the quality classes underwent signif icant alterations; therefor~ the normalization of the through high- _ frequency channel remains in class II of A~1-Union State Standard 11515-65. The through high-frequency channel is normalized with respect to all the quality indexes of the All-Union State Standard 11515-65: The reproducible frequency band; nonuniformity of the frequency character- istic in the reproducible frequency band; the harmonic coefficient; the signal/background ratio; the signal/noise ratio; the signal/intelligible crosstalk ratio. 122 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY The introduction of norms for the indicated quality i~dexes and their significance for the high-frequency channels have some peculiarities. Thus, nonuniformity of the fr~quency characteristic ia normalized by the commonly accepted "normative standard" (Fig 3.4~ only for the through channels. For the operating channel and the station part, the nonuniform- ity of the frequency characteristic is determined by other standards, Figures 3.5 and 3.6. In these standards the distortions of the frequency , characteristic are reflected in the region of upper modulating frequencies introduced into the transmitters. Here it is natural that the tolerance on the magnitude of the distortions for the operating channel is increased ~ by comparison with the tolerance on the transmitting part of the channel. - ~ ' ~ (2) - ~ ' ~ . ~a~ � c , e e ~ h v 0 . y0 D~ 6 Ol?( ' - (1)� Figure 3.4. Nonuniformity of the frequency characteristic of the through channel Key: 1, hertz; 2. 3 decibels . ~ . _ . � ~2~ ~ � . ~ ~ ~ - ~2 ~ ~ ~ . - ( ~ ~ ~ - QO 0 60 0/t~~i~ � Figure 3.5. Nonuniformity of the frequency characteristic of the station part of the channel Key: 1. hertz; 2. decibel _ . . _ . ~ . . _ ~2~ ~ ~ " ~ . � . ~ ~ ~ ~ t2~ : ' : ~ ~ . q000 . ~ 600011( (1~ Figure 3.6. Nonuniformity of the frequency characteristic of the.operating channel Key: 1. hertz; 2. decibels 123 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 ~ FOR OFFICIAL USE ONLY The harmonic coefficient is normalized in three frequency bands instead of two as indicated in All-Union State Standard 11515-65. The normalization of the harmonic coefficient in the 200-4000 hertz band is broken down into two bands: above 200 to 2000 hertz and above 2000 to 4000 hertz. The lntraducCiun uE ~lie la:~t Crequency band ie caused by un increc?se in tl~e harmonic coeff icient in this frequency band as a result of the presence of asymmetry of the side frequencies of the AM signal on transmission of it - over the TPB line channel. The harmonic coefficient is normalized just as in the All-Union State Standard 11515-65 ~y two norms: for the rated level and the levels reduced ' with respect to the ratedlevel from 6 to 20 decibels. The second norm pertains only to the channels with devices having two- cycle low-frequency stages. The signal/noise background, signal/noise, signal/intelligible crosstalk indexes are normalized in the interval and in the All-Union State Standard 11515-65. However, when suppressing the carrier in the interval not only does a change in the signal/intelligible crosstalk ratio take place, but also two others. Therefore, for proper coordination of the norms with respect to these indexes, all the channels and devices of the high-frequency channel must be norma~ized and measured for the suppressed carrier. Consisler- ing the different nature of the origin o~ the crosstalk interference from low frequency and high frequency signals and the different magnitudes of these interferences in the intermediate points of the channel, the signal/ - intelligible crosstalk ratio is noimalized separately for interference from low frequency and adjacent high-frequency ~hannels. In spite of the orientation toward quality class II, some of the indexes - of the through ehannel are lower. The basic deviation from the norms in class II represents the signal/intelligible crosstalk ratio (50 instead of 70 decibels) defined by the effect of the nonlinear crosstalk from the ~ low-frequency channel on the high-frequency channels. However, if we compare even the value of 50 decibels with the admissible interference of the radi~ receivers and the long wave and medium wave bands (not talking . about the short wave band), it is obvious that this standard significantly exceeds the standards for the radio receiver interference. Thus, �or the - WB radio receivers according to ~411-Union State Standard 5651-64, selectivity with respect to the adjacent radio +10 kilohertz wide with respect to frequency, 34 decibels for class II and 46 decibels for class I is admissible; the admissible attenuation of the sigaial from the mirror channel is 40 decibels for class II and 46 decibels for class I. Here the - 50 decibel standard is limited for all admissible signal/noise ratios at the input of the TPB receivers at the same ti~ne as for the radio receivers the actual magnitude of the interference is determined to a great extent _ by the reception conditions. On introduction of complete separation of the carrier in the interval, the signal/intelligible crosstalk from the low-frequency channel ratio can reach 70 decibels or more in the broadcast 124 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY transmission interval. The increase in mutual protection between the high-frequency channels pertains basically to the receivers and requires increased selectivity of them. 'i'lu� K1Knii1/ba~~k~;rou~id rutlo 1~ inferlor by 10 decibele Co ttte clays li norms on the channels only for the three-program speakers. This assumption was adopted beginning with the low rated sound pressure of these receivers and the correspondingly lower noticeability of the background when listening. However, during tape recorder recording of the programs of the high-frequency channels and reproduction of them by the devices with high sound pressure the noticeability of the background rises. Later the signal/background ratio for the channel with the three-program speaker in class Ii will be increased from 40 to 45 decibels. Insignificant deviation with respect to the harmonic coefficient from the norms in class II of All-Union State Standard 11515-65 (5% instead of 4%) is permissible in the frequency range of 2000-4000 hertz as a result of specific distortions of the envelope of the AM signal occurring in the WB lines as a result of asymmetry of the extreme side frequencies of the AM signal. When introducing the norms for the operating channel and parts of it, the uormalized quality indexes for each point of the channel are defined beginning with efficiency of the measurement of certain quality indexes at the given point of the channel. It is known that the labor consumption of performing the measurements in the WB channels increases in the direction from the station to the subscriber point. Therefore, in the intermediate channel points it is sufficient to li.mit ourselves to the normalization and measurement of only the indexes which in practice undergo changes on transmission of the AM signal from the preceding point to the investigated one. Beginning with these arguments, it is sufficient to normalize the - operating channel to the subscriber rosette of the three-program speaker - by the n~nuniformity of the frequency characteristic in the given frequency band. Here it is sufficient to perform the measurements of this nonuniformity in the frequency range of 1000 to 6000 hertz and also to normalize the harmonic coefficient in the frequency band of 2000-4000 hertz and the signal/ intelligible crosstalk from the low-frequency and high-frequency channels ratio separately. For the part of the channel ending with the output of the Cransformer sub- station, the number of normalized quality indexes can be reduced to two: - the harmonic coeff icient in the frequency band of 2000 to 4000 hertz and the signal/intelligible crosstalk from the low-frequency ratio. The WB station is normalized, just as the through channel, with respect to all the quality indexes. This procedure for normali~ing the quality indexes - of the through channel and parts of it is regulated by the draft of the branch standard "High-Frequency Channels of the Three-Program Wire Broad- casting System. The Basic Parameters," developed by the Scientific Research Institute of Radio. The norms in the draft of the indicated standard for the through channel and parts of it are presented in the appendix. - 125 FOR OFFICIAT, USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICiAL USE ONLY 3.7. Introduction of Norms for the Transmitters and Repeaters The normalized electrical characteristics of the transmitter must reflect tliree of ita functions: as the tranamitter of an AM aignal, as the device connected L�o tlie Wli network, and as the tranemitter of tl~e AM signal with regulatable carrier. The first fact makes it possible to introduce the norms for the transmitter with respect to the series of parameters analogously to the broadcast trans- mitters of the long wave and medium wave bands in accordance with All-Union State Standard 13924-68 "Transmitters, Radio Broadcast, Station. Basic Parameters." Accordingly, the carrier frequencies, the relative dev3ations of the ~arrier frequencies, the rated modulation coefficient, the relative harmonic levels of the carrier frequency, the rated powers and voltages of the carrier frequencies, the rated input level and the input impedance of the low- - frequency input are sub~ect to normalization. The connection of the transmitter to the WB network requires consideration of the actual dispersion of the load resistance with respect to modulus and phase; therefore, the normalization of the output power must be carried out not only for. the rated active load as for the radio broadcast transmitters, but also for a load equal with respect to modulus to ~he rated one, and with the positive and negative angles. In order to maintain constancy of the output voltage of the carrier frequency on variation of the load resistance it is necessary to introduce norms for the output impedance of each transmitter or increase the voltage when dropping the load analogously to introduction of norms for the low frequency repeater. The presence of a regulatable carrier requir~s introduction of norms for the limits of automatic gain control of the carrier frequency, the buildup time and the decay time. _ The standardization of the carrier frequencies for the two high-frequency channels is necessary, for the TPB system, independently of its territorial - application in the country, must have the same carrier frequencies; in the given case these are 78 and 120 kilohertz, wherein lies its significant diff erence f.rom the introduction of radio broadcast norms in which the - frequency band is given and the carrier frequencies of the radio broadcast stations are distributed by the territorial principle. The standard~.zation of the relative deviation of the carrier frequencies pursues two goals: exclusion of the noticeable draft of the carrier fre- quencies in the presence of f ixed tuning of the receivers and the appearanc.e ~ of noticeable beats of the carrier frequencies from the two like trans- - mitters wi.th significant parallel run of the feeder lines from~ the trans- mitters. 126 FOR OFFICIAL USE ONLY ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAI. USE ONLY The relative deviation of the carrier frequency ~ ef _ li--fol ~ : : . . 10 : ~o . _ (3.1) where f0 is the standard carrier frequency, kilohertz; f is the actual carrier frequency, kilohertz. The relative levels of the carrier frequency harmonics basically falling in the long wave radio broadcast band are normalized to exclude the inter- _ ference of the radio receivers .tn this band from the TPB system. - The harmonics of the carrier frequency are normalized with respect to each harmonic individually and this pertains only to the most noticeable harmonics the second and third for each carrier (156, 234, 240, 360 kilohertz). The relative level of the carrier frequency harmonic is . A~.= 201g ~Ut'~ ~ As,(.?) ~ (3. 2) Key: 1. rated; 2. decibels where UO rated is the rared voltage of the carrier frequency; Ufn is the voltated of the n-harmonic of the carrier frequency. , The rated power with respect to the carrier frequency for each transmitter is deterneined in the active rated load resistance for the AM signal with rated depth and modulation frequency of 1000 hertz. The criterion for the rated power pickup by the transmitter is satisfaction of the norm with r~spect to the harmonic coefficient for the indicated modulation frequency; here the output power is U~ . � ~ = ~ ~'p o~. BT, ~2) ;3.3) R�(3) ~1~) Key; l. rated; 2. watts; 3. load where Up is the voltage of the carrier frequency, volts; Prated is the rated output power; Rg is the rated load resistance, ohms. For transmitters with t=.~o secondary windings of the output transformer the resistances 2Rg are connected to each winding, and the output power is defined by the formula (3.3). However, in contrast to the radio broadcast transmitters, the basic guar- anteed value for operation of the transmitter in the WB channel is not - the rated power, but the rated voltage of the carrier ~ust as for the - station low-frequency repeater it is the output voltage of the low-frequency signal. 127 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY 'Tlie rated voltage of the carrier frequency ~p~= P~~~B. . (3.4) Key: 1. rated; 2. load The modulation coefficient m for a regulatable carrier has complex dependence _ on the magnitude of the modulating signal (Fig 2.40), and basically its maximum value is normalized corresponding to the rated voltage of the carrier. The maximum modulation coefficient is assumed equal to 0.7 considering the difficulties of detecting the AM signal with variable carrier. The limits of automatic control of the carrier in the given dynamic range of leveis of the modulating signal _ . . . UG HOM~ . : ~h~,K~ = 20~g~o~ ~ As. El) ~ (3.5) ) Key: 1. decibels; 2. rated; 3. min; 4. max . where UO min is the minimum. voltage of the carrier correspondjag to the minimum given level of the modulating signal. The voltage buildup time of the carrier frequency is defined by the time during which the ratio of the carrier frequency reaches a value of 0.9 UO rated for feed of a voice signal to the receiver input with a frequency of 1000 hertz and rated input level (Fig 3.7). The time for the voltage drop of the carrier frequency is defined by the _ time during which the voltage of the carrier frequency at the output of - the transmitter decreases from rated to 0.2 UO rated after picking up Ehe - modulati.ng signal from the transmitter input under the conditions that ~ the limits of regulation of the carrier are 20 decibels (Fig 3.7). 4 - . ' - ~I!~ ~ ~ ~7NAM ~1 ~ . : Q?Do~ar M~N ~ ~ _ ~ ~ ^ 'S' . tN , ~ Y~~ ~ � Figure 3.7. Determination of the buildup time and the decay - time of the carrier frequency voltage Up at the transmitter output Key: 1. rated ; 2. outside; 3. connecting line 128 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY . The high-frequency amplifiers installed in the high-frequency channel at the present time include the two-channel intermediate repeater (DPU). With respect to the output part the repeater is analogous to the trans- mitter; therefore the standardization procedure ar:d the proceciure for determining the quality indexes basically is the same as for the transmitter. liowever, there are some peculiarities. A distingu ishing feature is the normalization of the nonuniformity of the frequency characteristic and the harmonic coefficient. Inasmuch as in the repeater of the AM s3gnal there are no causes for variation of the non- uniformity of the frequency characteristic and the harmonic coefficient in the range of low modulating frequencies, the nonuniformity of the frequency characteristic of the repeater is sufficiently normalized and defined in the frequency spectrum of the AM signal, that is, for the DPU [two-channel intermediate repeater] in the fp+6 kilohertz band, both for resonance and band repeaters, and the harmonic coefficient can be normalized beginning with 1000 hertz and more. All of the signal/noise type ratios are normalized a~nd defined by the relatively normalized suppressed carrier. The norms for the quality indexes for the DPU were obtained beginning with the actual possibilities of introducing minimum additional distortions into the through channel. The normalized electrical characteristics of the DPU are as follows: the rated output power and the output voltage ~f the carrier; the maximum gain; the gain control limit; the input impedance in the AM signal band. Inasmuch as the two-channel interme~iate repeater can be used f or a signif icant interval of input voltage~, it is not the rated input voltage that is normalized, but the maximum gain and the limits of the gain control. Under actual operating conditions the output voltage of each carrier frequency is defined by insuring sufficient voltages of - the high-frequency signal in the entire segment of the line included after the repeater (Fig 3.8). - The specif ic norms for the quality indexes and the electrical characteristics are presented in the corresponding sections of the description of the given devices. 3.8. Introduction of Norms for Receivers The receivers in the TPB system can be divided into two groups: individual and group. The introduction of norms for each of these devices has its own specif ic nature. At the present time basically two types of receivers have become widespread: the three-program speaker (GT) and the group receiver (GPTV). The characteristic features of their standardization are investigated below. 129 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ~ ' �l~,~ ~1) . . � � . ' � = 319 ~ . ' ~ . . . . !p - ~ " . ~ ~rte 3} ~ ~ d - - ~ � II?ica~~ ~ f~~n? _ . ~ y~dn yo~iru Figure 3.8. Diagram of the carrier frequency voltage on the distributing feeder line with two-channel ~ intermediate repeater ~ Key: 1. volts; 2. point of installing the two-channel intermediate repeater; 3. UO ad 3 4. JC~X; 5. 1cm The introduction of norms for the three-program speaker is done in accordance with All-Union State Standard 18286-72 "Three-Program Speakers. Tech~ical Specifications." The group receivers are normalized with respect - _ to technical conditions. Here the three-program speakers are normalized as electroacaustic devices, and the group receivers, as electrical devices. The three-program speaker is normalized with respect to acoustic and . electrical indexes. The introduction norms f4r the low-frequency channel of the three-program speaker corresponds basically to the All-Union State - Standard 5961=66 for the single-prAgram subscriber speakers. The norms - for the acoustic and electrical indexes of the three-program speaker on reception of high-frequency signals have b~en established with respect to classes I, II and III. The acoustic indexes of the three-program speaker are determined by the sound pressure, and they include the following: the rated frequency band, nonuniformity of the frequency characteristic in this band; the average sound pressure and tbe harmonic coefficient. These indexes have the same def inition as ttie corresponding indexes of the radio receivers and the subs~riber speakers. Here the normalized nQnuniformity of the frequency characteristic of the average sound pressure must be satisf ied considering distortions in the upper frequency range of modulation (Fig 3.5). The harmonic coefficient is also normalized and def ined without considering the distortions. ~ 130 ~ FOR OFFICIAL USE ONLY I APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4 FOR OFFICIAL USE ONLY The normalization of the quality indexes of the electrical channels of the three-program speaker and the group receiver (GPTV) is carried out identically except that for the three-program speaker the electrical channel is normalized on the voice coil of the given speaker, and for the group receiver, at its output for any real load. For the three-program speaker of classes I and II, these quality indexes must satisfy the require- ments of obtaining the corresponding quality classes for the through _ WB channel. For the three-program speaker of class II, the satisfaction - of this condition is not mandatory. The nonuniformity of the frequency characteristic with respect to the electric voltage in the rated frequency band is also defined considering the distortions of modulating frequencies - in the subscriber rosette of the three-program speaker or at the input of the group receiver. Simultaneous satisfaction of the requirements of non- uniformity of the frequency characteristic with respect to sound pressure and electric voltage for the three-program speaker does not cause any mutual difficulties and, moreover, the observation of the nonuniformity ~ with respect to the electric channel promotes obtaining of the given non~ uniformity with respect to the acoustic channel. Inasmuch as the normative "standard" for nonuniformity of the frequency characteristic of the through channel with respect to All-Union State Standard 11515-65 can have any form within the limits of the given nonuniformiCi~s F1 and F2, it appears possible to correct the frequency characteristic for the electric channel correspondingly for satisfaction of its nonuniformity with respect to the acoustic channel, which has significance for the edge, especi.ally the low frequencies of the standardized range. The standardization of the harmonic coeff icient of the electrical channel ` of the TPB receivers has several peculiarities by comparison with the normalization of the radio broadcast receivers. The harmonic coefficient of the radio broadcast receivers is normalized - with respect to the sound pressure for a rated modulation coefficient and - average sound pressure. In the presence of the regulatable carrier the - normalized basic harmonic coefficient of the electric channel of the TPB - receivers must be observed in the entire range of carrier regulation for the corresponding modulation coefficients. This requirement pertains to - the AM signal detector creating nonlinear distortions of the envelope for small carrier voltages at its input. In the p.~esence of the low-frequency - channels of the receivers of the two-cycle repeaters the harmonic coefficient for output voltages equal to 0.1-0.5 of the rated must not _ exceed 0.5 af the basic one. The latter cond ition pertains to the GPTV - [group receiver] and the GT [three-program speaker], classes I and II, entering into the through channel. For the three-program speaker having a high-frequency amplif ier, the standard with respect to Kr must be observed for the given increa.se in the input signal. Out of all of the types of interference the greatest complexity is off ered by the normalization of the signal/intelligible crosstalk ratio. This f ratio must be def ined for all types of interf erence when receiving AM ~ signals. 131 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4 FOR OFFICIAL USE ONLY The interfexence from the low-frequency signals of program I, the high- frequc~ncy signals of the ad~acent high-frequency channel, and the aignals I: ruin ll~~ rudio brouJca~~ yLaLlons are oI tl~ia type. All of this interference in the TPB receivers is determined by the characteristics of the input frequency selectors, thcir structural execution and the presence of communications between the low-frequency amplif ier of ~ the receiver and the low-frequency program channel. i When normal~zing the existing TPB receivers with respect to the indicated interference ther.e is no united terminology. The terms "mutual protection," "interferen�e protection" for the three-program speaker, and "crosstalk interference" for the GPTV group receiver nre encountered. Therefore, hereafter we shall use the term adopted in All-Union State Standard 11515-65: signal/intelligible crosstalk ratio or, for short, the signal/noise ratio with indication of the type of noise. The signal/noise from the low-frequency channel ratio is normalized with respect to the maximum voltage of the low-frequency jigna.l at the inpnt of the receivers equal to 30 volts. For interference with the low-frequency and high-frequency channels the signal/noise ratio is normalized on the average interference frequency of 1000 hertz and upper interference fre- quencies of 6000 hertz for the three-program speaker and 10000 hertz for the group receiver with constant value of the input in~erference signal. The adopted signal/intelligible crosstalk from the ad~acent high-frequency signal ratio must be insured for the worst conditions of nuise protection of the receivers, that is, for maximum voltage of the carrier of the adjacent high-frequency channel of 3~volts and for a ratio of the voltages - of the carriers of the adjacent and recPived high-frequency signals of 30:1 cor;.esponding to suppression of the useful signal carrier by 10 ti~es. When defining the signal/noise ratio for the given type of interference it is necessary to use joint inclusion of the signa.l and interference - sources at the input of the receiver. - The no�rmalizati~n of the signal/noise rati.o from the radio broadca.st stations pursues th~ goal of insuring noiseproofness of the TPB receivers ~ with respect to this type of interference. In this case it is necessary to consider the diff erent effect of it on the circuitry of the TPB receivers. In order to determine the gi~�en intprference it is sufficient to limit ourselves to the long wave radio broadcas~ range. _ The volume of tY~e signal/intelligible crosstzlk ratio for all of the indicated types of interf erence in the receiver is taken from a comparison with the magnitud~ of the nonlinear crosstalk occurring in the line and it is equal to 53 decibels at a frequency of 1000 hertz. ~ The introduction of norms for tha signal/background and signal/noise ratios does not have signif icant peculiarities and is carried uut for the - suppressed carrier or in practice in the absence of it. Actually, ~ 132 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ~ _ considering L-he noticeable excess of the background level of the noise level, it is possible to limit ourselves to the normalization oC the signal/ _ (backgroun.d+noi3e) ratio or the signal/background ratio. Here, by the - background voltage U~ we mean the value of , U~ ~Ubo U oa + Uibo~ ( 3. 6) where U50~ U100~ U150 are the harmonic voltages of the background with frequencies of 50, 100 and 150 hertz respectively. All of the above-presented signal/noise ratios are defined by the formula - U~ ~ , A~=201g , As,(2> (s.~) . U,~,x ~3~ Key: 1. rated; 2. decibels; 3. interference ' where Urated is the rated output voltage of the electric channel; Uinterference is the voltage of the corresponding interference. The rated output power Prated is normalized for the rated load resistance and the modulation frequency of 1000 hertz; the criterion for picking up - the rated power is the satisfaction of the given harmonic coefficient. The rated output voltage used when determining the signal/noise ratio is as follows: 'L~~ox ~i~ (1) . (3. 8) - O Key: 1. rated where Rrated is the rated load resistance. For the three-program speaker ` this resistance is equal ~o the resistance of the voice coil of the speaker. The sensitivity of the three-program speaker and the group receiver is normalized for the rated output power and the input AM signal with modula- tion frequency of 1000 hertz and modulation coefficient of 70%, and it is determined separately with respect to the high-frequency channels. The - variation in sensitivity of the three-program speaker is accomplished by preset regulators. The limits of their control are normalized, beginning with the possible difference between the maximum and minimum values of the high-frequency signal voltages obtained on the subscriber rosettes depending o,i the point of connection to the distributing line. Inasmuch as the receivers are connected to the TPB distribution network, _ it is necessary to normalize their input impedances for elimination of , their effect on the quality indexes of the channels and the electrical characteristics of the line part of the TPB systems channel. 133 . FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 I FOR OFFICIAL USE ONLY The i~nput resistances are normalized in the band of received signals of the given high-frequency channel and in the bands of the ad~acent high-frequency - and low-frequency channels given by the selected quality class of the system. When using the low-frequency repeater of the three-program speaker for receiving low-frequency signals ("active version" of low-frequency reception), the parameters of the channel are also normalized. The normalization of the quality indexes is carried out with respect to the sound pressure and with respect to the electric vo~.tage analogously to the investi- gated method of norr~,zalizing the high-frequency channels. The norms of the quality indexes of the active low-frequency channel can be established just as for the high-frequency channel or higher, taking into account the higher quality indexes of the low-frequency channel on the subscriber rosette. In order to avoid the appearance of interference from the detection of AM signal in thP amplifying channel, the signal/noise ratio from the high- frequency channels is nortnalized for maximum input voltages of the high- frequency signals. Among the electrical characteristics for the "active version" of reception of the low-frequency signals, the sensitivity and the input impedances are normalized for all signals. The sensitivity is normalized with respect to the united rated output power of the electric channel, and i.t is taken equal to the minimum admissible voltage of the low-frequency signal at the subscribEr point, which permits compensation and the attenuation of the low-frequency channel. Theinput impedance in the frequency band of the low-frequency channel is normalized several times (4 to 8 times) higher than the corresponding input impedance of the _ signal-program speakers and the passive low-frequency channels of the three-program speakers which permits the load of the low-frequency TPB channel to be decreases. On the whole the normalization of the three- program speaker with respect to the active low-frequency channel corresponds to obtaining greater output power with lower input voltage and greater input _ ' voltage with respect to the preserved passive channel. The presence of the active low-frequency channel of the three-program speaker makes it possible to reduce the norms that are difficult to satisfy with respect to the passive channel, for example, with respect to the average sound pressure. The group receivers are normalized with respect to static and time operating parameters of the automatic gain control. The static characteristics of the automatic gain control are the control range with respectto input and the limits of variation of the output voltage. The normalization of - these characteristics is carried out jointly in the form of determination � of the minimum range of variation of the output level for the given lim~its of variation of the input level (Fig 3.9). The norm for the limits of variation of the output level of the group receiver of 3 decibels is _ taken from comparison with the admissible variations in level wfth respect _ to the low-frequency channel equal to 4 decibels. The norm for the ragulation band with respect toinput is determined from calculating the maximum fluctuations of the input level as a function of the weather con- ditions. The range nf control with respect to the input Dinp and the - 134 FOR OFFICIAL USE ONLY = APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ~ - limits of variation of the output level Dout are defined by the existing formulas: w us~t ~xe ~ A~~ ~ ( 3. 9) D = 201g 1 , ~:~ea(2) ' D - ZOI VeaxYaKC(3) B(7) (3.10) ~ ~`~6~ g u,~: Key: 1. inp znax; 2. inp min; 3. out max; 4. out min; 5. DinP; 6. Dout' 7. decibels Here the rated voltage is taken as�.the maximum output voltage. _ When putting the group receiver into operation it is necessary to establish some mean initial output voltage Uout mean by the regulator in order to insure the possibility of operation of the automatic gain control in the direction of increasing and decreasing the input voltage. In practice - Uout mean 26-27 volts is no less than the voltage at the subscriber point with respect to the low-frequency channel, and the equality of the volume of a11 three programs is not disturbed. . - . . U,~,~ 3Z------- ~ ~ t~ ~4 ~ - . I . ~ . � ~ 1 ~ " i � ' -~-�,m� (5) ~.6)~v,rm~c~mr~7) - Figure 3.9. Determina.tion of the control range of the automatic gain control with respect to input ' Key: 1. Uout 4� Uout min 2� Uout max 5� Uinp min 3. Uout mean 6� Uinp max 7. UinP The time characteristics of the automatic gain control are the response time of the automatic gain control and the time of increasing the gain of the receiver by a given amount. The response time of the automatic gain control is determined by the time during which the output signal is - distort~.~ (limited) on heating the AM signal to the receiver input with . maximum input voltage and rated depth of modulation with the initial dis- charged capacitor of the detector of the automatic gain control. The time for increasing, the gain is determined by the time during which the 135 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY output level af the signal increases by a given amount af ter the decrease in input maximum voltage by several times. As is assumed for the repeaters operating on a variable load, for the grnup receiver, the increase in output voltage on dropping the load ie normalized. 3.9. Introduction of Norms for High-Frequency Devices and Lines The introduction of norms for t?igh-frequency devices and lines is done to - provide for t~ansmission o~ high-frequency signal power with least losses and observation of the quality indexes of the envelope of the AM signal within the limits of the admissible values. The transmission of the high-frequency signal power i$ determined by the normalization of ~he transmission coeff icients of the high-frequency devices, the attenuations of the lines and moduli of the input impedances of the high-frequency devices and the lines on the carrier frequency. . The reduction of the additional distortions of the quality :Lndexes to a minimum is provided for by normalization of the transmissioa coefficients, the attenuat3,on, the modulie of the input impedances and the phase angles of the frequency bands of the AM signals. The transmission coefficient of the high-frequency devices .is a value ~R = . ~ ~3. ii> - ul where U1, UZ are the~.input and output voltages of the given frequency respectively. For converiieace of the overall calculation of the line attenuation and the attenuation of the high-frequency devices,~the attenuation of the high- frequency devices is used ~ a= 201g 1 a A~� ~1~ ~ ~3.12~ K~ Key: 1. decibels The transmission coefficient is normalized for equivalent load resistance. _ The modulus of the total input impedance Zinp and the hase angle ~ are components of the complex input impedances zinP Z~ e~~. For the high- frequency devices Zinp and ~ are normalized for equ~iva.lent load resistances, and for the line they are normalized for a real load. The devices of the low-frequency channel used to transmit high-frequency - signals, just as the subscriber transformer, or included parallel to the 136 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL t3SE ONLY high-frequency channel through the blocking f ilters (ZF) , as the f eeder transformer of the transformer substat~on and the KRF box and also the ~ single-program speakers, are not normalized with respect to the high- frequency signal~. The average characteriatics of the subscriber transformers ~ ZT and aT and the single-program speakers are determined by measurements, and they are used when calculating the attenuation of the distributing - feeder lines and the subscriber network. The necessity for normalizing the high-frequency devices and lines in the frequency band of the AM signal is determined by the fact that with an inc.rease in the modulating frequency the frequency band of the AM signal expands, and the asymmetry of transmission of the lower f~-F and upper fp+F transmission of the side frequencies of the AM signal appears. This asymmetry is expressed in inequality of the transmission coefficients and their phase angles for the frequencies f~-F and fp+F (Fig 3.10). Here the value of the resultant vector of the AM signal UP (Fig 3.llb) varies not according to a sinusoidal law, which leads to the appearance of non- linear distortions of the envelope of the AM signal (Fig 3.12), and, - consequently, distortion of the low-frequency signa.l at the output of the rec~iver detector. Thus, the given nonlinear distortions of the envelope of the AM signal are caused not by nonlinearity of the transmission - channel, but its asy~etric frequency and phase characteristics in the frequency band of the AM signal, which gives rise to the necessity for r_ormalization of the values of K, a, Z, ~ in the frequency band of the - AM signal for insuring the given Kr at the input of the receivers. The practical noticeabili~y of the given nonlinear distortions occurs for the modulating frequencies above 2000 hertz, which is one of the obstacles for expanding the reproducible frequency band of the high-frequency channels and improvement of their quality indexes. ~ � ~ , ,ti . . . ~ , ~ y ~ - f-f ~ f.~f .f Figure 3.10, Asymmetric frequency-amplitude and frequency- phase characteristics ~ _ 137 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY . al ' . ~ . - 'bj . ~ . . . - ~ . i . . X~ �'I~ ~ ~ b', L~.? . f ~ � /S?tfs? - ~ . ~Z~ I .t~~ . . : $ : ' . . - ` . ~Lo ~ . _ - _ . . y L+1~~ - � . , . . ~1� t . , . - . . . ' I ' . ~ - : . . . . Figure 3.11. Vec~or diagram of the input and output AM signals: - a) uri'distorted; b) distorted U ' ~ . . , . . ' ~ ~ ~ ? ~ ~ S i�~ ~ ~ ~ ~ ~ ~ ~~lt, { ~ ~ ~1. . ~ f i , ,j t . ~ ~ l ' . ~ ~ , . . ~ ~ . ~ , , . Figure 3.12. One of the types of distortions of the envelope of the AM signal for asymmetry of the side - frequencies ~ A characteri~tic feature of the normalizativn of the feeder lines and the devices with respect to the high-frequency channel is the necessity for insuring matched operating positions of the feeder lines. The wave impedance of the distributing feeder line, but not the pure line as in wire communicattons but the real line loaded on the subscriber transformers, appears in the role of the initial normalizing parameter. This equivalent wave impedatrce Z~ve equiv determines the norms for the Zinp of all the high-frequency devices installed on the distributing feeder lines and also the total magnitude of the load resistance with respect to the high fre- quency signals of the transformer substation for the stations with two- - ele~ment network. The value of ZWave equiv is determined by the type of wires, the density of the included subscriber transformers per km of line S and their type. 138 FOR OFFICIAI. USE ONLY _ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 I - FOR OFFICIAL USE ONLY As !he performed studies and calculations have demonstrated, insurance of ~Ite matched orerating conditions of the main and distributing feeder lines can be connected with normalization of the admissible harmonic coefficient occurring as a result of asymmetry of the side frequencies. Thus, it appears possible to ~oin the energy and quality criteria of the operating lines into one. Moreover, it is possible to estimate these two indexes by using the total input impedance of the feeder line as the initial paxameters zi~p=Zin ei~, that is, the parameter fixed at one point, and not distributed along t~ie line. In order to estimate the operating conditions of the lines it is possible to introduce the indexes of the degree of matching with respect to input impedance for the carriers and side frequencies: - ~1) - ~oet~. = ss ~ ~ie~~, _ rl ...'r~se~~..~ ~s . . _ . . . - ~so ss:t . . . . s'x~ ~4~ . . . ~ (z). . . : ~ (3). : . . (3.13) Key: 1. wave; 2. inp 0; 3. inp 19 4. inp 2 where zWave is the total wave impedance of the line equal to zWave equiv~ zinp 0~ zinp 1~ Zinp 2 for the distributing feeder lines as the total input ~mpedances of the line respectively on the ca~rier, lower and upper side freq~iencies. In order to estimate the degree of deviation of the modulus and the phase angle of theinput impedance from symmetric, the asymmetry coeff icients are ' introduced: . : Q� 1 Zsxo _ Zsxo . Q _ 1 isao . Zezo` - I; - . ~ _ ( . ~ s - -I- l ~ ~ Z . \Zaxt . Zsxi~ 2 Zesi Zaxs ! . . - , ^ -+I~ ~ es _ - $o� .~3:1`~) . . 2 . 2 . . Beginning with the condition for the through channel Kr~S% on a modulation - frequency of 4000 hertz, the maximum admissible Kr is defined for the line part of the channel: . Kr ~ Y5' - 43 = 3 0/ . - ~ ~ (3.15). Correspondingl.y, the asymmetric coefficienta of the frequencies of fp�6 kilo- hertz and the degree of matching with respect to the carrier frequency must be the following: , Q~ < o,15; Qa s o, l~; e~ ~ i o�; e, < io�; 0,7 s n s i,5; . ~po < l 5�. � . ~ . : ~ (3.16) ~ ; 139 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY The calculation of the damping of the line part of the high frequency channel is carried out beginning with the condition that the main and the distributing feeder lines have been processed, and traveling wave conditions with respect to high frequency signals are insured for them. The total attenuation of the three-link network channel from the output of ~ the transmitter to the input of the receiver is defined as: ~vs = ~?nn ~ aMm + aovrn ~m � a= ~.a. AS. (3.17) Key: 1. decibels ~1~ where a?�nn, ~~~tp, Qqy':n+ aP~ , as, aa6 are the attenuation of the trana- mitter connection ~circuit, the main feeder line, the transformer substation bypass, the distributing feeder line, the subscriber transformer and the subscriber network respectively. For the same two-link network channel the attenuation - ~v~ � avnn apm c~r a�~, A~ ~ ~ ($.1$) - Key: 1. decibels The maximum admissible attenuation of the n~twork aad is defined by the rated output voltage of the transmitter carrier UO trans and the minitaum admi:ssible voltage UO rec at the input of the three-program speaker: aA~ = 201g U= = 201g i2o = 53,5 ~i. (3.19) ~1~. UoDp~g~ 0,25 ~4~ . Key: 1. ad; 2. trans; 3. rec; 4. decibels For any point of the TPB network the following condition must be satisfied: a~ ~ aA�,. . ' ~ . . (3.20) - The components of the total attenuation of the attenuation of the iadividual devices and lines. The attenuations of the transformer substatian bypass [OUTP] and Che AT [subscriber transformer] are determined~depending on the load resistance or the number of subscriber points in accordance with the graphs in Figures 2.15, 2.17 and 3.13. The attenuation of the transmitter connection circuit for the three-element network does not exceed 2 decibels, and for the two-element network, no more than 10 decibels. _ The attenuatior. of the main feeder line in general form is 14~ FOR OFFI~IAL USE ONLY . APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL FJSE ONLY . ' aM~l~ a d a~ - ~ . ~ (3.21) - Key: 1. main f eeder; 2. insert where ak is the attenuation of the overhead part of the lines; aBQB is the attenuation of the cable insert. The attenuation of the short cable inserts is not taken into account. The attenuation of the distributing feeder line in general form ~ . . . ap = ~ 1 + QB 0 a� o~r,, - (3.2z~ ~1) ' . ~ ~a) . � ~r.=I ' ~2) - ' Key: 1. distributing feeder; 2. lead; 3. insert where tx~ is the attenuation of the overhead section of the line; is the equivalent attenuation per kilometer; aBl~B is the attenuation introduced by the long cable inserts; E~an lead is the total attenuation introduced by the lead; the attenuation introduced by one lead ~an is determined by the point of connection of the lead (Fig 3.15 and 3.15). _ 4~ Q22 - a20 - - a,a . . als ~ - o,,y i rAr�z � o,iz � o,~ ~ o,ae 2 ~ . ~e . a,os O,dV . ~~8~,~ 120r 2 a0z ~ rAr-m3~� ' ~ ZD 30 40 50 6C 70 BO N'mp~ Figure 3.13. Transmission coeff icient9 kT of the TAG-10 and � TAG-25 subscriber transformer as a function of load Key: 1. TAG-25; 2. kilohertz; 3. TAG-10; 4. NPoint 141 FOR OFFICIAL USE ONLY t. APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY _ . _ :'~A~ f (3). M ' . ~�rZ~ � J . . . Z~~~ t ~l . ; . � X.NM � ! Y J p S ~ f~lZOxlf~ : ' : ( 4~ ~3~ , . ' q Z~l. � . . ( (2 . : J ~ . t+iarl'll~ , . ~ t . . ~ ) ~2 ~ ~ ~ X~~ � i Y � ~ 6 Figure 3.14. Attenuation introduced by the lead as a function of the point of connection of it for a steel 13ne (x is the distance from the beginning of the line) Key: 1. lead 4� ~al~d, decibels ~ 2. wave 3. kilohertz The attenuation of the subscriber networ~: aab is determined separately for the building ~networks and the subscriber lines. Dependiug on .the number of floors, the attenuation of the building networks does not exceed the f ollowing: 2 decibels for 5 to 9 story buildings, 5 decibels for 12 to 19 story buildings. For the subscriber lines it is recommended that the following damping be - used� for a length of 0.3 km, aab=3 decibels; for a length of .0.3 to 0.6 km, aab=5 decibels; for lines of more than 0.6 lan, aab~10 de~ibels. Here, by the len~th of the subscriber line we ffiean the length of the line from the subscriber transformer to the most rea~ote point plue .the:length of all the branches included in the second half of the subscriber line. ~ 142 FOR OFFICIAL USE ONLY ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY _ M t^ia~rp ` , . p� d ~ ~ 1 e-2t44 . 8 ~ . , , ' ~ 1 t J y .Sr~M~i. ,d~~6 � ~ ' f -120~1y ' ~ � ~1~ 6 ~ . y . : ~ Zen,s"l~ � . Z s~Zt~ , r d ' ` X,lo'AI ' 1 2 d y S : Figure 3.15. Attenuation introduced by the.lead as a function of the point of its inclusion for a bimetal line Key: l. ~al~d, decibels 2. kilohertz 3. lead 4. wave When calculating the attenuations of the high frequency chanr.els it 3s sufficient to begin with the greatest attenuation of one of the carrier frequencies of 78 or 120 kilohertz. The distortion of the attenuation increases on going away from the station and approaching the subscriber points. ~ The presented radiation pattern of the carrier frequencies for the three- . element network (Fig 3.16) clearly indicates the increase in the voltage tolerance of the carrier frequencies on approaching the subscriber point. 143 ; FOR OFFICIAL USE ONLY ~ ; i � APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-44850R000200044465-4 FOR OFFICIAL USE ONLY , : . f:(4) ' . .~6, : ' . $ , ' 9. . - . . i %l~ IWMaA ~ ~l! ; ~dKM~ i ~7 ~ ~ ~A~fh~~- ~ t ~cr'�~a am~ IGr ' DI~:~� ~ yn ~r } ( , ~ . . i ~ ~1) . i ~ i y ~ . - . _ � ~.i� . ~ " t ~ ~ - " ~ 0, (11) . . x ' . ~ , � . ~e i - � - . . . . . :(11 . " . ' , . . . . . : 16Y . ~ . . , . � . . , 1 � ~ � . , ( . _ . - . . : . , . . ~ ~ ~ ' . . � ' ~ . ' � ~I ! ' . - .,j/Q ~77C IV.3t Figure 3.16. Diagram of carrier voltages of high frequency channels for the three-level systems cot~sidering decay of high-frequency equipment and lines Key: 1. UPTV transmitter 2. Transmitter connection circuit 3. Main~ teeder line 4. Transformer substation 5. UTP . 6. Dist~: ibuting f eeder line 7. Subscriber transformer 8. Subscriber network 9. Subscriber rosette 10. UO rated�120 volts 11. volts ~ 144 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02108: CIA-RDP82-00850R000200040065-4 1 FOR OFFICIAL USE ONLY CHAPTER 4. TRANSM7.TTERS ANA REPEATERS 4.1. General Information ' ~ The transmitter of the TPB system is a set of two transmitters of AM signals with carrier frequencies of 78 and 120 kilohertz designed to transmit two broadcast ~:rograms by frequency multiplexing of the WB network. Thus, in contrast to the radio broadcast transmitters operating on the emitting antenna, the transmitters of the TPB system are loaded on the WB line, the emission of which must be reduced to a minimum. The tiransmitters investi- - gated later are designed for use in the systems for building the station part of the channel in which the conversion of the low-frequency signal to the AM signal and obta3;ning the required power of the high-frequency signals at the input of the TPB network is concentrated at one station site (Fig 2.8, 2.10 and 2.12). A significant characteristic of the transmitters of the TPB system, in - contrast ta the radio broadcast transmitters of AM signals is regulation of the carrier voltage with respect to the corresponding law with variation of the broadcast signal level. The introduction of the indicated regulation - leads to variation of the functional diagram of the transmitters. The dis- tinction of the radio broadcast transmitters of AM signals is the introduction of the frequency characteristic correction of the modulating frequencies (raising it in the frequency range of 3000 to 6000 herez). At the present time the UPTV-60 and UPTV-200 transmitters have been developed. On the basis of the UPTV-200 transmitter, by increasing the output power of the terminal stage, a transmitter UPTV-400 has been built. The rated output powers of each transmitter af these transmitting installations on the carrier frequency are 60, 200 and 400 watts respe~tively. The quality indexes of the indicated transmitters are determined from the condition of obtaining quality indexes of the entire through channel which are close to class II of All-Union State Standard 11515-65. At the present time the PTPV-400 transmitter for channels of quality class I with output power of 400 watts and the transmitter ` based on transistors for the rural TPB system with an output power of 40 watts have been developed. . 145 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4 FOR OFFICIAL USE ~JNLY The indicated transmitters contain the basic devices for the shaping and the amplification of the AM signal and also the feed sources, the devices for monitoring, automation, control and protection. The structural diagrarns of the UPTV-200 and the UPTV-400 tranemitters are - identical and they diff er from the diagrams of the UPTV-60 transmitters by the feed sources, the monitoring, automation and protection devices. The functional diagrams of the basic channel for shaping and amplifying the AM signal of all the indicated transmitters are identical; moreov~er, the trans- mitters of each carri~r fre~uency of one type of transmitter are distinguished only by the e~.ectrical data of the elements of the resonance circuits in the high-frequency signal transmission channel. Let us consider the functional diagram of the channel for shaping and amplify- " ing the AM signal of the indicated transmitters (Fig 4.1). The system contains _ the amplifica.tion channel for the input low-frequency signal ~low-frequency repeater), the high-frequency channel made up of the carrier frequency master oscillator (ZG~, the adjustable carrier frequency repeater, the modulator (M) and the modulated oscillation repeater (Z3MK) and also the chann,el for ' shaping the control signal (regulating device). Thus, in contrast to Lhe radio broadcast AM transmitters, the given transmitters do not contain the ' frequency multiplier, powerful modulator for modulation of the output stage; - the modulatian and regulation of the carrier level are performed in the _ circuits with low signal levels. ` . ~ -'--(4 Cutnan 6 ~ 10 (11 12 (13) BXb'D~ ~ic�numtna M ta~"� yM/f Bux~e y y d! Ner.yr~~r,~. .I/V tueyQ ~2) � mat, vnr,mumd~ f.na� I7MC~tN?~! ~ (1) 3 ~5) oeiyn Nyt,uv,. Pca nu~iy : niu� Ho~ ~ua p~cyyt MYCYtNd4 . . rocrl~~ (9) , ' . _ ~ ~ - . ~ . . . , . , _ � N~movarrt~ ~14) � , , - . - ~ - numeyua - - . � � Figure 4.1. Functional diagram of the shaping and amplification of the AM signal of the TPB transmitters Key: 1. Low-frequency signal input 8. Signal with regulatable carrier 2. Low-frequency repeater 9. Low-frequency signal 3. ReguYator 10. Modulator 4. ZG master oscillator 11. AM signal 5. Carrier frequency signal 12. Modulated oscillation repeater [UMK] 6. Carrier frequency repeater 13. AM signal output 7. Control signal 14. Power supply - 146 9 FOR OFFICIAY,, USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 ~ � FOR OFFICIAL USE ONLY - The operating principle of the given system consists in the following. The - carrier frequency obtained in the master oscillator goes to the controlled high-frequency repeater and the control signal shaped in the regulator and corresponding envelope of the modulating signal (broadcast signal) go - together with it to the repeater. Under the effect of the control signal the gain of the controlled high-frequency repeater changes, which leads to _ the adjustment of the carrier frequency level by the law of the envelope of the modulating signal, that is, to primary modulation in practice not noticeable when heard. Then, in the modulator, under the effect of the low- frequency signal coming from the output of the lo~,rfrequency repeater, _ secondary, basic amplitude modulation of the carrier takes place, as a result of which the informatio.n of the broadcast signal is transmitted. The AM signal shaped in this way is amplif ied by the stages of the modulated oscilla- tion repeater. This structure of the functional diagram of the basic channel for which at the beginning total shaping of the AM signal with adjustable carrier is _ carried out and then amplification of it, is more expedient. The use of anode modulation in the terminal stage would ~equire the creation of ano~her powerful controllable rectifier in addition to the powerful 1ow-frequency amplifier of the modulator, which would cause significant diff iculties. With relatively low powers of the transmitters (on the order of hundreds of watts) - the energy advantages of the anode modulation cease to be decisive. In the i:ransmitters developed at the present time this principle of constructing - the basic channel is retained. All of the indicated transmitters have quartz stabilization of the carrier frequency of the master oscillator, which insures stable reception of the AM signals in the presence of f~xed tuning of the TPB receivers. With the exception of the diode modulator, all of the elements _ for amplif ication and conversion of the signals are executed from electron tubes, which imposes additiona.l requirements with reapECt to protection against high-voltage feed voltages. In the existing systems for construction of the station part of the high- frequency channel (Fig 2.12), the output power is determined by the received maximum voltage of the carrier frequency of 120 volts and the load resistance. For the ma.jority of cities the number of simultaneously connected main feeder lines does not exceed 5-6, and the power of 200 watts is suff icient. For a part of the reference repeater stations of such cities as Moscow and. ~ , Leningrad, with a large number of connected main feeder lines, a power of 200 watts turned out to be insuff icient, which also led to the necessity for increasing the output power to 400 watts. The most widespread is the UPTV-200 type transmitter; the UPTV-60 transmitter is in practice not wide- spread. At the same time, for the TPB systems of many small cities a power on the order of 40 watts is suff icient. - _ When calculating the energy indexes of the iJMK in the rated rsgime (the output power, the dispersion power, the voltage and current amplitude, and so on), in spite of the regulation of the carrier level, all of the relations , used for an ordinary AM signal are applicable. For the given maximum nor- malized modulation coefficient m=0.7, the calculation relations are as follows: 147 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY Maximum power. ~ - P~,~~ = P.~~~ m)~ ~ 2,9P.,~ (4.1) . Key: 1. max; 2. rated where Pg is the average carrier power in the absence of modulation for the signal with rate~ carrier voltage; The average power during the frequency period of the AM signal envelope Pz = Ps (1 .^.s 1,2~P,. . . . (4.~ 2~ . . The maximum voltage and current amglitudes of the ~1M signal are as follows: - UIIiKC~ - \i ~ m~ - 1 o7V ~ j ~ . . � . , � � , ~4.a7~ ~ I~ (1-}- m) = 1.?Is, : ~ ~ . � ~ (4.4) _ Key : 1. max where UH and IH are the rated voltage current amp~itudes of the carrier in the absence of modulation. For the transmitter with regulatable carrier when suppressing the carrier voltage in the interval by 10 times the output power in the interval , PH min 0.01 PH, which leads to reduction of the dispersion power under class B conditions. Thus, the presence of the regulatable carrier significantly reduces the average real dispersion power of the tubes and transistors when transmitting - the broadcast signal. The operating conditions for the rated output power of the carrier in the given case are maximal and correspond. to the maximum broadcast signal of it. The actual average carrier level is appreciably less ~ than rated foY the broadcast signal. This fact can be especially used to decrease the dimensions of the thermal leads of the modulated oscillation repeater transmitters. At t:~e present time the AM signal repeaters include only 'the two-channel intermediate repeater (DPU) installed on the distributing feeder lines to - insure the required high-frequency signal voltage aloag the entire length of the feeder liae (Fig 3.8). The.DPU [two-channel intermediate repeater] is made from transistors and is fed from the AC electric network. 4.2. Automatic Gain Control of the Carrier Frequency ~ In essence, with insignif icant variations in all three types of transmitters the same circuit is used to shape the controlling signal and the controlled carrier frequency repeater. Let us discuss the circuit for regulating the 148 . - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 P'UK Ur~r 1l:lAL U5~ UNLY carrler :in tl~e UP'rV-200 transmitter (and al;so in the UPTV-400) illustrated in Fig 4.2. The low-frequency signal volta~e from the output of the - tc~o-staga low-frequency amplifier goes through the cathode repeater in the tube L2b, the transformer 111, to the double halfperiod detector (in the tube 112, double diodes). In the RC-load of the detector (113-114), the envelope of the modulating signal is isolated. Then the voltage of the envelope is also filtered by the left diode of the tube 116 and transmitted to the RC-circuit (115, 117). The DC voltage which is opposite in polarity to the received erivelope voltage is introduced successively between the lower point of the circuit and the common point of the entire circuit through the 120 "carrier suppression" potentiometer. Both voltages are successively applied to the antidynatron grid of the pentode 50. The variation of the envelope voltage leads to variation of the bias voltage on the third grid, which also causes variation of the amplitication coefficient of this pentode. _ In Fig 4.3 the relation is presented for the relative variation of the carrier voltage as a function of the bias on the third grid E~g indicating the simple _ possibility of regulating the carrier by 20 decibels. The initial suppression of the carrier in the interval is established by the potentiometer 120 and according to Fig 4.3, consists in feeding the bias voltage on the order of 1.5 volts for suppression by 20 decibels. When feeding the rated input signal the negative bias is compensated by the positive voltage at the output of the circuit 115, 117, which leads to restoration of the rated carrier level. The right diode of tube 116 included in parallel to the third grid of the pentode, b~ocks it at positive potentials, which permits the formation of the required dependence of the carrier level on *he modulating signal level, that is, the extent of the upper section of the regulating curve with constant carrier voltage (Fig 2.40). The required low-frequency signal voltage a t the input of the controlling detector for creation of the given regulating curve is established by the "control signal" potentiometer 30. The buildup time of the controlling voltage of the RC circuit (115, 117) is basically determined by the output impedance of the cathode repeater on the L2b tube (34) by the transformation coefficient of the transformer 111, the internal impedances of the diodes of the tube 112 and the left diode of the tube 116 and also the capacitance of the capacitors 114, 115. This time correspondingly determines the buildup time of the carrier at the output of the tube 50. The steepness of the buildup of the carrier is determined only by the indicated elements in - the case where the steepness of the buildup of the modulating signal signifi- cantly exceeds the steepness of the charge of the capacitance 115. The decay time of the controlling voltage on the circuit 115, 117 is determined by the resistances 113, 117 and the capacitances 11G, 117. The decay time of the controlling voltage determines the decay time of the carrier. In the UPTV-200 and UPTV- 400 transmitters the buildup time of the carrier t~ a value of 0.9 U~ rated is on the order of 6 milliseconds, and the decay time of the carrier to ~7.2 U~ rated is approximately 200 milliseconds. For further increase in noise suppression in the interval of the modulating _ signal in 1967 another method of regulating the carrier frequency level was - pr.oposed in which the existing smooth regulation of the carrier is maintained within the limits of thP established dynamic range of the broadcast signal 149 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL 17SE ONLY . . � o , ~ . ~ ~ ~ ~ ~ ~ � ~ ~ � . ~ N ~ ~ -r------1i v ~ ~ ~ N . ~ + ~ r.srw-- ~ ~ ~ L) s i o~-~ ~ l ~ ' ~ '"a~'~`~~~ ~ ~ ~ . , ( oo ~ ~ } l:~ ` i ~ ~ i ~ i o � o~ I iii E~~~`~' y' iti ~ w en i' ~ ~ ~ N 't.._ i ~ ~ L- ~ ~ ~ I ~ ~ ' ~ o ~ 'a+ 1~~ ~~I � c�~ h ~ p, u 1~~~~ o o ~~~ii' ~ ~i ~ ~ ~ ~ . j ~ J ~ ~ ~ - 1 t. . ~ o~ 3-~d ~~T b ~a v ~ - - ~ ~ ~ A''a ~ ~ - - 1 L= ~ ~ a� ~ ~ , , T I ~ ; ~ - ~ ~ ~ ~ ~ ~ ii'~ ~ � ~ ~i---- z+. ~ ~ ~ ~ ~ ~ et~o es ~Q a~ ~ ~ o 1 t}~ ~ ~ ~is ~ a ,a ~ ~ w� N ~ ( N ~ ~ ; d , � ~ ~ ~ p. ~ ~ 5--~ ~ ~ - ?o ~ ~xJ ~ a ~ f^- ~ r - - ~ e~ ~ y . .roC ~ ~ ~ I ---N ^ " ~ a a~'i 1 ~ , Y ~iit n ~ e - ' ~ . ,c ,�-i ~ f . ..3-.. ..o. . ~ p 1~+ I J 1 1 I ~ ~ ~ ~ . 3�,(~ ~ ~ fi � 1 . . . O ~N ?~-I u ~ f~ r~ ~Y'ot ~ ~ d 9~ -==o I U I _ y _ ~ tE Ul I i r ~ ~ L 4 ~ ~ o~io 0~ u~ ; s; e~ C L v~ ~ a~.~ o u .v~.n ~ nnh ~ . ` an~wr ~ ~ ~ Hir,~ L.~._ ~ ~ b .~i ~ - . $ .1 ~x �~~v ~ ~ - J ~Z ,o yss ' e1 ' ~ ~ ~ ~ ' _ ~ ~ ~~n L ~ jq�v~ v' � cv o ~ w m 4 ~ ~ `~~i~,~~~ b a l � ,G ~ ~p ~ ~ ti � ~ ~ ~ ~ ~Y ~~-I Gal ~ C~" . ~ ~ �3~1 o v ~ ~ q ~ _ . _ ~ ~ ~ ~ ~ ~ ~0 ~ , L-' - - - - - - - --4 - - - ~ e w r+ ~ ~ . ~ . ~ . ' . . ~ . �w . ~ � ~ ~1 ~i ~ ~ _ 150 ~ a . FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 I FOR OFFICIAL USE ONLY . ~ ;p~~~ _ ~ ~ -18.. ZO _ JO , -+l0 ~ 30 F,.B -6 S J ? -1 ~'6~ Figure 4.3. Output level of the carrier frequency as a function of the bias voltage E~ 3 on the third grid o� the 6Zh2P tube of 40 decibels, and with the level below this range ~he carrier voltage is sharply suppressed by another 30-40 decibels, which on the whole makes it possible to obtain carrier suppression in the interval of 50--60 decibels (Fig 2.41). The schematic of the device for additional suppression oF the ~ carrier for the UPTV-200 transmitter was developed in 1969. The initial operating principle of the given device was investigated in Section 2.12 and illustrated in Fig 2.43. The schematic diagram of the device is illustrated in Fig 4.4.. The circuit elements which belong to the UPTV-200 transmitter are denoted anly by the numbers in accordance with Fig 4.2; the circuit elements of the device are designated in accordance with the type of element. - The device consists of a two-stage amplif ier-limiter based on the L1 tube (6N2P), a rectifier with respect to the voltage doubling circuit based on semiconductor diodes D1 and D2 (D226D), the parametric stabilizer Rg, Eg (D809), the DC amplifier based on the transistor T1 (MP37F~) and the switching _ diode D5 (D226D). The device operates as follows. The amplifier-limiter of the instantaneous values maintains the initial dynamic range of the broad- cast signal at 40 decibels to several decibels at the input of the rectif ier. � The parametric stabilizer reduces the limits of variation of the DC voltage still more, reducing in practice the entire dynamic range of the broadcast signal to one value of the ~C voltage on the D3 stabilitron. A voltage determined by the broadcast signal and the DC voltage~.on the resistor R11 are applied to the base of the transistor T1 in opposite polarity. In the presence of the broadcast signal, the voltage of inverse golaxity on the stabilitron D3 exceeds the voltage of direct polarity on the resistor R11 - as a result of which the transistor T1 is closed and the diode D5 does not shunt the carrier frequency at the input of the pentode 66. 151 . FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY . . _ . ~ . ' . . . , C' r~ - ~ F.~_-. o~ ~ ~ ' ~ ~ 11 e d . ~ ~ ~ - ,..i r. i w ~ ~ ~ ~ y e o . cs a? - o a+ . . ~ ~ : ~ - ~ ' ~ - a~i ~ ~ : ~ � . V QM ' ~ ~ ' ~ . ' . ~ ~ , ~ ~ ~ ~ . ~ , ' Q . . rl 1-~ ~ i. ~ ti~-1 a~ . , w ~ ~ V . ' ~1 ~ ~ W l~ a - v`� ' a? .n . ~ ~ x a~i ~L cs~' c~" ~t~' 'd . Gl ~ ~ . u'1 ~p ~ 1~-~ G! . ' v ' � W N ; . . O ~--I - . m ~ t~J - ~ 7 " . ~ ,a a b d ' !M ~ w ~ b b ~ N ~ � ? v i ~ w ~ ,i A. . . ~ I t ~ J'1 - ~ ' ~ . ~ ~ . vi c~i ,~.i . ~ ~y ~ ~ . ' ' ~ ~ . ~ r~l H . . . ~ ~ ~ ~ ~ ~ ~ _ _ - v ~7 rl O ~ ~ , _ . . ~ O V O ~ ~ a > oo w _ ~ Y~ ~ e..~~_~ ~ ~o ~ ~ m ~ c~d ~ ~ � ~ 7 _ 4 N o F~*~ ??~~i ~~H + . . a e . . . � - � ~ ~-i N N1 ~t u1 � ~ ~ " - ~ � ~ . . . . . x 152 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 In the broadcast transmission interval the voltage on the stabilitron D3 decreases sharply, and the transistor opens under the effect of the direct voltage, which causes transmission of the current through the diode D5 and ln prrictlce Kliort. citcuiting of thc input of the tube 66 with r~apect to the carrier frequency. The device can be placed in the UPTV-200 master oscillator unit, and all of the feed voltages are taken from its circuitry. The obtained total - suppression of the carrier in the interval was 65-68 decibels; for the - switching zone (Fig 2.42) it was 2-3 decibels. The performed operating tesCs _ of the device in the MGRS [Moscow City Radio Wire Broadcasting Network] over a period of several months in 1970 demonstrated its reliable operation and absence of ac'ditional distortions of the AM signals. 4.3. UPTV-200 and UPTV-400 Transmitters General Information The UPTv-200 and UPZ~1-400 transmitters have to a great extent similar structural diagrams and structural executions. The UPTV-200 transmitter was developed by the Scientific Research Institute for Radio of the Ministry of Communications in 1962, and at the present time it is basic [16]. The UPTV-400 transmitter was built at the MGRS in 1963 on the basis of the UPTV-200 by increasing the output power of the terminal - stage to 400 watts. The UPTV-200 and UPTV-400 transmitters have the following ~asic electrical characteristics: 1. Carrier frequencies of 78 and 120 kilohertz. 2. Amplitude modulation. Rated modulation coefficient of 70�6. 3. Regulation of the carrier level of 20 decibels. 4. Rated carrier voltage of 120 volts. 5. Rated load resistance for the UPTV-200 transmitter of 72 ohms and for the UPTV- 400 transmitter of 36 ohms. - 6. Rated frequency band of 50-6000 hertz. 7. Admissible nonuniformity of the frequency characteristic within the limits of the frequency band to 3 kilohertz is 2 decibels. On a frequency of 6 kilohertz the increase in the frequency characteristic reaches +4 decibels. _ 8. The harmonic coefficient with respect to the envelope for the rated modulation level in the frequency band of 200-4000 hertz is no more than 2.5%, and i:~ the 100-200 hertz band no more than 4%. ~ 153 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY 9. The eignal/background ratio on frequencies of SO and 100 hertz is no less than 60 decibele. 10. The rated input signal level for the broadcast transmission is 0 decibels (0.775 volts). The functional diagra:n o� the channel for sha.ping aad amplifying the AM signal is presented in Fig 4.1 and it is investigated in Section 4.1. Let us co~ sider the structural diagram of the transmitters in accordance with their _ structural execution (Fig 4.5). . Nr n~N~A~ ~ ~ na~~n K~uH~ Ir~d ,~r ~2~ llMlt3 rn ~4~ . (1~ _ ~ _ r l1QHGl1~~5 /1aKeni~6 /layra(7) . . . ~ . n~rmoyas a,u?epr,~~r~ a~ryemuyec ~ ?60~SS08 t0 ~roNmpcn . . $ 9 ' . . . /laxend /Icacn~ 1lq,~lr ~10) . ~ . cmosunoraa numnyua . a Nanpastis- a6ooB . � ~ � : NUA ZZC � . . ~ . s=~~' ~ ~ . . ~ � . . . ' _ . ti . . , . ~,~06(11) ~ . ' ' _ . : ~ ~ � Figure 4.5. ~tructural diagram of the UPTV-200 and UPTV-400 transmitters in the panel execution Key: - 1. Low-frequency input 7. Acoustic monitoring panel - 2. Master oscillator panel 8. Voltage stabilizer ~220 volt 3. Modulating oscillation repeater panel panel 9. 2600 volt feed panel 4. To the TPB lines 10. To the modu~ating oacillation 5. 260/550 volt shade panel repea~er - 6. Measurement panel 11. ,.220 volts The atructural diagram of each transmitter consists of seven panels: the modulating oscillation repeater panel (i,TrIIC); the master oscillator panel _ (ZG); the measuring panel; the acoustic monitor panel; the 260/550 volt feed ~ pauel; the 2600 volt feed panel; the voltage stabilizer panel. - The ZG and the iT1~IIZ panels are the channel for shaping and amplifyiag the AM signal. The remaining panels perform the functions of ineasurement, monitoring and feed of the basic channel for shaping and amplifying the AM signal. 154 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 ' FOR OFFICIAL USE ONLY , ZG and UrIIC Panels The total schematic diagram of the master oscillator and modulated oscillation repeater panels ~f the UPTV-200 transmitter is presented in Fig 4.2. The - low-frequency input signal goes through the level control (PY) 4, the transformer 8, the "demodulation control" 11 to the two-stage low-frequency amplifier executed from a double triode 15 (6M3P). The left triode of this tube is included by the circuit with common cathode, and the right triode, by the cathode repeater circuit. _ The control 4 is used to set the rated (0) low-frequency level in the I wind- ing of the input transformer 8. The regulator 11 is used to set the rated depth of modulation. In order to improve the noiseproofness of the AM signals with respect to the low-frequency signals of program I, an increase in the frequency characteristic in the u~per moduiating frequency range is formed in the low-frequency amplifier by introducing frequency-dependent current feedback realized by a series circuit of elements 18, 23 and 20. The given circuit has resonance on approximately a frequency of 8 kilohertz. On fre- quencies about 2 kilohertz the depth of the current feedb~ck decreases, as a result of which an increase in the upper modulating frequencies is cre~ted. Remodulatior. does norc occur on the upper frequencies as a result of diminished level of these frequencies inti~e broadcast signal spectrum. In the receivers the given 3ncrease is compensated by the corresponding trough. From the low-frequency amplifier output the total level of the loT,~-frequency signal is fed to the diode modulator, and Fart of the low-frequency signal from the "controlling signal" regulator (30) is fed to the cathode repeater based on the L2 tube (34). The shaping of the control signal by the elements 112-117, _ 120 and the gain control of the tu~be 50 are investigated in Section 4.2. The - generation of the carrier frequency is carried out on the L2 triode of the - 6M3P tube (34). The generatiQn frequency is stabilized by a vacuum quartz operating by the parallel resonance scheme. - Part of the carrier voltage is picked up from the anode circuit 33, 38, 40 of the master oscillator and is fed through the capacitor 41 to the first grid of the pentode 50. For stabilization of the operating conditions of ~ the master oscillator and the contxolled high-frequency amplif ier the feed voltage of their anode circuits is stabilized by the SG1P stabilitron (37). From the anode circuit of the pentode 50 the carrier voltage is transformed by means uf the high-frequency transformer 54 to the diode modulation _ circuit. Thus, the diode 55 (D2Zh) is iinder the effect of two successfully applied - carrier voltages and the low-frequency signal, which leads to obtaining the AM signal in the circuit made up of the inductance 57 and the capacitor 61. - The modulation is realized by varying the cutoff angle of the carrier frequency current in the diode circuit. The cutoff angle always remains normal, as a result of which proportionality is retained between the ampli- tude of the modulating low-frequency signal and the amplitude of the f irst - harmonic of the carrier on the circuit 57, 61. 155 _ FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY , This modulator corresponds well to the requirement of independence of the amplitude of the envelope of the modulated oacillation with respect to the amplitude of the carr ier required when using the carrier with regulatable level. In addition, the diode modu:~ation insures very small nonlinear dis- tortions even with a reduction in ehe carrier level while maintaining th~ deep modulation. In order to suppress the carrier frequency harmonics, the AM signal is fed from the circuit 57, 61 through the low-frequency filter 63; 62 to the input of the first stage of the modulated oscillation amplif ier based on the 6P15P tube (66). In order to establish the required output voltage of the transmitter, the "high-frequency level" regulator is used (64) at the input of the tube 66. The amplifier based on the 6P15P pentode operates in the class A regime. Then the AM signal goes through the sy~etric transformer 74 tuned to the high-frequencies to the preterminal double-cyc~e stage based on the 6P15P tubes (80, 83) operating as the voltage amplifier in the class A regimE. The cathode circuits of all the 6P15P tubes (66, 80, 83) include the resistances 70, 84, 85 for measuring the currents of these tubes. The diff erential relay 93 is included in the anode circuit of the preterminal stage. The preterminal stage is connected to the terminal stage by means of the _ high-frequency transformer 96, two secondary windings of which form parallel ~ - ` circuits with the capacitors 97, 98. The output stage of the UMIC [modulated oscillation amplifiexJ located on the UMIC panel is ezecuted in accordance _ with the doub].e-cycle circuit based on the GU-~1 tubes (11, 28, the number ~ - of the circuit elements of the UrIIC panel is separate). The GU-81 tubes operate in the AB class regime without grid currents. The output transformer 37 is executed from a torus made up of four Alsi~er halfrings type VChK-22 (outside diameter 75 mm). It is necessary to note that the high voltage transformer executed from the torus of relatively;small diameter requires careful manufacture from the point of view of the electrotechnical characteristics of the insulating materials of the inserts and the winding wires. The primary winding of the output transformer is tuned to resonance on the carrier frequency by the capacitors 38 and 43. In order to exclude the mutual effect of the transmitters on successive inclusion of them, two ` secondary windings of the output transformer are created. The series circuit (39, 41, 50, 51) tuned to the carrier frequency of the adjacent transmitter is included in parallel to each winding. This makes it possible in practice - to exclude the power losses of this transmitter. The terminal and the pre- terminal stages of the UNIK are encompassed by negative feedback with respect to voltage with depth on the order of 18 decibels, which insures sufficiently small output impedance of the transmitter (on the order of 7 ohms) and an increase in voltage on dropping the load of no more than 1 decibel. The negative feedback is f ed from the dividers 6, 7 and 31, 32 of the UMK panel to the first grids of the 6P15P tubes (80, 83) in series through the - secondary circuits of the transformer 74. The required bias voltage of the terminal tubes is estatlished by the potentiometer 4 led to the face of the ~ UrIIC panel. In order to decrease the voltage variation of the anode feed - of +2600 volts, a ballast resistance (45-49) is included in parallel to the power supply. For monitorin~ the constant components of the anode currents 156 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY of the GU-81 tubes, their cathode�eircuits include milliammeters 16 and 22 and a differential relay 14. In order to monitor the low-frequency and high-frequency voltages in the master oscillator and modulated oscillation amplifier panels [ZG and LTrIIC panels] there are control plugs. In the plugs 6 and 31 of the ZG panel, the low~frequency voltagea are monitored; in the plug 100 of the same panel, the high-frequency voltage i.s monitored. In the plug 44 of the iTrIIC panel the output carrier voltage is monitored. The filament feed of all tubes of the ZG and U1~IIZ panels is realized from special filament voltage transformers installed on these panels. The stabYlized voltage of 220 volts is fed to the filament transformer of the ZG panel. The UPTV-400 transmitters are distinguished with respect to the IJNII~ only by the schematic and structural execution of this panel. The f inal stage of the UMK is made in accordance with the two-cycle circuit of 4 type GU-81 tubes (two tubes in each arm) operating in the class B regime. The characteristic feature is the execution of the output high-frequency trans- former. The transformer is executed from an armored core of eight pairs of unitized II-type ferrite cores type F-600, which makes it possible to decrease the transf~rmer dimensions and losses in the core. The variation of the m~gnetic induction from 450 to 50 gauss causes variation of the resonance frequency of the output circuit in the primary winding of the transformer from 120 to 121 kilohertz, which is admissible with low Q-factor of the circuit (Q=5). The output circuit is tuned by varying the air gap of the - transformer, to prevent overheating the magnetic induction in its core must not exceed 450 gauss. The calculated gap is 5 mm. The output resistance of the transmitter is 4 ohms, and the variation of the output voltage when dropping the load does not exceed 1.2 decibels. _ Measuring Panel The measuring panel is designed ~o measure all of the DC feed voltages, the currents of the individual tubes of the ZG panel, the AC network voltage and also for visual monitoring of the AM signal. For measurements of the voltages and currents, one indicating instrument is used which measures the current of the 6P15P tube (66) of the ZG panel, the currents of the 6P15P tubes (80 and 83) of the ZG panel (each tube - individually and their total current); the voltage of the 220 volt AC network, the anode voltage of +2600 volts of the UMK panel, the grid voltage of the tubes of +550 volts of the UMK panel, the bias voltage of the tubes of -170 volts of the ITMK panel, the bias voltage of -23 volts for suppression - of the carrier in the ZG panel, and the anode voltage of +260 volts of the tubes of the ZG panel for various positions of the measurement switch. 157 ' FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02108: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY Visual monitoring is realized by the oscillograph using the SL038 tube. . With a suff icient degree of accuracy for practice with respect to the tube grid divisions it ia possible to determine the modulation coefficient _ and the dept~ of control of the carrier and also to estimate the maximum depth of modulation in time of a real transmission. The monitoring AM signal is fed to the tube from the output of the band filter of the acoustic monitar- ing panel. The feed of the anode circuits of the tubes in the tube of the measuring pa}~el is provided from the +550 volt power supply. Acoustic Monitoring Panel The acoustic monitoring panel monitors the fitness of the basic channel by means of the "input-output" comparison circuit, acoustic monitoring, the � creation of a bias voltage of -170 and -23 volts. The "input-output" circuit compares the envelopes of the low-frequency signals at the input and output of the transmitter. For this purpose the output voltage of the AM signal is detected initially for isolation of the low-�requency signal, and then the low-frequency signal obtained is detected for isolation of the envelope of the low-frequency signal. The low-frequency input signal is deteeted once for isolation of its envelope. The voltages obtained f or the envelope of the low-frequency signal are f ed to the individual windings of the polarized relay which responds and attenuates an emergency signal for the relative variation of input and output levels of the transmitter of +5 decibels. The polarized relay used with f ixed extreme positions permits an emergency signal to be obtained even at trans- mi~sion peak. In order to return the relay armature to the initial position, a separate.button is used. For acoustic monitoring, a low-frequency signal is used which is obtained after detection of the AM signal for the "input-output" circuit. As the sound reproducing device, the dynamic 1GD-18 speaker i3 used with an intake power of 250 milliwatts. Its volume control is realized by a step regulator with constant input impedance. The low-frequency signal obtained after detection of the AM signal is also used to f eed the re*_urn munitoring to the TsUS with a voltage of 5.5 volts. This low-frequency signal voltage is picked up from a separate winding of the transformer. The bias rectifier with a voltage of -170 volts is made by the bridge system from the D7Zh type diodes. In order to smooth the pulsations, the LC-filter is used. Part of the voltage equal to -23 volts stabilized by two reference diodes of the D811 type is fed to the ZG panel for creation of the initial bias on the 6Zh2P regulatable pentode and to the "input-output" circuit for feeding the transistorized repeater. By means of another divider, a voltage of -48 volts is selected for feeding the emergency bell and two relays in the 260/550 volt f eed panel. 158 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4 FOR OFFICIAL USE ONLY 260/SSO Volt Feed Panel The 260/550 volt f eed panel is designed for crea.ting a feed voltage of +260 - volts of the anode circuits of the ZG panel tubes and a feed voltage of +550 volts of the second grid of the tubes of the modulated oscillation repeater panel and also the tubes and the electron-beam tube of the measuring panel. Two rectif iers with voltages of +260 and +550 volts are placed on the panel. _ The f eed rectifier at +260 volts is executed by the grid circuit from D7Zh type diodes, two diodes in each arm For ~iltration of the pulsations the LC-f ilter is used. A d ivider is connected to the f ilter output from which a voltage of +4 volts is picked up for the emergency relay contacts. The rectifier with a voltage of +550 volts feeds the second grids of the - GU-81 tubes and the measuring panel tubes. The rectifier circuit is a bridge circuit made of D7Zh type diodes, three diodes in each arm. The output of the rectif ier has the LC-f ilter connected to it which is loaded on an additional ballast resistance of 20 kilohms. A rectifier of +550 volts is f ed from the ferroresonance stabilizer. The toggle switch for switching on the transmitter and the switch for the type of control of the transmitter "local-remote," are taken out to the face of the panel. - ~600 Volt Feed Panel The anode feed rectifier of the GU-81 tubes is designed for an intake current ~ of 0.5 amps, and it is made by the bridge circuit from silicon diodes of the D205 type included in series, 12 each in an arm. The rectifier operates from the LC-fil~er. In order to improve the stabilization of the rectified voltage, a ballast resistance located on the modulated oscillation repeater panel , which consumes a current of 90 milliamps is included in parallel to the load. A rectifier of +'L600 volts of the UPTV-200 transmitters has significance differ- ences. It is made Y,y the six-phase Larionov circuit from 54 D205 type silicon diodes, nine in each arm. In the presenee of a th~ee-phase electric net~rork at the station the application of this rectifier circuit is the most expedient. The multiphase rectifier circuit insures low output impedance and the necessity drops out for a ballast resistance. The execution of the smoothing filter is simplified, the rectifier efficienc y is incrPases with the same rectified power. The rectifier is designed for maximum intake current of 1.2 amps, the actual current in the maximum power regime does not exceed 0.6 amps, ~*hich makes it possible to get along without the radiators to the diodes. Voltage Stabilizing Panel In this panel there is a 200-watt ferroresonance stabilizer of the SN-200 ~ type which feeds the +550 volt rectifier and the filament transformer of the ZG panel. 159 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4 FOR OFFICIAL USE ONLY Control, Monitoring and Protection Tlie UPTV-200 and UPTV-400 tranamittera are designed for local and remote control. ~or remote cantrol, protection and monitoring of the transmitters, automation elements are introduced into the circuitry of each tranamitter. - The automation circuitry permits us to switch the transmitters on and off, receive signa~s about the execution of the com~ands, realize m~~nitoring of the operation of the transmitter and perform some protective functions. The control of the set of transmitters can be realized either with the help of a free panel of the UPI servounit (from the remote control ~~et for the WP-1 or UUP-2 amplifier substations) or direct current over the connecting line for f eeding t1~e programs over the circuit made up of the "two wires to ground" using t~e WA-1 panel. The f ilament feed and anode voltages are connected _ to the UMK [modulated oscillation repeater] panel and the measuxing panel separately in time. On response of the first servorelay the feed voltage is f ed to the bias rectifier; ~lie anode recrifier of +260 volts, the ferro- ' resonance stabilizer and the win3ing of the delayed relay which with a delay of 18 seconds feeds a 1ow-frequency voltage from the input of the ZG panel to _ the "input-output" circuit. This delay is suff icient to exclude the false response of the "input-output" circuit on random inclusion of the transmitter _ with the previously fed modulating signai. The inclusion of the anode rectifier of +2600 volts and tiie recti.fier of +550 volts is accomplished with a delay of 2 seconds; after inclusion of the bias rectifier this delay is realized by the relays included in the bias rectif ier circuit. The automation system which realizes the monitoring of the correctness of = operation of the transmitter includes the "input-output" com~arison circuit which g~nerates the emergency signal with relative noncorrespondence of the - input and output levels at +5 decibels. The polarized relay used in the system receives emergency signals from all of the protective relays, includ- _ ing the differential relays installed in the two-cycle stages of the modulated oscillation amplifier. In the transmitters there are soun.d and light signals - abaut emergencies and failures. The sound signals usual~.y bell in case of - lo~al control for all emergencies recorded by the polarized .alay of the - acoustic monitoring panel, and the light signal indicates the presence of feed voltages on the corresponding panels and also burning of the fuses in the AC feed circuits of the +2600, +550 and +260 volt rectifiers. When - opening up the rear doors of the transmitter the blocking picks up the high ~ - voltage feed voltages and dischar~es the capacitors of the +2600 valt recti- f ier. The connection of the feed voltage of the electric network, the low-frequencq _ _ signal, the remote control and monitori:ng devices and picking up high-frequency voltages are accomplished by means of the term.inals installed on one plate ~ - of the inputs located below the transmitter, on the rear side. - 160 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY 4.4. UPTV-60` Transmitter The UPTV-60 transmitter was developed in 1960, and it is the first type of tYan smitter used in the adopted TPB system. The functional diagram of the channel for shaping and amplifying the AM signal is the same as for the UPTV-200 and UPTV-400 transmitters and it was investigated in .Section 4.1. Structurally each transmitter will contain four panels of the modulated oscillation repeaters, the ZG panel, the anode rectifier panel, the bias rectifier panel ~..nd the voltage regulator. - The functional diagram of the master oscillator panel is the sa~e as the - UPTV-200 transmitter. Moreover, the schematic diagram of this panel differs insignificantly from the ZG panel in the UPTV-200 transmitter. In contrast to the UPTV-200 and tYie UPTV-400 transmitters, the output power of the UPTV-60 transmitter is created by tbur UrIIC, 15 watts each. The output of each amplif ier is designed for connection of one main feeder line for a distributing f eeder line when providing a carrier frequency voltage at t:ne input of the 95-volt line. _ 'The output carrier voltage is set by the high-frequeney level regulator ~ included at the input of the f irst stage of the modulating oscillatiort repeater. For monitoring the output voltage of the carrier, an electronic - display based on the 6Ye5S type tube is used. The dark section of the display , is closed for values of Uout=90 volts and m=70%. A toggle switch permitting the feed of ths individual module of the UMK to be disconnected is led out to the face panel of the UMK panel. The acoustic monitoring panel contains a dynamic speaker and receiver. ,The - output transformer of the low-frequency repeater of the receiv.er has a separate winding for connection to the reverse monitoring line. The input of the monitoring receiver can be connected to the output of any af the four UNIK modules with the help of a switch. '1'he modular construction of the transmitters during operation of each module on a separate load complicates obtaining the inverse acoustic monitoring in the case of remote control of the transmitter, for transmission of the ~ instructions to switch the return monitoring line to each module or the four return monitoring lines is required. In order to overcome thi5 deficiency it is possible to use addition of the powers of the individual modules on a common load. Comparatively low carrier frequencies, a conttnon master oscillator, a wide UNIIC transmission band and short lengths of the mounting wires create the possibility of strict cophasal addition of the output signal without power losses. For low resistance of the UMIC outputs, series inclusio:~ of them is possible (Fig 4.6). 161 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY � y,~flf ( ~ ~ MK ~ .~2~ yMll K ~eF~~ (3) Figure 4. 6. Schematic of the power addition of the tJl~ in the UPTV-60 _ Key: 1. UNII~ [modulated oscillation repeater] 2. to the load - 3. Master oscillator With this circuit diagram the unavoidable differences in the output voltages and the distances do not cause additional power losses. In order to insure ` rated output voltage of 95 volts, a lead from the quarter of the turns of the _ secondary winc~ing is used. Here the output resistance of each UI~IIC module decreases approximately to 4 ohms. It is possible to connect up to 8 feeder lines with an output voltage of no less than 75 volts to the common output of the transmitter with addition of the iTMK powers. - The el~ctrical characteristics of the UPTV-60 transmitter, with the exception of the output power, basically are the same as the UPTV-200 transmitter. 4.5. Connection of the Transmitters to the TPB Circuit General Information The investigated TPB transmitters are designed for installation of a centralized network at the stations and alsu at the ref~erence repeater stations (OUS), the repeater substations (UP) and the substation blocks (BP) for the de- centralized network. In accordance with this definition, the transmitters must have the possibility of the connection to the three-elPment, the two- element and mixed WB circuits. Let us consider the circuitry for connectin~ r,he transmitters to the TPB network. Connection to the Main Feeder Lines The connectior~ of the UPTV-200 and the UPTV-400 transmitters ~o the main fee~ier lines is made through the devices for connecting r_he UPi'-1 trans- mitters (Fig 4.7) which are symmetric high-frequency transformers with tra~s- formation coeff icient of n=1:1 and tuned in the primary windirig circuit to carrier frequencies of 78 and 120 kilohertz. The secondary windings of the high-frequency transformer of the transmitter connecting circuit are 162 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY connected to each other through two series circuits tuned to the carrier frequencies. The two secondary windings taken from each output transformer of the two transmitters and included in series form the ~oint output of the two trans- mitters to which several main feeder linea are connected through their own UPP-1 [transmitter connecting circuits). The secondary windings of the two transmitters are connected to each other in the sequence such that the currents from the ad~acent transmitter will flow in the secondary windings - of one output transformer in opposite phase. The total load resistance connected to the two UPTV-200 outputs must be no less than 72 ohms and no less than 36 ohms for the UPTV-400. Here it is necessary insofar as possible to distribute equally the load resistance between the two outputs of the trans- mitters in order to de~crease the mutual effect of the transmitters. The UPP-1 are installed in the output commutation phase (SVK) and they are = - connected between the II winding;of the step-up meter tr~nsformer and the linear protection elements (fuses and lightning arrestors). When connecting the transmitters to the main f eeder .lines having cable insert with the input with a capacity to 5600 picofarads i3entical for frequencies of 78 and 120 kilohertz it is necessary to decrease the capacitance C3, achieving tuning of the L1C3 circuit to a frequency of 120 kilohertz consider- _ {.ng the input capacitance of the cable insert. With a capacitance of the _ cable insert of 5600 picofarads the capacitor C3 is com~letely disconnected. _ The tuning of the L1C3C6 circuit to a frequency of 78 kilohertz is not r.equired, for its tut_ing is maintained on connection of the capacitance C6=7500 pico- farads to the invariant total capacitance of the c.apacitor C3 and the cable - insert. With different input capacitance of the f eeder line for fr~quencies of 78 and 120 kilohertz it is necessary to tune separately for each carrier frequency. Initially, the tuning to a frequency of 120 kilohertz takes place by variation of the capacitance C3, and then, the tuning to a frequency of 78 kilohertz, by selection of the capacitance C6. Connection to the Distributing Feeder Lines For connection of the transmitters to the distributing feeder lines, two versions can be used. In the f irst version, the distributing feeder.lines are conneeted through the common UPP-3 device analogous to the UPP-1 device , (Fig 4.7), but having a transformation coefficient of n=3.16:1 and correspond- ingly altered values of the elements of the secondary circuit L2, L3, L4,. C1 and C2. The input impedance of all the feeder lines must be no less than 60 ohms (approximately 10 distributing feeder lines) on carrier frequencies of 78 and 120 kilohertz. The output voltage of the carrier frequencies on a common bus of the distributing feeder will be on the order of 30-40 volts. The tuning of the UPP-3 to carrier frequency of 78 und 120 kilohertz will be carried out analogously to the tuning of the UPP-1. Here the limiting magnitude of the input capacitance of all the feedex� lines must not exceed 56a0 picofarads. 163 FOR OFFICI~,L USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY . ~OZ~nn-J , ;Tqar~a~ P~ g~ , lni~ . (1~ , i T ~ ` ~ , ~(1~) - - / T~ . ,rv-t4,' ~ ~ 14 ~'3?c'~ ' I ~ : ' ~ L-' - . ~ r ~ ~ _ ~ � ~5~ - 4 ~ ~ . ~17 �rr-~ ~16) a,~,,~fi.~ro ~ = ~ ey;~,~-o r~ ( ~ j' � Np~ aiw.~zY ~ ' pj~ ~~~1~~ ~ 1 ~ � . . I8 - Z~OIiYf f14~ ' ( : . . \ ~ . ~ ~ ~ , . ~ ~+e~?~~?.r~n~ ~19> . _ ~ . . i� ~ _.�_DA~ 1 ~ , r. . . � � . . - eHr,~~o . . _(9) ~ ` . - : ' . ~ : . �e~i'�"ro"t~e ( Z ) ~ . . . . . ~ - Figure 4.1. Connection of the transmitters to the main and the distributing lines Key: 1. From the regeater I of the 11. Common bus of the distributing - low-frequency channel feeder 2. Transformer 12. Operation 3. UPP-1 13. Varistion 4. Main feeder 14. Limiter ~ 5. Transmitter for the II program 15. RF-10 distributing feeder 6. autput transformer 16. RF-1 distributing feeder 7. Transmitter of the III program 17. R1~ _ 8. I output 18. NRF 9. II output 19. Distributing feeder 10. UPP-3 transmitter connecting bay (STR) circuit In the second version in the absence of UPP-3, the connection of the transmitters to the distributing f eeder lines can be made by using elements of the structure for connecting the transformer substation (Fig 4.8). The feeder lines are connected to the transmitter through the bypass (OUTP) having the same transformation coeff icient as the UPP-3. Between the output of the low-frequency repeater and the common bus of the distributing feeder, blocking f ilters are included (ZFR). The compensation for the input capacitance of the feeder lines is accomplished in this case on inclusion of a seri~s circuit tuned to a frequency of 100 kilohertz parallel to the _ output of the low-frequen~y repeater to the terminals 5-6. In order to _ compensate for the capacitance of the lines it is necessary to decrease the capacitances in the parallel ZFR circuits, achieving tuning of them to frequencies of 78 and 120 kilohertz with input~capacitance of the lines. This tuning is accomplished with respect to the maximum transmission 164 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR UFFICIAL USE ONLY coefficient of the OUTP rahen feeding high-frequency signals to the OUTP through the series resistance R=600 ohms. 1~ _ . E9) . ' , ~ ~ .t~/~7 ~e mz.a P~ ~ e ~10). ' ' ~~~~taa:;r. ' . N ~ . . ~ l~ , . (Paf~raz , . . ~4, - ~:4-:~y,-- 1 ~ � mn-~ - - --=.:r ya~~. 13 . . . ~-r �(14) ~1~ ~~f~Q q , . ~2~ t~r a~'-P i r � A�~ Pa~amII ' - i j � NP? u.wtFtnGt 1 - ~ , (5) ~ 6 ~a~~rvuma~ 13 . ~ da rctuanQ ~ylp (6) , . ~ . ~u~~~ - ~rJ ~.Mdrvm.tsrsn ~�r~4+u~(L7)) ~ ~ - ~ (17) � . ' � ~ 1~..___J . , . : , ~ . i t . � ' ' , - _ ( 2 tur.mPV ~ , . , � . . . . : . l3~ ll~.z'~muc,v~y. - Figure 4.8. Connection of transmitters to the distributing feeder lines (Version II) Key: 1, Transmitter for program II 10. RF-10 distributing feeder 2. Output transformer 11. Operation 3. Transmitter for program III 12. Pieasurement 4. UPP-1 transmitter connection 13. Limiter circuit 14. RF'-1 distributing feeder 5. To the main or distribu.ting 15. Rlim - feeders 16. IRF 6. OUTP [Transformer substation 17. Distributing feeder bay bypass]. (STR) 7. ZFR 8. From the repeater I of the low-frequency channel - 9. Common bus of the distributing _ f eeders Connection of the Transmitters to the Mixed Circuit The con~ection of the transmitters to the mixed circuit made up of the main and distributing f eeder lines can be made by the circuits in Fig 4.7 and 4.8. For e~c~h type of wire network, its own version of connection of the trans- mitters is used. Here it is necessary that the total load resistance - reduced to the secondary windings of the output transformers of the trans- mitters be no le~s ::han the rated and it be distributed uniformly between two secondary winding;. In the presence of long distributing feeder lines 165 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 _ FOR OFFICIAL USE ONLY ; . - ~ : . ~ . � 'O - . . . . . ~ . . . ~ � 4s o m 1 ~ ~4 : I =n I ~c, _ ' y S~ s N' k~ '.1 z ~ ~ ~ ~ M` ~ ' ~ ~ ~ ~ t ~ ' ~s v~ ~ ~ b . 0 ^ ~ ~ t < ! . ''a ( ` b t~1~ 1 v ~ ~ .::,~~ly~ . ~ . ~ , I ~~a~o~~vo~ocaaqj ~ ~ ,^p tr~~V�,~N~VN`~~ti~~~0`aN , [ ' f i i - y - � , , . _ . . 1 ~ ~ ' ' � � ' ~ ~ f. ' . ' ~ . r ~ ' - . ~ ',~N~~.V VN~~`~~"`~~^'~~.:~�ao~ O � ~ i b` . . , . . ~ a ~ - . . - . . ~ - . ~ ~ I ~ ~ ~ - . ~ ~ 4 ~ , ~ n ~ ~ ~ ! ` , ` 1 ~ C ~ ~ N' C\~ ~ , b y ; p _ ~ H ; ' H a' - ~ ` 1 T . ~ - ~ ' ~ i~o. r~~ ~ ~ ~ ~ . . ~ 4 ~ ~ ~ ( ~ . ~ ~ ~ ~ ~ ~ v ;l:s. ~ ~ ~ - " ~ ~ ' ~ ' _ ~:g,~ ~ ao ~ ~ Qo~~~a.~a~o~oa~o v~~3:~ a a Q: b b �~Riey~~~.*.~.~~b~ ~ O~ r,~ ~C^�`~~Vry~wV4::~.~~.~o ~~V ' . . ~ ' . � . _ . ' � . . ~ . 4,". . . . , . . � ' - 166 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ~ 0 ~ ,i x ~ u : . . ~ - . . ~ ~ � . . . . ~ ~ ~ ~ ~ . ~ ~ ~ ~ ~ ; a ~ > . - �,r~ . y,Za I o ~ " ~ ~ ~ ~ - w ~ p �.�c.'. +.1 ~7~q' ~ A c ~ y C ~ v a ; N ' `b ~ ~ e? ! i:.,. ~ ~ . ~ . ~ 'r~? ~ . C N. b5 ~f.~t~ N ~ `r ~ i� ~k ~e i ( . v' ~ a r.~. ~ ' ~O~ f ~ ~ ?�1+ ^ ~ ~ -i~: f� j a ~ tv~~ � ~ -1 ^ ~ sr" I H O ~ _ ~ ~ ~ i ~ O a, ,~r.~,{ ~ v ; ( ~~~�V~jNy~~`'~~~~o~oa~V ~ ~ QO . C~ O r~ "p~~cr~:~. ~ r a ~,cp ~ ~ ~ ~ ~~N~Vnrv V~'~'~~ -V~N . ' o ~o j' u . - ~ ~ ' v e, ~ ~ ~ ~ . ~ . - - Q x i . � '_r ~w~^~.., ~ y~~.l M _ , ~�j ~lj ~ u'1 . ~ , a 4 ~i ~ w ~ ~ ~ , ~ ~ ai ~ ~3~ ~ ~ a~ ~ ~ ~ 1 V ~ i( ~ co a~ ~ k ' ~-'`r' - ~ a ~ r-I ~ ~ - ~'1'? d ' al r~ t~ y.~ c/~ ~ ? ~ ! ~ '1~ h ~ 'b � ^ '~J- ~ C ',C~~ . ~ ~~j'~ ' a C~l ~'I ~ b.` I - . 5. Gl W r-1 I ~C'_~'~~A 7 1~.i 00 C1 ~ ^ ~ y � N I I c.~ o c~n v I,~,r v� I ~ ; i ~ ~ ~ r "f:~ ~ ~i c~d ~ ~ Iq / ~ "f '"a.[ 1 I . ~ ~''''rj ~ � ~ ~ e`I ~ a`CC,t~t~t~'h :`1 ^1~Oa~0~'n1 v r~.t..`~ ,c 1 ~ r~l rl Ul 1~J ~ '~tV '~l 3 f ~ r ~ ~ ~ A ~rJ a~ ~ ~ t ~1 ~ � s ~ .-1 t/~ ' i+ ~~'c~~N~NNw~~~~`d'~*H ~ o~ ~ c~1 . ' : . _ . � ' ' . . ~T ~ ~ , - - � . . � , ; . � N . - " � ~ 1 I 00 � �rl r-I U1 fs+ ~ . ~ ~ 167 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 i FOR OFFICIAL USE ONLY with atteruation of more than 20 decibels, the UPP-2 can be used with ~r:ti~t~L~~rmuL.[on coc~fflclc:nt n~1.73:1 and ruteJ load resietnnce of 200 ohme. 4.6. Two-Channel Intermediate Repeater (DPU) The introduction of the TPB on the city networks demonstrated that there are cases where on satisfaction of the norms for attenuation of the first (low-frequency) channel, the requirement of insuring minimum admissible level for the high-frequency programs of channels II and III is not satisfied. ~ , This occurs on the distributing feeder lines having long leads and cable inserts, and with long length.s of the basic directio~. In these cases, in practice it is recommended that a distributing network be constructed, the load be redistributed.between the distributing feeder lines, the structure of the line be changed with a decrease in the number of leads, and their length. . However, tF:is procedure is not~always expedient because it is connected with construction operations. The increase in voltage at the input of such ' feeder lines also is inexpedient as a result of the energy expressions which disturb the effects during emergencies on the lines and overloads with - respect to the input for the receivers. A simpler solution can be the application of additional amplif ication of the high-frequency signals in the channel by installing the repeater and the distributing line circuit. For qualitative and quantitative estimation of the set of possible cases, let us use the previously calculated hypothetical versions of the lines distinguished by the load density S, the number of leads and the materials of the lines. The leads more than 300 meters long are taken into account. The f t Tio ~,s ~da o~~~ ' ~sos ~ Rsy~z~ ,7~ .~~r,s... nscs i ~ x~ Q6 , _ t � � � . � � : _~'_C+" _ . _ . Xo ~ : ~ ' ~ . ~ ' ~ . ~ . . . - Cae ~ . , intermediate repeater [DPxJ] 175 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY lT . . . . ~ . ' ~ ~ - .f0' ~ ZB 26 ~ ~v ~ 22 g Cm~~r~/~�~' (2) f6 ~um+ac Nop B~ N ~3) 1y ~ra6~np Ka (4) ~ 12 ~ - 6 ~ . . ~y B~ - 8~ - 2 . ,1 Z Z,B 3 � ~ Figure 4.12. Vo~coge diagram of the distributing line when using the DPU Key: - 1. Uf auxiliary 2. Steel-3; S, tr/km=5 3' ~max norm low--frequency 2� 6 kn' 4. Zinp ab tr-8 kilohms, N=2 couplers/km 4.7. Prospects for Improving Transmitters and Repeaters - The prospects for ~improving the transmitters and repeaters of the high- frequency channels of the TPB [triple-program wire broac~cast] system ~ consist in improving the quality and the operating indexes of these devices. The quality indexes of the transmitters and the repeaters can be improved to the norms required to insure quality class I of All-Union State Standard - 11515-65 of the entire through high-frequency channel. For this purpose gt the present time a transistar-tube transmitter has been - developed with an output power of 400 watts. In order to decrease the noticeability of the.nonlinear crosstalk from the low-frequency program in ~ the new transmitters it is proposed that the stati:c and time characteristics _ of the carrier frequency level control be varied with respect to the existing - control and that additional suppression oF the carrier frequency in the _ -broadcast transmission interval be used. The improvement of the quality and operating indexes of the transmitters and the repeaters is connected with rebuilding the station part of the high- frequency channels. When !nstalling the low-power AM signal shapers at the referer.ce repeat~er stations and the mqdulator oscillation repeaters at the transformer subetations (Fig 2.13), the problem of complete transistorization of the given d%vices is solved. Here the reliability of the head unit for _ shaping the AM signal at the reference repeater stations is improved signifi- cantly (the out~~ut power is decreased frc~. 200 and 4U0 watts to 1-2 watts), ~ ~ 176 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY the problems of satisfying the safety engineering requirements for the transmitters remain only for the electrical network voltages, for all of the anode voltagea of +2600 volts, +550 volts and +260 volts are excluded, and the f eed voltages do not exceed 70 volts. This improvement of t'~e quality - and operating indexes pertains to constructing t~he atation part of the channel with the installation of the transmitters at the central station and the repeaters of ti~e transformer substations (Fig 2.14). 177 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY CHAPTER 5. RECEIVERS 5.1. General Information Inasmuch as the transmission of additional programs is realized on high- frequency and low level, a device must be installed at the end of the line (at the subscriber) which converts and amplifies the signal. In the triple- - _ program wire broadcast system two versions of the receivers are used: individual, three-program loudspeakers (GT), and group, GPTV. In the first - version the high-frequency signals are fed to the subscriber rosette. In the second version, over the f eeder line to the group device which realizes separation, detection and amplification of them; from the output of the GPTV, the signals of each of the three programs are fed to the subscriber speakers over indepe~lent pairs with a level of 30 volts. The receivers are the ele- ment which determines successful introduction of system and must find demand among the population, that is, they must be cheap, they must have high reliability and good, varied external appearance. The application of the transistors insures increased reliability and simplicity of str.uctural design with low electric power intake. The technical specifications for the receivers are selected beginning with the given parameters of the TPB [three-program wire broadcast] system. The sensitivity of the GT is selected eQual to 250 millivolts. It is obtained as a result of a compromise between the requirements of maximum simplification of the GT and also exclusion of the eff ect of induatrial interf erence and interf erence from radio stations, on the one hand, and an effort to increase the range of the system and absence of interference with wireless reception, on the other hand. An imQortant index of the receivers is the input impedance (Rinp); inasmuch as thE :;T [tripl~e-program speakers] can be connected to the circuit in large - numbers, they constitute a signif icant load for the network RT [distribution points], and therefore their RinP must be high (on the order of se~reral kilohms). The power on a sound coil of the GT is selected equal to 150 - ^~illiwatts, which coxresponds approximately to the power with respect to the high-frequency channel. 178 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY The Eirst version of the GPTV-1 group receiver had a sensitivity of 300 millivolts. When putting it into operation at the end of the long feeder line the sensitivity did not insure stable reception of the high- frequency programs. Therefore it is necessary to connect the GPTV to the subscriber transformer through a bypass. In the GPTV-3 the sensitivity is increased to 100 millivolts. The output power of each high-frequency channel of the GPTV is selected equal to 25 watts by analogy with the power of the GT so as to retain the developed configuration of the distribution network. The excess power obtained as a result of low probability of connection of all subscribers for one auxiliary program or all speakers at full volume is useful as the reserve for the case of use of 2 to 3 points operating in the apartment by the subscribers. The GPTV input is connected in parallel to the subscriber network, the resistance of which at high frequency can vary from SO to 200 ohms. In order that this not influence the characteristics of the GPTV filters and, conseouency, the frequency characteristic, RinP is selected equal to 400 ohms. The technical specifications of the receivers are presented in Table 5.1. As is obvious from Table 5.1, the GPTV type receivers have higher quality indexes (the problem of maximum reduction of cost was not stated during their development). The subscriber network of the three-pair wire of the GPTV is more reliable than the single-pair wire network with high-frequency signals where poor contacts at the branch points and connections are sources of cross- talk. The number of transistors and radio parts used to build one GPTV is 15 to 20 times less than required to build the equivalent number of GT. During the first years of development of the system there was orienta~ion toward the development of attachments for the single-program speakers (Gr). This solution arose from an effort to use the large number of Gr [single- ~ program speakers] available to the subscribers. This RT-61 type attachment was produced at the Riga VEF plant. Since the subscribers basically had quality class III Gr, it turned out to be impossible to realize the cl.~ss II quality built into the attachment. The necessity arose for combining the receiving-reneating part with class II Gr and making them in a single case. ~ Thus the Venta GT appe~red with higher sonnd quality which has found high demand among the buyers. Later the improved GT were developed: "Riga," - "Avrora," and "Mayak." In connection with the jmprovement of the processing of the networks for receiving TPB programs in recent years, in nany cities of the country it has become necessary to provide a large assortment of receivers. The problem has again come up of developing attachment for the Gr. The circuitry for such an adapter has been developed and is in the _ experimental operational stage. The "Avrora" GT with somewhat simplified high and low-frequency amplifiers was taken as the basis for the system. Passive attachments are in the developmental stage which will permit the owners of the receivers; tape recorders and television sets to receive three programs without interference. They do not consume power and are simple to service. - 179 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 ~ FOR OFFICIAL USE ONLY The development of the receiving network will proceed in the direction of creating new types of individual devices for various quality claeses, at different pricES and with different external appearances. Table 5.1 . Standardized values _ Name of parameter GT GPTV Sensitivity, millivolts 250 100 Output power, watts 0.15 25 Frequency band, hertz 100-6300 100-6340 - liarmonic coefficient, T: ~ from 100 ta 200 hertz 7 6 above 200 hertz 4 3.6 Modulus of input impedance over the high- frequency channels, ohms 2500 400 - Background and noise level, decibe~.s -40 -55 Crosstalk attenuation between the high-frequency channels, decibels -53 -60 Average sound gressure, newtons/m2 0.25 - Noise protecti~n of the high-frequency channels: - from the low-frequency g�rogram, decibels at a frequency of 1000 h~rtz -53 -60 - at a frequency of 6000 hertz -40 - at a frequency of 10000 hertz - -50 Admissible overload of high-frt~quency channels with respect to input level, decibels 10 10 Automatic gain control range witn respect to input, decibels - 14 Response time of the automatic gair. control, ~ milliseconds 20 Increase in output level on disconnecting the load, - decibels - 2.5 Limits of variation of the feed network voltage, volts - 176-242 - The group devices were developed in three versions: GPTV-1 [19] developed in 1962 had an output power of 25 watts; structurally it was made up of six modules: a replaceable f ilter module (or the filters and the automatic gain control system), the low-frequency amplifier module and feed module for one channel and the same three modules for the other channel. This structural . design is complex and expensive. The GPTV-1 was produced in two versions: ~ with automatic gain control and without it. Practice has shown that it is necessary to build the receiver only with automatic gain control inasmuch as _ its cost increases significantly, and the operating reliability and range of the TP B systea are increased. The GPTV-2 had an output power of 7 watts, _ but simplification of the circuitry and the ~ceduction in its cost turned out to be very small by comparison with the decrease in power; therefore the _ l- - 180 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 I - FOR OFFICIAL USE ONLY decision was made not to build it. The GPTV-3 which is built at the present time is made with a modif ied circuit and structural design. The AGS circuitry, filters and low-frequency amplifier have been simplified, the operatii:g reliabil- ~ ity has been improved as a result of using transistors with long service life (P214 instead of P210 in the GPTV-1) and as a result of a reduction in the number of parts; the structural de~ign has been simplifien: instead of :ix modules there are three. The operating characteristics have been improved: 1. The sensitivity has been increased by four times, and the operation of the automatic gain control, improved (it operates in practice without non- linear distortions while insuring low voltage on the r~gulating diodes). _ 2. The input impedance has been doubled. This makes it possible to install the receiver on lon ger lines, and in combinati~n with increased sensitivity, � it can be installed where the GT cannot operate. 3. The increase in gain of the receiver in an interval of 2 minutes increased from 1.5 to 2 decibels. The high~discharge time constant leads to a reduction = in the average transmission level with respect to the rated level. In the given case the average level is closer to rated level. The range of the - automatic gain control has been increased, which is more important for opera- tion of the receiver. At the same time the dynamic range is not distorted, for the distortions come only during a ~otal gain recovery time of the receiver of less than 1 minute. 4. The rectifier with stabilizer has been made co~mmon to both high- frequency channels. One stabilizer is cheaper and more economical. It has a higher stabilization coefficient. The reliability increases, for the thermal condi- tions of the transistors are equalized as a result of mo?-e uniform loading. The total number of subscriber points serviced by one receiver is H _ 25 watts = 140 - 0.25 watts 0.7 ' where 0.7 is the coeff icient of simultaneous inclusion of all points of the given subscriber network. When using headsets (for example, in the hospital) the number of subscribers connected to the GPTV can be increased to 400-500. 5.2. Riga Type GT The Riga GT (Fig 5.1) has two band filters tuned to channels II and III respectively, a detector, low-frequency amplifier with speaker at the output, a three-position program switch and power pack. In position. 1 of the switch IIa the. low-frequency program coming to the input terminals of the GT is connected through the loudspeaker regu.'_ator R15 to.th~ transformer Tpl, the secondary winding of which has a loudspeaker connected to it. In this case the AC n~twork is disconnected. In position 2 of the switch I[a of the RT, the network is connected to theinput of the band f ilter tuned to a frequency of i8 kilohertz; simultaneously the filter output is connected to the input ~f the detector; the output of the low- 181 FOR OrFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR UFFICIAL USE ONLY _ frequency amplifier is connected to the pr ~nary winding of the transformer Tpl, and the power pack, to the AC network. In poaition 3 of the RT, the - network is connected to the input of the band filter tuned to a frequency of 120 kilohertz, and its output is connected to a detector, the output of ; the low-frec~uency umplifier is connected to the winding 1-4 of the Tpl transformer, and the power pack is connected to the AC network. _ ~ Alamrme~en ~1) 9a T ~ T All Sa .P~ P, rp ' 13�1/� ~ ,p tSO,t ~ R2 i~, . ~ ~j ~ ~ 3 q ~ qf q T /113 ~ r� f~ $gZ r ~ ~C~,BL j ? . ~ T c"C,i~1: ~ ~s 6~~ ~ X ~n~ n~ '%rC~s C~ . ~GOj ~1' M ~ ~ ,9 cn T 7.l (i Rj 4 ~s ~r � A.. �?9~ A I.iU! /!r ~l~ ~ fd0 110 ux tn ~oB �ntiZr 'f7~ p~6 - C~ ~ ` ~p, /1~ ltica , SO Ci ~ , ~ . ~ ~ ~ ~ - . _ ~3~ ~ - . , '~2~ 19~i . ~ � ~ , Figure 5.1. Electric circuit diagram of the Riga type GT Key: 1. Tape recorder ~ 2. Electric network 3. Radio The capacitor C1 blocks the path of the low-frequency program currents to the preset regulators R1, Rz, whi~h served to equalize the initial levels o� the high-frequency programs and prevent overloading of the detector. Their shafts run to the face panel. Each band filter is made up of three loops; for example, the filter of channel II is made up of ;he series L1C2 circuit inductively connected to the parallel L2C4 circuit, and a third L3Cg circuit connected by the capacitor C6 to the second circuit. The capacitor CS is common to both channels. The shunting resistor R5 does not permit disconnec- tion of the base circuit of the transistor T1 at the switching time and pre- - vents it from breakdown. From the f ilter output the modulated signal goes to the ingut of the emitter triode detecEor - the base-emitter 3unction of _ the transistor T1. The detector has the least linear distortions when installing a transistor with a value of S>,20. This stage has high thermal stability, for the resistance to the direct current in the emitter circuit is high. The resistors R5, R6 feed the initial bias to the base of T1. The voltage on its collector is reduced using the R9R5 divider. The low-frequency signal detected and ampl3fied by the same transistor from the load divid~d into two parts (R~, R$) goes through the separating capacitor C10 to the input - of the three-stage low-frequency amplifier operating in the class�A mode. The resi:,:or Rg is simultaneously the volume control, which is aechanically connected to the volume control R15 for the first channel. This coupling .7 182 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY eliminates the danger of short-circuiting of the output, which can occur on movement of the regulator to its extreme position. In order to simplify the commutation R15 is not disconnected from the primary winding T1 on reception of the high-frequency channels. In this case it uses about 7~ of the total output power in the maximum volume position. The capacitor C9 filters the remains of the carrier frequency and also increases the depth of the negative feedback for the higher sound frequency harmonics. The feedback depth depends on the position of the regulator Rg, which also increases the regulation limits. The first two stages of the low-frequency amplifier are the emitter repeater based on the transistors T2, - T3. When using the transistor with S>100 it is sufficient to have one stage. The second stage of the low-frequency amplifier is made in accordance with the transformer circuit with co~on emitter based on the transistor T4. The _ low-frequency amplif ier mode is provided by the resistors R10, R11, R12 and R14. The stability of the load with respect to direct current is insured as a res~lt of connecting the resistor R17 to the emitter of the last sta~e. The feedback with respect to AC voltage is fed to the input to the first stage of the low-frequency amplifier. The feedback diminishes the nonlinear distortions. The R16~13 circuit corrects the frequency characteristic for high frequency and prevents receiver generation. The electric power supply for the GT comes from the AC network. The rectifier - is assembled in accordance with the double halfperiod circ�uit based on the - diodes D1, D2 with a capacitive load of C15. The null potential point with ' respect to alternating current does not coincide with the positive end of the rectifier. This made it possible to do away with two capacitors with a capacitance of 200 microfarads each (C14, C15) and to decrease the cost of the circuit. The filtration of the rectif ied v~ltage pulsations is accomplished by the R1~C14 f ilter. The intake power in the network is 3.6 watts. In order to connect the receiver to the relay network with ri voltage of 15 volts it is necessary to resolder to Tpl (the wire running from the sliding contact of the resistor R15 is unsoldered from the lead 1 and soldered to the lead 2). The Riga GT [triple-program speaker] is made in a wooden case. On the front there are controls for the preset regulators, the volume control and the channel switch. On the back panel there are jacks for connecting a tape recorder and two cords for connecting the receiver to the radio network and the AC network. 5.3. Avrora Triple-Program Speakers [GT] - The Avrora GT [triple-program speakerJ (Fig 5.2 and 5.3) is made in two - versions: for operatic~l on the subscriber networks with voltages of 30 volts and for Moscow, 15 volts. The basic parame~ers are the same as for the - Riga GT [triple-program speaker], but as a result of introduction of the high-frequency amplifier stage into the circuit, its sensitivity is increased. The preset regulators are included here after the filter, which decreases the variation of the input impedance of the GT for various positions of the regulators. The program switch B1 has an additional "off" position. When 183 FOR OFFIC~AL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ' a low frequency program is received the switch must be set to position 1. The low-frequency voltage is fed to the primary winding of the output trans- former TP1 through the fuses IIpl and IIp2 (which are included to keep the AC network voltage out of the RT network and exclude ruining the GT if the radio plug is erroneously plugged into the electric network) and the contracts 5, 6, 10 of the switch Blb' . On reception of programs II and III the GT is connected to the radio network by means of the switch Blb and to the feed network B1a. The band filter of the second channel consists of the connected circuits L, C2L2C4; for the third channel, L3C3L4C5. The high-frequency amplifier is assembled from the transistor Tl; its collector circuit includes loops with tuning to the high-frequency cFiannels which increase the selectivity of the receiver. The diode detector is assembled from the D9V diode. The detected high frequency signal goes through the volume control R,~a and the dividing capacitor C10 to the input of the low-frequency amplif#er, the first stage of which is assembled from the transistors T2 and T3 included as a compositional transis- tor. The connection to the terminal stage is direct. The low-frequency amplifier is encompassed by negative feedback, the voltage of which is picked up from a sep-rate winding 6-7 of the output transformer. � - si~ . . 2 r~-_�-~ ~ ~ (1) ~ ~ I : I - ~ s o s ~ ~ ~ ~ ~,r,t~ e ~ n ~n - s / ~ ~ ~ ~Nme ~ ~ e�w~~~ '�~uni R�y"' . I ! ` ! - ( , t'~ ~ ~ _ ~ ~R ~ T, ~aw G . i u i eK I~ -~o ~ - ti~ ~ ~ ~ I , n.e , i ' I ~ ~I, ~ y,~~ 4i M,~~c ~~r A ~ i~ ` ~ p~ar ~s as ~ ~ ,~~4~,{~~! ~ ~ ~3~ � _ .4l! t'~~rwc'__ _ ~ , . Figure 5.2. Circuit diagram of the "Avrora" type GT. Key: (1) volume (3) Program II level (2) tape recorder (4) radio The depth of this coupling depends r~n the position of the volume control, which also increases the limits of its adjustment. The operating conditions of the low-frequency amplifier are stabilized by the resistors R17, R18 and - the DC feedback through the filter R14C12Rl 3 The pow~r pack is made up of a power transformer, two-halfperiod rectif3er and II-filter. 184 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 rux urrl~tt~, uaG ~rLx [Photo not reproduced.] Figure 5.3. External appearance of the Avrora GT [tripl~-program speaker] ihe Avrora receiver [35] is made in a wooden case weighing 2.9 kg. The GT circuitry is mounted on a printed board fastened parallel to the face plate in a case finished off with a plastic grating. This panel has the - volume control and channel switch knobs. The knobs for the preset controls are located on the back of the case (they are rarely used). On the back there are also plugs for connecting the tape recorder, the network switch for 127 or 220 volts with fuse and the leads of the cords for the radio net- work and the AC network. , The "Mayak" GT (Fig 5.4) differs from the Avrora GT by changes in the input circuits and the structural design. [Photo not reproduced.] Figure 5.4. Outside view of the Mayak GT [triple-program speaker] 185 FOR OFFICIAL USE ONLY ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY - 5.4. GT with Low-frequency Channel Gain (Fig 5.5) - It is known that the crosstalk from the low~frequency to the high-frequency channels occurring in steel wire is reduced with a decrease in the low- frequency current. The magnitude of the current depends on the load on the line: the greater the load resistance, the less the current and the lesa the crosstalk. Consequently, in order to decrease the interference it is . , .r - ~ . 9 ~ (Z~ . ' . . ~ . . - AXnt (3) j - _ = . - B~ (b) (5) . ~ B~~ rPf(4~ ...`9, ~i 7~ r ~t ,,ys~~:~ n~:~e. ~ ~ ~'yti~'~ ` ~::,~r:.~.,.~ y;:;~ o ~ ; ~Nnt ~ ~ ~ ~ : (1~ ) . ~ � . ~ . (10) _ - . . ~ Ba1np~K - . PTcem~ (8) _ _ . . ~ . - ~ _ ~ . . . - . ' . , . - - . 9l~.~E~~`(11) . Figure 5.5. Structural diagram of the GT with low-frequency channel gain Key: 1. Control 7. Detector 2. Passive 8. R'T network - 3. Active 9. Terminal low-frequency amplifier 4. Transformer 10. Rectifier - 5. Low-frequency preamplifier 11. Electrical network 6. High-freqsency part 12. Gr [speaker] necessary to increase the input impedance of the GT connected to the subscriber points, that is, to decrease the power fed to their input. Since _ ~ the volume of the GT on the low-frequency channel must not be less than the volume of an ordinary speaker, the decrease in power at the input must be compensated for by amplifying the low-frequency signal, for which it is impossible to use the amplifier available in the GT circuit which is used _ ~o a~pl~fy the signals of programs II and III. The r.eceiver with amplifica- tion with respect to the low-frequency channel has certain advantages in addition to the decrease in crosstalk: the possibility of raising the low- frequency characteristic appears; with simultaneous use of seveial plugs installad in the apartment on fi.he low-frequency channel, the power intake from the PV network in practice does not increase by comparison with the - power intake by one ordinary speaker; the output power of the GT can be - increased to 0.5-1 watt without increasing the network load; in the future it will be possible to increase the number of subscribers connected to the network without increasing the power af the station repeaters, The ~ 186 FOR ~FFICIAI. USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4 FOR OFFICIAL USE ONLY possibility of improving the volume of the low-frequency channel both f or liigher quality operation of the remflte subscriber points and for introduction of stereophonic broadcasting requiring equal volume of both used channels, is important. The signals from programs II and III go through the GT exactly as in the ordinary GT without low-frequency amplification. The 78 and 120 kilohertz f ilters are installed at the receiver input. From the output of the high-frequency f ilters the signal goes to the detector; the detected signal goes to the low-frequency preamplifier. The input of the terminal low-frequency amplifier is connected to the output of the low-frequency preamplifier through the switch B1, which makes it possible to connect the input of the terminal low-frequency amplif ier to the PV*network when listening to the first program. The terminal amplif ier is loaded on the speaker which can be connected directly to the network (without amplification) and it is possible to hear the first program in the case of absence of voltage in the feed electric network. As is obvious from Table 5.5, the GT with amplif ication with respect to the low-frequency channel contains two additional switches which provide for its operation with respect to the first program with or without amplif ication of it. In ad~ition, the low-frequency amplif ier of this receiver can be connected to the PV network only through the transformer. The connection of the subscriber network to ~he input of the low-frequency amplifier cannot be made without a transform~~r as a result of the high back- ground level occurring in the output of the c~T. These structural complications increase costs somewhat, and the introduction - of an additional transformer into the circuit increases the copper consumption for the wire broadcast needs. The problem of introducing this type of GT has still not been solved. 5.5. GPTV-3 Group Device _ The GPTV is made up of two independent receivers distinguished from each other by the filters and circuits in the high-frequency amplifier tuned to 78 and 120 kilohertz respectively and the common power pack. From the diagram of the GPTV [18] presented in Fig 5.6 it is obvious that the receiver of one channel is made up of the band filter, high-frequency amplifier, detector, low- frequency amplifier and automatic gain control system. The schematic diagram of the GPTV is presented in Fig 5.7. At the input the GPTV has a type K filter, one element of which can provide for attenuation with respect to the other high-frequency channel to 46 decibels. In this type of filter the series and parallel branches are return two-terminal networks, that is, Z1Z2=R2. This condition is satisfied when their resonance frequencies are equal to w1=w2=w=7E kilohertz or L1C1=L2C2. In this case the selectivity of the filter is improved. In the GPTV the filter is made up of one element. _ Resistors are connected at ics input in order to decreas~e the effect of the feeder line resistance on the frequency charactertstic of the filter. The transformer L2 supp resses the cophasal interf erence operating with respect to the "two wires-ground" circuit. The filter has an input impedance of *wire broadcasting 187 FOR OFFICIAL USE ONLY _ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 I MUL BY YR. DZYRDCH I K, S. A. ZRSLA~SK I Y 31 JANURRY 1980 B. N. F I LRTO~, R. SHERSHRKONR t FOUO ) 3 aF 4 APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 ~ I ~ FOR OFFICIAL USE ONLY . - lap. (2) --------~�Ira6oytymaM (3) " (4) !layarn'B~rrq ~ ~ ~ - ~ . 1 t g) Qune p yBy ,Qtme yNy ~o~ON~HRIOM ( 3~ I ~ ~S~fu . ~6) ~7) . ~8) ' - ( pmpT ~ /!Py 10~ j . ' AuHU - - - --�-----J � � - 6noK N ce~rE . numayus (12) ~ , , r---- 14 ~uniinp yBy Qemen yHy ~ daoNeHma,~ 3) ~ ~2oKr ~ . - � ~ (13) . ~ ~6) (7) ~8) I .I . � ~ � ~ I - - I APy 10~ ! ' � . ~ � /rUNdp 120I~PU~5~j . � L------------------ - Figure 5.6. Structural diagram of the GPTV-3 receiver _ Key: 1. From the RT lines 11. Power pack 2. Program I 12. Network _ 3. To the subscribers 13. Band filter 120 kilohertz 4. Channel 78 kilohertz 14. Program III 5. Band filter 78 kilohertz 15. Channel 120 kilohertz 6. High-frequency amplifier 7. Detector 8. Low~-freque:.~y amplifier 9. Program II 10. Automatic gain control 400 ohms (the average uupedance of the subscriber tsansformer on high frequency). The high-frequency amplifier with load in the form of a single two-stage ' circuit is based on the MP40 type transistors. It is used to amplify low _ voltage of 5-10 millivolts on the regulating diodes of the automatic gain _ coztrol to a voltage sufficient for undistorted operation of the detector - , and also to insure additional se?ectivity with respect to the adj~cent channel. - The operating conditions o� the high-frequency amplif ier are stabil.ized by including the resistor R9 in the emitter circuit of the transistor T2. The input and output circuits are tuned ta the carrier frequencies by the _ capacitors C5 and C10' 188 FOR QFFICIAL USE ONLY ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FUR OFFTCIAL USE ONLY The signal detector is two-cycle based on D9G type diodes. The current - running thrnugh the load has a freqL~ency of 156 kilohertz, that is, the current with a basic frequency of 78 kilohertz is absent in the load, which facilitates filtration of the high-frequency component of the aignal. The = condition of absence of nonlinear distortions i~i the detector is equality of ~ = the load resistances of the detector for direct and alternating currents, ~ rY?at is, observation of the condition RA~/RDC30.8. For this purposs th~. load resistance of the detector is split into two parts: R11 and R12. Then ~ RBxRas 11 + 15�5,1 ' ~ knep Rii -t- Rea -f' Ria _ 15-~-5,1 l~s Q,9e ( ) Rii Ri, 11-~- 5.1 Rnxr 2. Key: 1. RAC~RDC where RinP is the input impedance for the alternating current of the low- frequency amplifier. The capacitance shunfi.ing the load of the detector is selected equal to 620 picofarads, which cc~rresponds to a maximum transmission ` coef f icient of the detector and facilitates an increa in selectivity of the receiver with respect to the other channel as a resulc pf using the properties of inertialessness. The suppression of the interference at the detector output " is proportional to twice the amplitude ratio of the signal and interf erence carriers at the input of the detector: � ~1) rUc r~ = c~ cxrn \ U - )8 \ Unax !ax (4 ) - r2) . ~ Key: 1. signa.l; 2. interference; 3. output; 4. input Let us assume that signals of identical level arrive at the inputs of the two channels. The int~erf erence of one of tnan, for example, II, is 1 measur~d in the interval of the useful signal when the carrier amplitude is diminished by 20 decibels, that is, st the input of the channel the inter- f erence exceeds the signal by 20 decibels. In the f ilter this interf erence - is attenuated by 40 decibels and becomes lower than the signal level by 20 decibels; in the high-frequency amplif ier the interference is attenuated by another 15 decibels. The detector gives suppression by 35+6=41 decibels, that is, a~ the output of channel II the interf erence from channel III will - be attenvated by 35+41=76 decibels. If the interference comes to the channel input, for example, 3 times the signal level (by 10 decibels), then it will be attenuated by 56 decibels in the receiver. The filter and the circuits ~f the high-frequency a~plifier also provide for suppression of ~ the crosstal~C from the low-frequency channel t~ the high-frequency channel by 60 decibels. 189 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 , FOR OFFICIAL USE ONLY ~ - - . . ~r:r~:7cvcXrrx 74~d'q d~ - I . . . s.ax ~ ~l~ . � ~0 , ~ ~ I t4a ~ N, A, qexr ~s ~ c+' ~ Il'v.~ax ~T, i Q I "if.~ TP,t T ~j91 . , c, R,, . ~S ,~nvo ~.l ~ ~ wis~~ ~.~lr � ; ~~1~/r' i! u!X ( lr4 At ca i , ~ 'o . . - C~ s P, ~ ~n d' . 9 _ 0 1Gn 2~70 ' . . 1 ~ , - . ~B Cp9~ ` . . w_ ~ ~YY L11r . K . .e.~ � I 6~o~r ~umrrNrrp qp - . . : ~ ~2~ masxso - . IYS B~ ~1P~ T'~ .I{~ ' _ _ . = ~ . 'A a ~ . . ~ ~ ~p~ ~ A - c G C ~ - - - I 1A 11~dSr~ ~ t~~ I . Aa ~~g p , ~ ~ - . ' ~ . - . . . . . : ' - ~ _ y _ I . . . : , ~ . . ~ ~ . - - Figure 5.7. Circuit diagram of the GPTV-3 ~ey: 1. Amplification module 78 kilo'r~ertz 2. Power ;pack - _ The first stage of the low~-frequency amplifier based on the MP40 type _ transistor operates by the system with separated load and is used for transition tothe two-cycle stage. The load resistance is in the collector _ ci~;:uit and is divided into two parts: R14 and R16. The high internal impedance offers the possibility of encompassing subsequent stages with feedback. Since the input impedance of the next to the last stage is low . as a result of the negative feedback, the first stage does not give voltage amplification. The stabilization of the operating conditions of the _ transistor T3 is realized by the resistors R15, R16' The coupling to the 190 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY a�/~~ ~ ~w.~~ Ar 6YY TB /7 ~ ' R~ ~ ~ ~r ~v~ ~r � Rq I,VX ~rQ ` J: J l � ~ ~ c : ; ~ ra . ~n ~~~r~. i ~ ia S.., D , l A' I ~ T 3,0 B~s ~..y--,=r~ - , . d~ r~ ~ A1QU0 C~ ~ ~ ~ ~ ~S /A � ' 4 5~,~ ~ i ~ 8 ~r ~ t ~ . R ( ) x~ R~ -r'-~. 4 ~'c ~ ~,3 1S0 Ts ,;pi.: ~ ~ t� ~ r d( F'Pr ~ ~ w I .y , 'a _ ~ Ir~ ~ ` ' , � ~yyK � ~ � i2; ~fB ' 1 ~ . ~ ~ zJ0 . . ' . . - ~i ~ . ' . ~ I ~ .J ~ Ts . ~ t I ~ . . ' '~X T n31~IQ T' ~ . ' I . ~ _ . - ~ ~ ro ~-~~lt . ` YRVJ.4 ~ 1~t5 ~ - ~ R Rn . i'~ 5~ qtf 0~ t.~ - � A~ ? si~ R ~ ~ ~~Pl ~ ~ ~X~ iw a. - rP~? 3A N y~~.''~ ~ 3) ~ 3. Ta the channel 120 kilohertz 4. MP40 5. MP40A next to the last stage is rheostat-capacitive. This two-cycle transformer ~ stage executed from the MP40a transistors gives voltage amplification from 100 millivolts to 10 volts. The t~rminal stage is m~de from P214V type transistors in accordance with the circuitry with grounded emitter. It operates in the class B mode. In order to eliminate the nonlinear diatortions of the central cutoff type, especially noticeable in the case of low signals and low air temperature, the initial bias is fed to the bases of the _ transistors T6-T9 trrough the resistors R24, R25 and the thermal resistances which also stabilize the opGraLing conditions of the s.*.age on variation of _ 191 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY the ambient temperature. Eac'~ pair of parall,~l-connected transisters is located on the radia~or, which insures normal operating conditions of the receiver even under the conditions of short circuit load and high air tempera- ture (+40�C). In addition, provision is made for two-stage protection of the transistors from short circuiting using fuses. The output and the next to the last stages are encompassed by parallel feedback as a result of which the low-frequency amplif ier haa low internal impedance and operates well on - variable load. On disconnect.ion of the load the output volr.age increases from 30 to 32 volts. The RC circuit which eliminates possible generation when working with the disconnected or capacitive load is connected t~ the secondary , winding of the output transformer. Inasmuch as trie GPTV operates without - constant servicing and operative level controJ. at its output is impossible, _ _ an automatic gain control is introduced into the circuit which is designed for fluctuations of the high-frequency signal level within the limits to - 14 decibels. Introduction of the automatic gain control offers the possibility of installing the GPTV at the end of the long lines and insurance of stable operation with a large number of subscribers. The fluctuations of the attenua- tion in the lines occur slowly, over a period of several hours, for they are basically determined by the meteorological conditions. The rapid jumps in level are passible in the case of damage to the line, and fast response of the automatic gain contrcl is required with an increase in the input level, _ but slow recovery over a period of several minutes is admissible with a decrease in it. The response time of the automatic gain control is selected equal to 20 milliseconds (on cc,nnection of the broadcast programs the non- liriear distortions are undetectable to the ear), and the time for increasing the gain by 2 decibels (after picking up the input signal) is 2 minutea. The difficulty in building the automatic gain control consists in the fact that the known procedure using carrier frequency fluctuations is unsuitable in the case of 98M signals with variable carr3er, for it leads to compressiun - of the dynamic transmi~sion band and tQ an increase in noticeability of the - - crosstalk in the intervals. It is also impossible to use a pilot signal for automatic gain control, for its frequency must differ fro~ the carrier freq~sency by no less than 15 kilohertz so that the beats between the carrier and the pilot signal are not noticeable. However, in t',is case tYie relative difference between the freQuencies of the carrier and the pilot signals is found to be large, and the attenuation in the signal for these frequencies ` can turn out to be different, that is, the variation in 4mplification as a result ~f the effect of the auto~atic gain control can fail to coincide - quantitatively with the actual requirement of the variation. In the GPTV the automatic gain control is used with storage of the maximum carrier level. Since the output ~oltage of the lourfrequency amplifi.er is proportional to thE carrier level, a winding is wound on the autput transformer to see to the operation of the automatic gain control. The selection of the regulator for the automatic gain control is conditioned by the sufficient range of control and comparatively low nonlinear distortions in the entire control range with maximum admissible level of thE input signal (in order to h~ve less amplification of the high-frequency amp].ifier). A regulator was selected which operates by the potentiometric system and has low high-frequency resistance so that shuntin~ of it by the input impedance of the high-frequency 192 FOR OFFICIAL USE ONLY - APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY amplifier will not decrease the control range. The semiconductor diodes used in the conduction region do not introduce distortians for a high-frequency signal level up to 5-10 millivolts. The D226V type diodes are used in the _ circuit. They are connected in series with respect to direct current and parallel with respect to low frequency. The control consists in variation of the transmission coefficient with respect to the high-frequency divider made up of the resistor R4 and the diodes D1, D2 with variation of the magnitude of the direct current f low through these diodes. _ The automatic gain control ~perates as follows: the low-frequency voltage is detected by the diodes D5, D6, and the direct ~~urrent flowing through the ~ diodes D1 and D2 chariges their resistance with res,~ect to high frequency. _ The resistor R4 and the controlled resistance of the diodes form a divider with automatically variable ratio with respect to high frequency. With an - increase in voltage at the input, the direct current increases, and this ratio decreases. The stabilizer voltage of 23 volts is used as the delay. - The detector of the automatic gain contral has large dischar~e time constant ~ (several minutes), which keeps the amplification coeff iciei~t :n the trans- mission intervals and the dynamic range invariant. This discharge time is created by a capacitor C9 with a capacitance of 200 ~icrofarads and the resistor R~ with a resistaiice of 2.7 megohms. The sensitivity of the receiver in which the automatic gain control begins to operate is 10 millivolts. - With an increase in the input level by 14 decibels, the output voltage varies frum 23 to 33, that is, by 3 decibels. The automatic gain control does not introduce noticeablc nonlinear distortions; the deficiency of it is an - increase in noise after prolonged interruptions and a decrease in volume by - 2 to 3 minutes after the pulse interf erence. The electric power supply of the GPTV is autonomous --from the AC network. The f eed module is cou~on to both channels. The rectifier is double half- period. It is equipped with a filter which starts with the choke, which is better for operation on a variable load (at *_he filter output the DC voltage varies to a less degree than for the f ilter beginning with the capacitance). ~ Inasmuch as the GPTV is fed from the household network, the voltage of which can vary significantly, and it operates without servicing, it is impossible to guarantee fail-safe operation of it without stabilization of the DC _ voltage. The AC voltage stabilizer does not fit here, for it has a large scattering field (which leads to a high background level of 50 hertz at the receiver output) and also in con..ection with the fact that the terminal stage of the low-freqiiency amplifier operates in the class B mode and is a variable load for the rectif ier, the voltage at the output of the rectifier _ does not rema~n constant. The operation of the stabilizer is based on the - fact that the magnitude of the emitter current in the transistor does not depend on the voltage var3.ation of the collector. If we connect the load (the receivers) to the emitter circuit of the stabilizing transistor T13-T15' the em~tter repeater circuit is obtained in which the voltage on the load is almost equal to ihe voltage on the base of the transistor. It is necessary to keep the voltage on the base constant. On variation of the load, the emitter and base currents vary; therefore in order to obtain a a 193 FOR OFFICYAL USE ONLY E APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY " DC voltage on the bases of the T13-Tl , two stages based on the transistors T11-12 ~P214V) are included. The voI~age on the base of T11 is stabilized by the "parallel stabitizer" circuit using the transistor T With an increase in voltage at the input of the stabilizer, the vol~~ge increases somewhat also at its output. Hexe the voltage on the base of T10, its collector current and voltage drop on the resistor Rlp increase. The voltage on the base of T11 decreases, and the voltage at the output of the stabilizer decreases. Analogous processes take place with a decrease in feed voltage and on variation of the load. On variation of the network voltage from 176 to 242 volts and with simultaneous variation in the load - current from 0 to 4 amps the voltage at the output of the atabilizer varies _ by no ~ore than 4%. In order to increase the operating reliability of the stabilizer the output stage is assembled from three parallel-connected transistors of the P214V type with resistances in the emitters of 0.3 ohms each which equalize their current. In addition, the transistors are located on the radiators, which insures sufficient reserve with respect to the dissi- pation power. The stabilizer has low internal impedance with respect to alternating current; therefore the operation on both channels of the receiver *aithout an increase in the crosstalk between them is possible. The power intake by the GPTV from the network in the rest mode is 33 watts and in the _ rated power mode in both channels, 180 watts. - Structurally the GPTV is executed in the form of a small bay in which there are three modules: the receiver module for channels II and III and the power pack. The bay is closed by a removable door to kiiich a lock is fastened. The external appearance of the GPTV is presented in Fig 5.8. The GPTV is _ m~unted on the stairwell wall of the upper story of the building as clos~ as possible to the subscriber transformer, or it is installed on a table in tile specially assigiied facility. The receiver is connected to the TPV [triple-program wire broadcast] network by the sch~me shown in Fig 5.9 (to the secondary winding of the subscriber transformer) or Fig 5.10 (to the distributing feeder through the bypass increasing the magnitude and the stability of the high-frequency program level if this level is below 50 milli- volts). The outputs of all three channels are connected to the intermediate terminal block instalied on the rear wall of the bay. The three-pair, intra- building network is made of KRVPM-3x2x0.5 or KRVPS-3x2x0.6 cable which runs ~ from the GPTV to the subscriber switches through the KTVO splitter blocks. - [Photo not reproduced.) r^igure 5.8. External appearance of the GPTV-3 194 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY � ~ ~ ~ (5) (1) ~ ~2) � 8~a B r~ r-- - ~ . I 1 d 1 1'I ~ ~ ~4~ - - - - a~ rnre Figure 5.9. Connection at the GPTV through the OU sectional center ` Key: 1. Distributing feeder 4. GPTV 2. Subscriber transformer 5. Speaker 3. Sectional center a , AT (3 ) 3X _ � , ~r . , bf ~ . . l'l)T8 .$d ~ ~ , ~ Figure 5.10. Connection of the GPTV tothe subscriber transformer - Key: 1. GPTV 2. Distributing feeder _ 3. Subscriber transformer The output level of 30 volts is established in each channel by the level control on f eeding the low-frequency signal to the input with modulation _ frequency of 100 hertz and depth of 70% on a load equivalent of 36 ohm~. 195 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY CHAPTER 6. MEASURING DEVICES AND INSTRUMENTS - 6.1. General Information The proper operation and maintenance of the TPV [triple-program wire broad- - casting] system requires the application of the corresponding measurement equipment for tuning the transmitters and reGeivers, amplifiers, measuring the electrical parameters of the low and high-frequency transmission chann~ls. The TPV system has a number of peculiarities which complicates the application ' of the existing measuring equipment and which must be considered when develop- ing new instrumen~s. These peculiaritics include the fcllowing: Amplitude modulation with adjustable carrier level wict~in the limits of 10 to 100%; A broad pass band with respeci to the carrier equal to +1~ kilohertz; Rigid requirements on tlie harmonic coeff icient; The presence of various channels (low and high frequency); Signifi~ant voltage of the low-frequency channel sub~ect to measuremEnt (~o 300 volts); Great difference in magnitudes of the voltages of the low and high-frequency - channels to 1000 times. _ The stability of the signal level of programs II and III in the RT networks is appreciably worse than the signal of program I; therefore the demand for monitoring them increases. The measuring equ~pment for the TPV must have smal~l nonlinear distortions, a wide modulating frequency band, small cross- talk between channels, ad~ustment of the output voltage within broad limits, syrtunetric input and output, relatively large input and small output resistances.. With respect to purpose the instruments can be divided into stationary and portable. - 196 FOR OFFICIAL USE OPILY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 � FOR OFFICIAL USE ONLY The stationary instruments make it Possible to centralize the measurements at the TsUS, OUS and TP. Frequently they are built into the station equipment, for example, into the SVK and STP bays. Portable instruments have been designed for monitoring the networks and lines. They are produced in large quantities, because the line service personnel need them. ~ The modulation attachment and the test signal pickup with high indexes of standardized electrical parameters have been developed for the TPV. The simplest measuring instruments are the lineman's display and the RTPV-2 pulse meter, by means of which it is possible to meascre the voltage in each of three channels. A complex resistance meter has been designed for introduction at the line - development system measuring the resistances of the lines and sections of them. A high quality monitoring receiver (KPU) is also used to check the - high-frequency network of development units. It is possible to measure the level diagram of the high-frequency programa on the distributing f eedere by using the high-frequency VRG-3 measuring oscillator [31]. A damage finder has been developed to find damage in the ~ radio relay lines. All these instruments are transistorized. They are small in size and lightweight. 6.2. Modulation Attachment - The modulation attachment (MP) (Fig 6.1 and 6.2) is a source of AM signals of the carrier frequencies of 78 and 120 kilohertz, and it is needed to check out the receivers, amplifiers and line devices. In addition, in combination with the KPU the attachment can be used to check out the dis- tortions of the shape of the AM signal envelope introduced by the passive - network development units. In practice the attachment makes it possible to ~ make an entire set of ineasurements of the quality indexes and eYectrical ~ characteristics (with the exception of the time parameters) of all active and passive devices :~n the system. The MP circuit contains the low-frequency f ilter FNChl, the phase shifters FV78 and FV120, modulator, the low-frequency filters FNCh2 and FNCh3, the modulated oscillation amplifier iTMK, the circuits K78 and K120, the symmetrizing transformer (ST), the monitoring detector, the channel switch, the output voltage switch and regulator, and rectifier. The attachment operates jointly with the osciliators: G3-33 is the source of carrier frequencies and G3-35 is the modulating frequency source. In _ = the f irst case the voltage from the oscillator is fed to the high-frequency input, and in the latter case, to the low-frequency input. The resistance _ of the high-frequency input is nonlinear and small in magnitude. In order to decrease the voltage of the carrier frequency harmonics, the FNCh-1 low- frequency filter is included at the modulator input. Although the circuit 197 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY � _ 3 . . ~ ( --1. . ~ a6~~?~ ~ ~ ~ ( ~ s,r~r ~ (9 � _ � ( ! � sa+'v m R Ir ~ ~ l ~�s '~a D �e~ uo ~r ~ e� ~12). ~ ~11~'0"'~ - ' (2) ~v4 ~ y ~ . ~~lg~ ~I 1 ~da9 . _ ~ y ~ . . . , . ~+apura~a~t (15) ~ ~ � Figure 6.1. Modulation attachment Key : I. Low~frequency 8. Decibels - ' 2. Hig:~ frequency 9. UMK modulated oscillation amplifier 3. Frequency 10. Vo~tage 4. FNCh2 low-frequency f ilter 11. Manitoring detector 5. FNCh3 low-frequency filter 12. High frequency 6. Modu~atar 13. Low frequency 7. Regulator 14. FNChl lourfrequency filter 15. Rectifier - [Photo not reproduced.] ' Figure 6.2. Outside view of th~ modulation attachment 198 - FOR OFFICIAL USE ONLY _ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY diagram of the modulator is more complicated than usual, it provides small _ nonlinear distortions with great depth of modulation. From the modulator output the AM signal gces to the input of the LTMK, where the signal is power-amplif ied. Since carrier frequency harmonics occur in the modulator, the FNCh2 and FNCh3 low-frequency filters are included in the circuit to _ eliminate them. In order to decrease the cross modulation in the UNIIC during testing of the ~ various TPV ~levices for noiseproofness, the K7F and K120 circuits are - connected to the output of the UI~C. The symmetry of the output of the MP is insured by the transformer ST. In order to check out the operating quality of the attachment, that is, to measure the nonlinear and frequency distortions ' introduced by the modu'_.ator 3nd the UMK, the circuits include the monitoring detector. Connecting a meter to measure the nonlinear distortion coeff icient ~ and a voltmeter to its output, it is possible to measure the frequency characteristic of the MP and the harmonic coeff icient with respect to the " env elope. In order not to equip the portable device with a special power supply, the UMK is powered by rectifying the. high-frequency voltage from the G3-33 generator output. At the output of the attacr.*.aent, a modulated voltage is obtained with carrier frequencies of 78 and 120 kilohertz and a modulation ;:~pth oF m=70%. It is possible to regulate the magnitude of this voltage - from 15 mv to 6 volts. The rated voltages are switched from 0.3 to 6 volts - with an output power of 40 milliwatts. The MP is a high-frequency device. The range of modulating frequencies is from 50 hertz to 10 kilohertz with nonuniformity of 0.2 decibels. The harmonic coefficient in the frequency band of 50 to 5U00 hertz is no more than 0.2% (at the monitoring detector output). The ratec~. input voltage of !8 and 120 kilohertz is 12 volts; the modulating frequency voltage is 11 volts. The rated voltage at the output of the monitoring detector on an active - load of 100 kilohms with parallel capacitance of no more than 300 pico- farads is 0.775 volts. The input impedance for frequencies of 78 and 120 kilohertz is 30 ohms; for the modulating frequencies it is 600 ohms. The crosstalk between the channels is 70 decibels. 6.3. Lineman's Indicator The indicator is designed to measure alternating and direct voltages of three channels an3 resistances of two direct currents. Its circuit diagram is presented in Fig 6.3. - The indicator is made up of two switches, two voltage dividers, f ilters, - a rectifier and microammeter. There are five jacks at the indicator input. One of them is common, and one of the wires of the line is connected to it. 199 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY Depending on the measured parameter it is necessary to connect the second wire to the jack: V~ for measuring AC voltages; V= for measuring DC voltages; Rxl and Rx100 for measuring resistances. The limit switch II1 of the scales for measuring the voltages has five positions: from 0.5 to 1.5; 6, 30; 150 and 300 volts. The switch for the type of operation IIZ also has five positions: nch measurement of AC voltages; 78 measurement of the 78 kilohertz carrier voltage; _ 120 measurement of the 120 kilohertz carrier voltage; V= measurement af tne DC voltage; St measurement of the resistances to direct current. The first voltage divider I DH is connected to the AC circuit. It switches from the 1.5 scale to the 6 volt scale. On switching to the 30 and 150 volt scales it remains in the 6 volt position, and the variation of the scale limits is realized by the second divider II DH included in the - DC circuit. On making the transition to the 300 volt scale the second divider remains in the 150 volt position and again enters into the operation of the I DH. This complication of the scale switches is intended to decrease the error in readfng the instrument as a result of the effect of spurious capacitances and the possible asymmetr;~ of the measured low-frequency voltage~ The II DH decreases the power of the rectified current to the magnitude required for complete deflection of the instrument indicator, and it reduces the effect of the spurious current to a minimum. In order that during switching the filters not change the frequency characteristic, the resistance of the I DH must be constant. This is insured by inclusion of resistors R1-R5 and R13. The second divider is made up of the resistors R22-R24; it insures _ constancy of the load rPSistance of the rectifier which is assembled on the basis of the diode D. The capacitor C15 filters out the variable components of the currents after detection. The filter of the low-frequency channel is a 1I-type L1C1C2 element with cutoff frequency of 15 kilohertz. The 78 kilohertz filter is made up of the ~ three-element band filter L2L3L4C4-Cg, and the 120 kilohertz filter, from one element L5~6~12-~14� - The AC voltages are me.zsured by the circuit in Fig 5.4. The scales of the in3icator are calibrated in the effective values of the AC voltage. The instrument error does not exceed 7%. When measuring the voltage of the _ high-frequency channels as a result of the crosstalk between them the additional error does not exceed 3%. When measuring the low-frequency voltages the error as a result of the crosstalk from high-frequency channels is absent. When measuring the DC voltages the measurement limits are 200 FGK OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 - FOR OFFICIAL USE ONLY ~ ~ ' o,~, ~H ~ . . . C c'~' o ~1 1 + . ~ ~ N ~ ~ V /1 v '`V C ~ rl . o ~ ~ ~ ~ ~ ~ ~a~ ~ ~ 0 = t ~ - ~ u C~' � ~ cd ~ u - . ~ ~ ~ . b b ~ .(-'a . V ~ ~ v ~ _ _ � ~ ~ ~ c~'i G ~ ~ ~ � ` ~ C~" q ~ ~ - �~I . . a ~ r ~1 ' ~1 fyl C � ~ ' ~ Gl ~ � _ ~ , - . CO � ' �rl y ~ � C 4 _ ~e 1 + ~ ~ ~c ~y ~ CN`~~ 0 ~ O~ a ~ \ ~ Q..~~q h . . g ~ N . 1~~ ~~,t C~ x ~ p o ~ ~ . - u o ~ . � . ~ u r~ N T N C~l+ 201 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY determined by the resistors R~-R10. In this case the meter has a high - input impedance caused by high sensitivicy of the mi~roammeter. In order to measure the resistance to the dirECt curr.ent the indicator has a two-limiC oiimmeCer mude in accordance with the serie~t circuit with balance null control. The pow~r suppl; of the indicator is the KBS-D-0.5 type dry cell. _ ~ ~i . . . ; g, ~ ~ Bs ~ f. ' . V / ~t~ ; ~ . M ~ . � . ~l~- . . . Figure 6.4. Circuit for measuring AC voltages MI � Key: ' 1. IP iridicator - - 6.4. Complex Resistance Meter (IKS) When introducing the TPV [triple-program wire broadcasting] it is necessary to carry out tedious high-frequency development of the RT networks in order to create conditions close to the traveling wave conditions and insure an input impedance with low reactivity, which var~es little in the frequency bands from 72 to 84 and from 114 to 126 kilohertz. The existing instruments do not permit measurements of the total resistances _ with unknown magnitude and sign of asymmetry on the required frequencies with given error. Thus, for example, when making the measurement by the MPP-300 bridge it is necessary to know in advance whether the resistance - subject to measurement is symmetric, and if it is asymmetric it is necessary to know the sign of the asymmetry. The IKS instrument can be used to mea.sure the input impedances of lines and secti~ns of lines, TP [transformer substations] and high-frequency devices having any asymmetry with respect to ground. Its operating principle is based on measuring AC voltage f ed to the input of the line with a magnitude of current f lowing through the line known in advance (Fig 6.5). Within the limits of one scale this current is always establ3shed at one and the same value b~ regulating the measured voltage of the line input. In this case, in order to discover the magnitude of the modulus of the input ~mpedance of the line it is sufficient to measure the voltage at the input of this line, and it is possible.to calibrate the voltmeter scale directly in ohms. 202 FOR OFFICIAL USE '?NLY _ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY In accoxdance with this operating principle, the str.uctural diagram of the IKS depicted in Fig 6.6 has been developed. It includes the following: the oscillator, the reactivity box, voltmeter and switching devices. " A. t ~ ~ ~ L ZX - Figure 6.5. Operating principle of the IKS [complex resistance met er ] Key: 1. generator ~ BlJXO~NO(1 ( 2 ~ � ` ' , . . " " ~ ~paNC~~ae~a~,~n . ~ ~1) QJ~,~o~ra~?ocnu~ ycunum.e~j e,-~� ~ ~ID ..~~.T~ . . i ~ i 3) �r': 3 B, Z ~ q~ - L~ _ A r:. l 1..~-0c' i 3 ,x, E Br~ 1 - _ v ~ ~ Om~yun A'a~ ~ ~ 5 6 . M~tO.~uH (7) ~ Cin~7mue~~+� a;:c~xr~mr~ (4) . ( ) ( ) . ~ea~rmuCNOCmcu . ~ Figure 6.6. Complex resistance meter . Key: 1. Wide band amplifier 5~ Reading 2. Output transformer 6. Calibration 3. Calibration 7. Reactivity box 4. Selective indicator The generator consists of the master stage and the wide band amplifier and is used for f eeding sinusoidal signals of given frequency and power to the measuring circuit. The generator can provide four fixed frequencies: 0.4, 3, 6 and 10 kilohertz; it covers two bands: from 68 to 88 kilohertz and from 110 to 130 kilohertz with smooth tuning. - 203 ~ FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFTCIAL USE ONLY ~ The wide band amplifier (ShtJ) has a pass band from 300 hertz to 150 kilohertz with a nonuniformity of 4 decibels. At the output the amplif ier provides a power of 50 milliwatts on all operating Frequencies on a load of any nature. The gain cuntrol in the wide band amplifier (ShU) is used to calibrate the instrument, that is, the magnitude of the current flowing through the line oC determined magnitude selected when designing the instrument is established. ~rom the amplifier output the voltage goes to two output transformers: one for low frequencies and the other for high frequencies; and from their secondary windings it goes to the line, that is, the load of the amplifier is the measured resistance of the lir.e, and when measuring the total resistances the reactivity bo~ also. The calibration resistor Rsh is connected in series in the line circuit. The current in the line is established (the scale is calibrated) by measuring the voltage drop on this resistance. In order to increase the precision, the range of ineasured resistances from 20 ohms to 3 kilohms is broken down into four intervals: - 20-100, 100-300, 300-1000 and 1000-3000 ohms in the frequency band of channels II and III. It is desirable that the power fed to the line input during calibration would be identical on all intervals. Tk?erefore, the circuit includes the switch B1_1 which realizes discrete measurement of the voltage fed to the line input: the higher the input impedance, the higher the fed voltage. However, since at all limits the voltage corresponding to - the lower limit is measured, in order to eliminate the error in the measure- ments the magnitude of the calibration resistance on variation of the mFasure- ment limits also is varied by the switch B1_2. - The shunt resistance is selected small in order to decrease the errors when measuring the modulus of the r~actances so that in the least favorable case - (when measuring the resistance moduli near 20-30 ohms) this erxor does not exceed 10%. ~ The input of the ohmmeter is switched by means of B4 from the calibration - resistor Rsh to the output of the generator through the voltage divider R1, R2. Since the scale of the voltmeter is not calibrated in volts, it is more correctly called an indicator. The selective indicator includes the band f ilters, a wide band amplif ier, detector and the M265 type magnetoelectric microammeter with a sensitivity of 200 microamps. - The filters with an average frequency of 78 and 120 kilohertz pass only the . f irst harmonic of the frequency on which the measurements are made, and - the harmonics of this frequency are delayed which can occur both in the generator itself and in the real line. The elimina.tion of these harmonics increases the accuracy of the measurements. . The anglesbetween the active-ard reactive components of the input impedanc~e are measured by the compensation method: the reactanCe opposite with respect to sign to the reactance of the line input is connected parallel to the line input, and its magnitude is established so that these reactances 204 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ~ are mutually compensated fo.r. Here the modulus of the input impedance of the line reaches the maximum value an3 becomes purely active. The compensating _ reactivities are included in the composition of the IKS meter and are an inductance and capacitance box. The inductance box contains five stagas: "off," "0.75," "0.25," "0.75" and "0.025" millihenries, that is, it can assume only discrete values. Therefore, for exact compensation of the i capacitance of the line input, a variable-capacitance capacitor is connected in parallel to the inductance. Thus, after obtaining the compensation for the reactivity of the input impedance of the line with respect to the scales of the boxes it is possible to reckon the values of the capacitances or inductances required for compensa- tion and calculate by them the compensated magnitude of the reactance and the phase of the input impedance of the line. The basic instrument when - iaeasuring the angle wi~.l be more than 15%. The instrument is f ed from three of the KBS-0-0.5 type batteries during the summer operation of th~ instrument and KBS-Kh-0.5 in the winter. The ~ rated feed voltage is 13.5 volts. In order to indicate the on condition and to check the voltage of the battery, a M4283 type indicator is used. In spite of some complexity of the process of ineasuring the complex value of the input resistances of the line, the IKS greatly facilitates and accelerates tiie processing of the lines, insuring good quality of the high frequency , channels. 6.5. High-FYequency Oscillator (VIG-3) In order to record the level diagram on the distributing feeders and also to measure the modulus and the angle of the input impedances of the feeders, the VIG-3 type high-frequency measuring generator can be used. The oscillator permits voltages of the carrier frequencies of 18 and 120 kilohertz to be fed to the line simultaneously to pick up the level diagram of the channels or - sections of the channel. It is connected to the distributing feeder gap instead of the feeder protectors at the transformer substations. In contrast to the IKS, the VI~3 feed is realized from the AC ne~work (the intake power is no more than 25 watts), which limits the region of its application. The structural diagram of the VIG-3 is depicted in Fig 6.7. The instrument is made up of the 78 and 120 kilohertz oscillators, a transformer designed for connection to the line and therefore called a measuring transformer, devices which measure the high-frequency voltage at the output of the line " and the current in it and also a phasometer. The feed unit is common to all of the modules of the circui~~, and it is a _ rectifier with stabilizer, at the output of which a DC voltage of 12.5 volts is maintained. 205 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAi. USE ONLY ~ 1 ~ 31' ~NOI!(N. rtnsm ~H~. ~/vyuT~ 7BM'q ycunu 7B~r!'q - ~2) (3) (4) (5) ~na aNep. ~ude numoH (6) mp p p (8) . 3~ Afou~x. u~wn � ~ r~7i~-u yau~a ~ 120~rrq ~~'p z a~M~14) Figure 6.7. High-frequency VIG-3 oscillator Key: 1. "/8 kiloherta master oscillator 8. F.eeder 2. Power amplif ier 9. 120 kiloliertz master oscillator 3. 78 kilohertz filter 10. Power amplifiPr 4. FNCh-4 low-frequency filter 11. 120 kilohertz filter. - 5. Transformer substation buses 12. ~-meter 6. Rec t if ied f eed 13 . Z-met er _ _ 7. Measuring transformer 14. Zmeas The oscillators are identical with respect to circuitry and are distinguished only by the magnitudes of the circuit capacitances and inductances. Each oscillator is made up of a master oscillator, buf~er stage, terminal stage power amplifier the output circuit of which includes a band filter for the correspondiiig frequency filter. The oscillator can give a power of 1.2 watts on a resistance of 100 ohms. Fig 6.3 shows the device by means of which the input impedance is measured, _ that is, the voltage at the input of the line, the current through it and the phase shift angle between the current and voltage. A simple, convenient method of ineasuring the phase angle of the input impedance of the line is used in this instrument. This procedure consists in the fact that a voltage ~s fed to the pointing indicator through a ring _ modulator which in the given case is a controlled rectif:ier. It is assembled from four diodes D1-D4, the signal voltage sources Tpl, C1-C2, R~-R2, the load resistances with the midpoint R3, R4 and the sources of the controlling voltage Tp2, the pr;mary winding of which is connected to the resistors R~-R1~. The amount of a voltage drop on them and, consequently, on the windings of the transformer TP2 is directly proportional to tne strength of the current running through the line. The secondary winding of this transformer is connected between th~ midpoints of the load and the - oscillator, the role of which is played by the resistors R1-R2. It is obvious that in view of the sytmaetry of the circuitry this voltage will be absent between the ends of the resistors Rg and R4. The signal voltage from the Tpl through the capacitor C~ or C2 is f ed to R1, R2. Since the amount of the capacitances is selected so that their resistance on frequEncies of . 78 (C1) and 120 kilohertz (C2) is appreciably ~reater than the sum of the 206 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY resi~~ances R1 and R2 with parallel-included R3, R4, the voltages on R, RZ will - be shifted with respect to the voltage on the windings of the Tpl by 9~�. 'L'I~e pl~u~c meter oper~tes .tn the followin~; w~y. Let ua pr.opose thut 1nHtcnd of the line the capacitor is connected, the magnitude of the impedance of which corresponds with respect to modulus t4 the resiatance of the real line. ~ Then the current through the resistors R~-R1~ determined by the magnitude of the cap~citance of the connected capacitor will be almost purely reactive, and the voltage on these re~istors will be shifted by 90� with respect to phase relative to the voltage on Tpl. This means that with the correctly included windings of Tp2, there will be no phase shift vetween the signal _ voltage on R1, R2 and the controlling voltage on Tp2. Then the signs of the voltage or on the upper end of R1 and the lef t end of the secondary winding of TP2 will always compare. Then we assume that the current strength through R1 and R2 from the controlling voltage is greater than from the signal voltage. Then a DC voltage is formed on R3, R4 with "plus" on the upper end of Rg. This occurs because if the voltage on the upper end of R1 has a plus sign, the controlling voltage opens the diodes D and D4. The voltage from R1, R2 is fed through the diodes to R3, R4. I~ at another point - in time the voltage on the upper end of R1 has a minus sign, then on the left end of the secondary winding of TP2 there will be a voltagE with the same sign, and the current from this winding will go through the diodes D2, D3, opening them and closing the diodes Dl, D4. Since it is stipulated that this current is greater than the signal current, the signal current passes through the diode D3 (where these currents flow in opposite direction) without cutoff and the voltage with the plus sign goes from the lower end of R2 to the upper end of R3. The indicator j~2 connected to R3, R4 indicates the presence of the DC voltage. Thus, if the current through the diodes created by the controlling voltage is suff iciently large, the ring modulator operates as a two-phase rectif ier. It is easy to see that if an inductance is connected in place of the line _ and is not a capacitor, the size of the voltages on R1, RZ and the left end - of the secondary winding of TP2 will not coincide, that is, they will be 180� out of phase. The plus sign will always be on the lower end of R4 in this case, and the indicator pointer will be deflected on the opposite direction in the same amount. _ It is obvious that the input impedance of the line is ~urely active, the ~ phase shift on the ring modulator between the signal voltage and the controlling voltage will 90� (capacitors C1 and C2 are included in the circuit for this purpose), and the constant component of the voltage on R3, R4 resistances. The indicator pointer will remain at zero. For convenience of ineasurement, the type of indicator ~~2 is selected so _ that it will be in the middle of the scale. In this case the total deflection of the indicator pointer in one direction or another will correspond to the phase shift between the voltage and current in the line by +90 or -90� and indicate inductive or capacitive nature of the input impedance of the line. 207 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY . w ~ . _ e- ~h v ~ ~ H N ~ ~ . . ? N w ~ ' ~ ~ ` ' _ ~ ~1 ~ ~ ~w ' i ~ ~ O 0 . ~ ~ o I u ~ a ~ ~ ~ � b ~b ~ a~ ~ ~ ~ N R i , . o~'~~O ~ C N ~ a ~ t 4~ ~ ~ ~ _ ' ~b ~~1 x ' ~~1 ' - ~ ~ ~ . ~0~0~ ~ ~a~ rl . a~ ~ A ~ ~ ti~~ ~ ' N . ~e ~ ' ~ ti ~ ~ o ~ ~ q ~ ~ o ~ ~ , ~ I aH~ ~ ~ ~ ~ ~ ~ ~ ~ ~ ~ y . ~ . _ ~~y i~v ~~N A ~ ~ `..~~J ~ � ~71~ ~w ~v ~ ~ }a . , Gl O . h F+ ~ � . �C . : . � . ~ . . ~ � ~ . � . � " w q ONrI . ~ { N M - ~ C) ."!a ZOO FOR OrFICIAL USE ONLY a ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY '1't?e measurement ol' the input impedance o~ the ltne is tnade by measuring the current flowing through the line, with known and previously established magnitude of the voltage at its input. Since when measuring the phase Zinp ~ of the input a pointing indicator is used with 0 in the middle of the scale, in order to use the entire scale of the same in~licator to measure Zinp~ the meter circuitry is altered somewhat by compsrison with the usual version. The difference in DC voltage is proportional to ~.Y~e magr.~tude of the current _ in the line and the voltage at its input is fed t~ the indicator. The voltage on the line is constant for all values of its input impedance, and the current decreases with an increase in ZinP. Therefore the voltage diff erence to _ which the indicator reacts will be equal to zero for some value of Zinp. For ~maller values of ZinP the indicator will basically be affected by the voltage obtained from the rectifier which is connected through TP2 to the resistances included in series in the line circuit. With an increase in ZinP the current in the line decreases, thQ voltage at the output of the rectifier connected to Tp2 decreases, and then this rectifier is blocked by the voltage formed on R5 on passage of the current from the second rectif ier connected to the output of the generator through it. For monitoring the voltage at the output of the line a voltmetex is connected which is made up of a microammeter N1, diode bridge and resistor R24, R25. [Photo illegible] Figure 6.9. Outside view of the VIG-3 oscillator The accuracy of ineasuring the modulus of the resis~ance and phase angle is no worse than 5%. This high accuracy required separation of the entire measured range of resistances into two subranges: one from 20 to 100 ohms, and another from 100 to 1000 ohms. The phase angle is measured within the 209 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY limits from -90 to +90� in the entire range. 1'he outside of the instrumen~t is shown in Fig 6.9. 6.6. Fault Detector (IPTV-1) _ The detector is designed to determine the locations of short circuits in the = 1ew and high frequency channels on the overhead and underground f eeder~and _ subscriber lines and also on house distribution cixcuits for monitoring the ' presence of high-frequency programs; in order to find the section of line with damage causing an increase in xhe crosstalk between channels; in order to determ.ine the path of damaged underground lines and the location of the hidden wire in house networks. ~ The instrument makes ~t possible to find the location of short circuits in the low-frequency channel of overhead lines from the ground, and in the absence of the interfering effect of the electrical network current f ield on the overhead lines running above the roofs of three to seven story buildings. A short circuit beyond the limiting net resistance with respect to any ef the three channels in the room wires using double lines, for example, TRVK, can . be found with the search coil of the detector at a distance on the order of , 5 to 10 cm from the wire, and up to the limiting resistance on the house network stands at a distance of 50 cm or more. - The operating principle of the instrument is based on the fact that the electromagnetic field of the current of the RT network is picked up by the - search coil, it is amplified and fed to a hea~set. The structural diagram of the detector is shown in Fig 6.10. The search coil has three windings: low frequency and two high frequency tnade in such a way that the inductive ~ coupling ~ccurs only between the high frequency windings. Depending on the position of the channel switch either the low-frequency winding of the search coil is connected to the amplif ier input Qr the output of the two-circuit concentrated selection filter tuned to 78 and 120 kilohertz is connected. On setting the switch to the low-frequency position all of the stages of the detector operate in the amplification mode. When receiving high-frequency signals and setting the switch to the 78 or 120 kilohertz position the last stage performs the functions of a detector, and all the rest, the high- frequency amplifier. �I a.~ ~ ' j ~ ~~NV ~l~ . . I , ,1a D ~ ~ ~ . r ~ ~ ~ ; Bxoa~~~ . ~ ; ~.--o ~ . _ Figure 6.10. Fault detector IPTV-1 Key: 1-- low fre~uency; 2-- input - 210 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FQR ^:~`'ICIAL USE ONLY Tt~e input ~jacks are used to feed the programs of the high-frequency channels to the input of the amplifier through the coupling winding of the search coil. Tlie principle of determination of the short circuit location is based on the Eact that the magnitude of the carrier in the wires at this point clianges sharply. If to the left of the short circuit point the current ha~ ' significant magnitude exceeding the opetating value of the current, then to ttie right of this point the current in the line decreases in practice to 0. When working with the detector this is manifested in the sharp change in strength of the sound on advancement of the search coil along the line past the short circuit point. The short r..ircuit on the line causes different consequences for the sound frequency currents and the carriers of the high- freqsency channels. On the sound :Erequencies the current increases by compar- ison with the operating value over the entire section to the left of the short circuit point. On the frequencies of the high-frequency channels in the presence of a short circuit as a result of reflection of energy in this segment, standing current and voltage waves occur before the short circuit point. In some sections in the presence of a short circuit the current can diminish by comparison with the operating value of the current at the same time as in other sections it increases. However, on any channel there is discontinuous variation of the current at the short circuit point, that is, variation in volume of the sound in the detector headphone. Tlle detector has the following qual.ity indexes: a sensitivity of 40 micro- amps wi.tk~ inductive coupling through the search coil at rated output voltage; _ An output voltage of 1 volt developed in the :ieadphones with a resistance - of 3000 to 4500 ohms; . A reproducible frequency band with resr~ct to the high-frequency channels _ of 300-3500 hertz for nonuniformity of 15 decibels; Coeff icient of nonlinear distortions on the high-frequency channels of 7%. - The detector has two sensitivity adjustments: step by 40 decibels and continuous by 30 decibels. The instrument f eed is from 3 of the 1, 3FMTs-0.25 type elements. When building over overhead and cable lines, house RT circuits and also ~ when detecting faults it is expedient to use the IPRL type detector which - is made up of the IPRL-I �ault detector itself and the oscillator G. The locat~.on of the break or short circuit is fixed by a sharp change in volume of the sound in the headphones of the detector beyond the location of the break or short circuit. The detector detects the location of the following fault: On pole subscriber lines at 15 and 30 volts with accuracy ef +10 meters when it is at a distance of no more than 6 meters from the path of the line and at an admissible noise level from the electric network; 211 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL U5E ONLY Pole and stand distributing feeders suspended at a height of. up to 20 metere with prc~c~ston oF +20 meters when the detector is at a distance of no more ll~aii l.t) mc~ter~ fr~~m thc p~i~h of the ].ine; House wiring laid open or hidden. The precision in this case is +8 cm when _ _ the detector is at a distance of no more than 1 cm from the wall; In secti4ns of underground f eeder lines laid using cable with nonmetallic shielding with precision to 1 meter. The qcality indexes of the detector are as follows: a voltage of 100 milli- volts on the TON-2 headphones, fxequency band of 700 to 1400 hertz with non~iniformity of 6 decibels, coefficisnt of nonlinear distortions of 10% with an output volta~e of 0.5 volts; the detector has step adjustment of the amplif ication 20 decibels deep and the continuous 18 decibels deep, and the detector oscillator frequency is 1000 hextz. 6.7. ITPV-2 Type Triple-Program Wire Broadcast Pulse Meter The portable ITPV-2 instrument [29] is designed to determine the quasimaximum values of the voltages of broadcast programs on the wire broadcast networks. ' Ttie program can be heard on headphones. By using the instrument it is also possible to measure the magnitudes of the sinusoidal voltages at frequencies of 78 and 120 kilohertz and low fr equency in the range of 50 to 10000 hertz. The structvral diagram of the instrument is presented in Fig 6.11. At the input of tt~e W, two symmetrizing transformers are installed for low and high frequencies with different transformation coefficients, which permits - the signals of the three programs to be reduced approximately to the same level at the input of the voltage divider (DH). Band f ilters ~78 and ~120 are included at its output for the cr rier frequencies (the low-frequency filters pertain to the input circuit). From the f ilter output, and when measuring low-frequencies �rom the output of the divid er the measured voltage goes to the input of the wide band amplifier (ShU) which passes a 50-hertz to 200 kilohertz band. The amplif ier ioad is two detectors. The first is - the pulse meter detector (DI), and the second detects the AM oscillations of programs II and III. From the output of the second detector the sound _ monitoring detector (DZK~ and when listening to a low-frequency program from the output of the wide band amplifier, the low-frequency voltage goes to the low-frequency amplif ier which insures a level sufficient for normal operation of the hea~phones (T). The detector of the pulse meter is loaded _ on the measuring bridge (IM) with a microammeter, the scale of which is calibrated in volts. In the absence of a signal the bridge is balanoed and - the pointer of the instrument is at zero. When a signal arrives, the balance is upset and the pointer is deflected proportionally to the maximum value of the voltage. _ 212 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 _ FOR OFFICIAL USE ONLY ~.5~_~~~ ~ - r-~--~---------r-- ~ T ~ - ~ ~ ~~an ; 3~r p yHV . 1 _ ~ - drea B9 ,qy ~q m~B G'19 JjJI //,N , (1) ~3~ 4) ll.,..._..J ~6~ ~ 6 . - � . 9B (10) Figure 6.11. ITP-2 pulse meter I~ey : ~ 1. Input 6. ShU 2. P1 7. Low-frequency amplifier 3. low frequency 3. DI _ 4. DH g. IM 5. DZK 10. B, 9 volts The limits of ineasuring the voltage of program I are as follows: 10, 30, 100 and 3.00 volts; the ttigh-frequency programs: 0.5, 1.5, S, 15 and 50 volts. 'The measurement error does not exceed +5% (on the 50 volt scale the error is +7%). The input impedance of the instrument in the frequency band of 50 to _ 10000 hertz is 12 kilohms; for the high-frequency channels with a pass band ot every 10 kilohertz, 3 kilohms. The crosstalk between the high-frequency channels is -36 decibels. Th~ noise - protection of the high-frequency channel from the low-frequency signal is 70 decibels. The integration time when feeding the low-frequency signal to the input is 30 milliseconds with 85% f idelity, and when f eeding the high- frequency carriers modulated by a frequency of 1000 hertz to the input with ~ m=70% the integration time is 50 milliseconds with 80% f idelit~. The power supply for the instrument is from a 9 volt battery;~the intake current is 10 milliamps. In combination with the PZK-1 type sound monitoring attachment which has an amplifier, speaker and battery, the ITPV-2 permits loudspeaker sound monitoring of broadcast programs. The outside of the instrument is shown in Fig 6.12. 6.8. Monitoring Receiver (KPU) The KPU [mor~itoring receiver] is the highest quality instrument designed to measure the qualitative and technical indexes of the low-frequency and high- frequency channels of the system and permitting measurements of the normalized parameters with respect to quality class I. In order to perform all of the required measurements the instrument has two operating modes: in one mode it performs the functions of the high-quality monitoring receiver of AM signals, and in the other, it is a three-band, - multilimit selectivP millivolt meter with symmetric input. 213 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY [Photo illegibleJ Figure 6.12. Outside of the ITPV-2 pulse meter Eeginning with ehe problems of ineasuring all of the quality indexes the KPU , contains the following assemblies: the amplifying channel of the receiver, attenuator, low-frequency and high-frequency filters for various purposes (including filters for separate measurement of background and noise), the symmetrizing low-frequency and high-frequency devices, the amplifying channel - of the voltmeter and the sound monitoring, the switching devices and power supply. In order to perform the set of ineasurements crosstal~c, noise, background, frequency characteristics with respect to the envelope in the modulating - frequency range and in the high-frequency and low-frequency cha~.inel bands the following instruments and devices are required: symmetrizing transformers, lineman's indicator, the Kazakhstan receiver, the GT Avrora, the tube volt- meter, cathode repeater and filters for separate measurement of background and noise. Al1 of these devices are replaced by one KPU instrument, the structural diagram of which is presented in Fig 6.13. The input circuits of the KPU are made up of the SU-VCh high frequency and SU-NCh low frequency symmetrizers, the AT1 attenuator and the PF78 and PF120 band filters, The SU symmetrizers make it possible to obtain symmetrizing input of the instrument and, in addition, the SU-VCh has additional selectivity with respect to the signals of the low-frequency channel. In order to insure the possibility of ineasuring voltages in a wide range from 0.25 to 300 volts, an 8-step attenuator with attenua.tion in the limits from 0 to 80 decibels is used. 214 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY Each band f ilter has a noiseproofness of 60 decibels wbetween the high- frequency channels. When measuring the low-frequency channel the required noiseproofness (30 decibels) from the high-frequency channels is insured by the FNChl low-frequency f ilter. When measuring the background level, the _ FNCh2 low-frequency filter is included which cuts off the frequencies above 200 hertz and has attenuation in the 200-1000 hertz band equal to 22 decibels. - In order to measure the noise level, the high-frequency filter is included in the circuit which cuts off frequencies below 200 hertz having attenuation of 21 decibels in the frequency band of 50-100 hertz. - The high-frequency amplifier is four stage. It is used to amplify the signal to the amount suff icient for linear detection. As a result of the application of negative feedback in the f irst two stages the high-frequency amplifier has high input impedance required for norma.l operation of the band filters. The double halfperiod detector insures high linearity of loading the high- frequency amplifier and improves the suppression of the remains of the carrier frequencies and their harmonics. " The low-frequency amplif ier is single-stage. Its load is the FNCh3 low- frequency filter. The UNCh2 low-frequency amplif ier is three-stage with ~ommon amplification coeff icient of about 140. It amplifies the voltage to - the rated output value of 0.775 volts. It has low output impedance and is _ loaded on the attenuator AT2 of the level indicator. The voltmeter amplifier W is four-stage, wide-band. It has a total amplifi- cation coeff icient of about 1000. The rectification circuit is a bridge ~ circuit. A microammeter for 100 microamps, type M265, is connected to one of the diagonals of the bridge. Part of the voltage of the UV voltmeter amplifier is fed to the monitoring amplifier UNChk which is made of 5 transistors and is loaded on the 1GV-1 speaker for listening to programs and interf erence. The power supply for the KPU can either be from KVS type batteries placed in the instrument case or from the AC network. The power pack is made up of the step-down power transformer, filter rec�3fier and voltage stabilizer. The IP indicator monitors the inclusion of the instrument and the magnitude . of the feed voltage. In order to include the instrument there is a flipflop switch 8B1 Pitaniye [feed]; for switching power supplies there is a toggle switch 8B2 Rod Pitaniya [type of feed]. The current intake by the instrument when powered from the battery is 55 milliamps. The power intake from the - AC network is 4 volt-amperes. 215 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY ~ r._..__~_~'____j-_~~~:..:...:~ - . ~ ~ ~ (lo)~ ~ , ~1) ~ i wru ~ �'95-u1 ya"V . . _ `k.r. t 1 ~ ~~v 1 t' tl ' V 8 ~,i; ~ f~ ' I 1i l0 L - '"'r""j; , ~o a ~?t~ p~a-73 6 ~ ~ . ~~l~ ~ t-8/B Yz~~ ~ . y, _ ~ " _ .1 � ~ ~ . 1 , A'UN0~1 ~ _ ' ~ . (2) ` ~ ~ _ , . , 9-~~, ~e~ti nn. . ~ ! 16 5-~ _ . - S-e1 ~ ~ 9 I I , ~ ~ r0 . o~ Is ~ s ~ 1 9~ ~ 1~ I~ ~ y ~ ~ . ~ ~ 1 Pc~~~l ~e ~ . ~ ~ 1 j : . . , Od~nms~ f Yo ! ~8y j , 1 I . ~3 ~ ~ ~ansm~0 ~ 1 ~ j " ~ ' ~ ~ ~4~ ~-----+----+~---Z--~----~------ - ' - - . . ~ . . . ' _ . . ' i � 1 ~ ~ . ' ' . . ~ . , y . ~ /lam~i~e I~, Pcd ~um~n~ ~6~ - ~ . Z . . . . ~ ~l 6ao~r num~arua ~ ~ . . . . ~ . B-B1~ 'v~ ~~~16~ _ . . ~1 1 A , cs~ . ~ : I~ . : . L--- B-Bl N11 . . . ~ . - ' ~ . ' . . ~ Figure 6.13. I~Ieasuring rece~iver KPI3 Key: 1. Input 2. Channel 3. Type ~f operation - 4. Filter~s ~ 5. Power supply ~ 6. Type of feed 7. Power supply module 8. 220 volts 9. 135 volts 10. High-frequency amplifier 11. Calibration 216 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFIGIAL USE ONLY _ � � . 12 � 13 s~ry, D~ ee,x~~ (14) ~ i~' ' ~ � ~ q ? . . . - S?B 6 ~ ~ ~ t. E ~ � ' ,s : e' i;3 ' ? . N/l-1 : . . ~ � . t i?~ A ~ . , ~0~'15~ a B . ~ ~ ~ . . ' ' ~ . . - ~ . . ~~~i ~ K, rpc~?xocmE (16) . - ~ . . _ . % ~ . . , . . ~~~r~... ~ ~J ~ . i ~ ' ~x ~P . ' . _ ~i .s . [Fi~ure 6.13] 12. Low-frequency filter 13. Low-frequency amplifier 14. Output - 15. Calibration 16. Volume - 217 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY For separate ~xplanation of the operation of the instrument let us consider two operating modes separately: 1-- Vol'tmetr [voltmeterJ and 2-- Priyemnoye ustroystvo [receiver]. In the first operating mode the KPU makes it possible to measure the eff ective values of the AC voltage of all channels from 10 millivolts to 300 volts in the frequency bands from 50 to 10000 hertz, 68-88 and 110-130 kilohertz; the effective values of the carrier voltages of channels II and III in the presence of tone modulation or modulation by - tiie broadcast signal with the carrier level ad~ustment included on the trans- mitters; the modulus of the input impedance for frequencies of all channels. In addition, in this mode the KPU permits the performance of the following: separate measurement of the background and noise voltages of the low-frequency channel to 75 decibels; measurement of the frequency characteristic in the band of each channel, listening to the broadcast program of the low-frequency channel. The Ka.nal [channel] switch is used to select one of three channels. The instrument has the following voltage scale: 30, 100 and 300 millivolts; 1, 3, 10, 30, 100 and 300 volts. The measurement error is no more than +6~; the nonuniformity of the frequency characteristic is 2 decibels. When measuring the voltages the low-frequency signal goes to the low-frequency symmetrizers SU-NCh, from the output of which the voltage is fed through the attenuator AT1, the groups 5-V1V of the type of operation switch, the FNChl low-frequeno.y filter, the KK correction circuit, the S-V1V type of operation switch group, the 2V1V channel switch group, the SVla and 5-Vlb groups to the input of the W voltmeter amplifier and then to the rectification circuit of the IP1 microammeter, type M265, calibrated in millivolts (volts). When measuring the voltages of the high-frequency channels the signal goes to the input of the SU-VCh device, then to the attenuator and to the correspond- ing f ilter which insures the required selectivity. From the output of the filter the measured voltage goes through the 5-Vla and 5-Vlb groups to the UV and the instrument. In the second operating mode the~instrument makes it possible to measure the following quality indexes with respect to quality class I and II: the frequency characteristic, inter.ference protection of the high-frequency channels, background and noise voltage, and by means of the nonlinear distor- tion meter, the harmonic coefficient. In this mode with a sensitivity of the instrument of 25 millivolts the output voltage is 0.775v. The voltmeter has 6 scales: from 0 to 3, 10, 30, 100, 300 and 1000 millivolts. Its basic error is +6%. The nonuniformity of the frequency characteristic of the instrument is 2 decibels, the harmonic coefficient is 0.5%. The noiseproof- ness between thp high-frequency channels is 77 decibels, from the low- frequency program 105 decibels, from the radio broadcast band on frequencies . - above 180 kilohertz, 70 decibels. 218 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY The signal to be measured goes by means of the 2-V1 channel switch "78" or "120" to the input of the high-frequency sysumetrizer SU-VCh and then to the AT1 attenuator and the PF 78 or PF120 band filter. Then the signal is amplified using the WCh high-frequency amplifier, it is detected and again amplified with respect to low frequency (UNChl). The setting of the required sensitivity (calibration) is made by ad,justing AT1 (rough) and variation of the amplification coeffScient UVCh (smoothly). Here the IP1 instrument is = connected by means of the switch B2 to the output stage of the high-frequency amplifier. From the output of the UNChl low-frequency amplifier the signal goes through - the FNCh3 low-frequency filter.s, the 5-V1 switch group and the FNChl low- _ frequency f ilter, the KK circuit, the 5-V1 group to the UNCh2 low-frequency amplifier connected to the "output" terminals. The voltage at the output of the KPU is measured by a built-in voltmeter which is made up of the attenuator AT2, the K-circuits (K1 and K2), the rectifier B and the instru- ment calibrated in decibels. Depending on the type of ineasured parameter the "filters" switch is set to the required position and the following measurements are made: - 1. In the ShP position measurement of the harmonic coefficient of the ~ amplitude of the modulated oscillation of the high-frequency channels and - pickup of the frequency cha.racteristics with respect to the envelope. In ' this case the KK is included and the pass band of the receiver is 50-10000 hertz. In order to measure the harmonic coefficient, the harmonic analyzer or coefficient of nonlinear distortion meter is connected ta the output terminals. 2. In the "background" position measurement of the background voltage of the high-frequency channels. In this case the FNCh2 filter is included, and the pass band is limited to frequencies of 50-100 hertz. - 3. In the "noise" position measurement of the high-frequency channel noise. In this case the FVCh high-frequency filter is included, and the band is 400-10000 hertz. 4. In positions 1 and 2 kilohertz the measurement of the croSStalk in each high-frequency channel. In this case the narrow band f ilters K1 and K2 are included respectively, and only the voltages at frequencies of 1 and 2 kilohertz are measured. The presence of noise interfering with the _ - measurement is determined by using the acoustic monitoring channel in the "loud" position of the volume switch. The outside of the instrument is shown in Fig 6.14. , 219 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY [Fhoto illegible] Figure 6.14. Outside of the KPU 6.9. Channel Monitoring Device (UKT) The UKT channel monitoring device is a portable instrument which can be used for checking and tuning the channels of the TPV network, to check the fitness of the GT at the subscribers and the GPTV. The 1000-hertz oscillator in the UKT can be connected to the UPT~I-200 transmitter and it is possible to check the correctness of the regulation in it of the suppression of the carrier and depth of modulation. Rigid requirements are imposed on the portable device with respect to weight and economy when fed from a battery. Therefore the UKT circuit is appreciably simpler than, for example, the VIG-3 . oscillator, but the simplif ications are achieved at the expense of some loss of precision and stability of the instrument. The structural diagram of the UKT [35] is presented in Fi~ 6.15. The device is made up of the master oscillator (ZG), the low-frequency 1000-hertz oscillator (GNCh), the power amplifier (UM), multivibrator (MV), the meter that measures the modulus of the input impedance on carrier frequencies, the Z-meter, rectifier, and stabilizer of the DC f eed voltage. The oscillation _ frequency of the master oscillator ZG (&8 or 120 kilohertz) can be switched both manually and automatically using the MV multivibrator. The multivibrator controls the relay which, in turn, connects (or disconnects) the capacitors - to the oscillatory circuits of the ZG and UM. The frequency is switched every 6 to 9 seconds. This time is entirely sufficient to measure the level on the line using the lineman's indic~3tor. The amplitude modulation of the carrier frequencies is realized directly in the master oscillator itself without an additional modulator by feeding a _ voltage from the output of the GNCh low-frequency oscillator to the emitter circuit of the transistor. The AM mode is used to check, without meas+iring ~ the quality indexes, f itness of the GT and GPTV. The voltage of the GNCh 220 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY can be used also for other purposes. For example, on connecting its output to the transmitter it is possible to check and adjust the depth of modulation, the degree of suppression of the carrier. The modulus of the input impedance of the feeders is measured in the usual way: a current or defined magnitude (calibration) is fed to the line, and then the voltage drop on the Zinp line is measured. The two-limit scale of the meter is calibrated directly 3n ohms from 0 to 100 and from 100 to 1000 ohms. In the UKT, the M24 microammeter for 100 microamps is used. The device is connected to the line in parallel, but so tha~ the band-elimination filters ZFR separate the UKT from the low- frequency station amplifiers. ~9) ~8 ~ 3r y~ Da~xod oy rt /1M ~5) ~6) ~7) ~ /'yy M6 Z-,~ ' _ e~,Xaa yy ~4~ . . ~208 B ~ t 188 ' ~ 2 ~ BNtul~tua `l~ ~3 ~ _ ucmowyuK . Figure 6.15. Device for monitoring channels - Key: 1. Outside power supply 6. MV 2. 220 volts 7. Z-meter 3. 18 volts 8. High-frequency and AM output 4. Low-frequency output 9. UM power amplifier 5. GNCh 10. ZG master oscillator The parameters of the device are as follows: the o.utput power on the carrier frequencies on a resistance of 300 ohms is 1 watt; the voltage of the GNCh is 2 volts, the hig~-frequency on a load of 1500 ohms is 2 volts. The operating frequencies are as follows: 78 and 120 kilohertz with precision of +1.5%, 1 kilohertz +20%. The continuous adjustment of the high-frequency signal level is no less than 20 decibels. The measurements of the modulus of the input impedance of the RF distributing feeder on carrier frequencies are within the limits of 10-1000 ohms+l5%. The instrument is powered from the AC, 220 volt network or 3 to 4 KBS batteries with a voltage of no more than 18 volts. 6.10. Test Signal Pickup (G-78/120) In order to tune the individual and group receivers and intermediate amplif iers, - a special AM oscillator is required with higher quality indexes. The 221 FOR OFFICIAL USE ONLY , APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 - FOR OFFICIAL USE ONLY _ G-78/120 pickup is a source of AM signais made up of two independent carrier frequency oscillators identical with respect to circuitry and a common power pack. The structural diagram of the sensor is shown in Fig 6.16. The amplitude modulation of the carrier frequencies can be realized either by an external low-frequency oscillator or internal with modulation fre- _ quencies of 1000 hertz and rated modulation depth of 70~. Each oscillator _ is made up of the master oscillator with quartz stabilization of the frequency and a modulator executed by the circuitry of the two-cycle amplifying stage with modulation in the emitter circuit. At the output the oscillator has - a continuous amplification regulator which provides for regulation of the output voltage within the limits oi 15 decibels and a step voltage regulation switch for 0.1, 0.3, 1.0 and 3.0 volts (for the DPU). The power supply for the pickup is from the 220 volt AC network. This volt~ge is rectified and stabilized with respect to the DC voltage by a parametric stabilizer. As the source of the low-frequency signals it is possible to use any sound frequency oscillator with output impedance of 600 ohms. The basic parameters of the - pickup are as follows: modulating frequency band 20 to 15000 hertz with non- - uniformity on the higher frequency of 3 decibels, harmonic coefficient of 0.5% in the 20-6000 hertz band, background level 65 decibels, signal/noise ratio with mutual connection of the outputs of the two oscillators to the common load of 70 decibels, power intake from the network 3.5 watts, mass of the instrument 2.5 kg. ~ - ~1~ ~B~ ~2~ Aloayn. Oy OscmD ~3~ ' 4 ` . ~ B,v!~ir,/;~~JrN,~A d~t6/,CG~.9lJUA/ . � w~~~�:;anuA Hv dxe9 (8) _ ln~r~ Bod AyuA rrcuw. ~rc-yux~6~ Gxn~ (8) _ . ~4~ I~ayuta~r~5~ : ~ l20KPy Mods,n. OqOe~roD~10) ~ ~ ' . ' ---ir.;~' . . t - ~ ~ � ~ � ~(i yum~Qa G~Rb (12) . ~ . . Figure 6.16. Test signal pickup Key: 1. Low-frequency oscillator 78 kilohertz 8. Low-frequency input 2. Modulator 9. Low-frequency oscillator 3. High-frequency output 120 kilohertz ' 4. Internal modulation 10. High-frequency output 5. Carrier 11. Power supply 6. External modulation 12. Electrical network 7. 1 kilohertz oscillator 222 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 Fok orr'ICIAL USE UNLY 6.11. Measurement Panel of the Distributing Feeder k~ame (PI-STR) The measurement panel is built into the STR-5 distributir~g feeder frame installed on tr~3nsformer subgtations for remote control and monitoring of tl~e operaClon c,f tl~e trnnHf.ormer aubstationa af large citie9 with triple- " program wire broadcasting. The measurement panel provides for the following: measurement of the signal level of all three programs, measurement of the modulus of the input impedance of each feeder (to 10) on the signal frequencies of the three programs, measurement of the quasipeak value ef the envelope of the modulated signal of the second and third programs. All of the measurements are performed without interrupting broadcasting over the distributing feeders. The levels are measured simultaneously with respect to three programs. This is achieved as a result of daing away with - the pointing indicators and using a cathode ray tube as the indicator. Another characteristic ot the PI-STR panel is the fact that thE modulus of the input impedance of the feeder is measured not by using special oscillators, but on the broadcast transmission currents of the low-frequency programs and the carrier frequen.cies of the second and third programs. The structural diagram of the panel when measuring the program levels is presented in Fig 6.17. The voltage from the STR-5 buses goes to the input device which insures the possibility of connecting three filters to the buses: low frequency trans- mitting the signal of I and two band filters at 78 and 120 kilohertz. The voltage from the output of the filters goes through the preset regulators to the integrators (IU). Their purpose is to insure measurement of the level - by the procedure established by MRTU-1029-66 specif ications. According to _ this procedure the integration ti.me (the minimum sigtnl duration, the level of which is reckoned with 90%+10% fidelity) is equal to 10 milliseconds, and the capacitive discharge time is from 3 to 4 seconds. The integrator - satisfies these requirements. It includes two amplif ication stages (emitter repeaters), detector and integrating circuit. All th�ree devices are identical. - From the output of the integrator the voltage goes through an electron switch to the vertical deflection amplif ier (WO) but only in the case where the switch is not closed. The switches are controlled by an electronic commutator and pass the signal from the IU [integrator] alternately. The switching speed is 100 times per second (twice the electrical network voltage frequency). The UVO [vertical deflection amplifier] amplifies the signals arriving from any IU and transmit them to the vertical deflection plates of the cathode ray _ tube beam. With respect to horizontal the beam is deflected by pulses obtained from the same electronic commutator which controls the switches. The deflection (scanning) is realized so that if the first program switch is opened, the bea.m is not deflected, but remains on the left side of the screen. When the second switch is opened (the f irst one is blocked), the beam deflect~ jumpwise to the middle of the screen, and on blocking the third switch, farther - than the middle. In addition to the pulses, an AC voltage (from the network) is fed to the horizontal deflection plates, deflecting the beam so that instead of points from the beam on the screen dashes 5 to 10 mm long appear. This facilitates reading and increases the service life of the cathode ray tube. A transparent mask is fitted to the cathode ray tube screen with three 223 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY scales plotted on it calibrated in effective volts. By these scales and ~ tl~e m~ximum beam deflection the program levele on the STR-5 buaea are reckon,ed. Wlien the electronic switches operate the transient processes influencing the degree of deflection of the beam occur. These spurious beam deflections can be per~eived by an observer as a variation in the signal voltage. However, even if the observer, knowing the origin of this interference, doea not , notice them, they still complicate proper reading of the level with reapect to the beam position. In order to facilitate reading, the beam is ext~n- guished during the switching time of the measured channels. In order to extinguish the beam pulses are fed to the modulator of the cathode ray tube. These pulses are obtained ~in the electronic commutator. The integrators, electronic switches and commutator are made of transistors, and the vertical deflection amplifier ls made from the 6N2P tube (the magnitude of the voltage required for the beam deflection reaches 200 volts, and industry still does not produce the corresponding transistor). ~3) . ~ trr~l Nyl ~n, Rp 9A'1'~14) ~r ~R 4 : ~ ~ : ~r;J ' s Hy~l lfn, y80 _ Fr, , j , ~1~ ~ ~13) ~11:1 ~ f!'/~ /f/I~ . o . . ��~12~ ,~/!Z/l~lpD.NH611L . . _ . aoM,~y~ramop ` Figure 6.17. Structural diagram when measuring program levels - Key : 1. STR-5 buses 11. Switch 3 2. Input unit 12. Electronic commutator _ 3. Low-frequency f ilter 13. WO [vertical deflection amplifier] 4. Band filter 78 kilohertz 14. Cathode ray tube 5. Band filter 120 kilohertz 6. Integrator I 7. Integrator II 8. Integrator III - 9. Switch 1 ~ 10. Switch 2 _ The structural diagram of the PI-STR when measuring the quasipeak values of the envelope of the modulated signal is presented in Fig 6.18. In contrast ~ to measuring the signal levels, the measurement of the level of the envelope is made not simultaneously with respect to two (II and III) programs, but in turn. The program is selected manually by the switch B. The electronic commutator does not operate in this case, and the magnitude of the corresponding DC voltage deflecting the beam horizontally is established by the variation in position of the switch B. The high-frequency voltage \ from the STR-5 buses goes through the input de�~ice, the 78 and 120 kilohertz filters and the switch B to the input of the amplitude detector. At the 224 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY output of the detector a low-frequency voltage is obtained, that is, the same envelope, the voltage of which must be measured. Then the low-frequency volt~igc i~ fed to the integrator, And from its output thew puleating voltage is fed to the vertical deflection amplifier and then to the deflect- ing plates. " , . _ - , (2) �'-'d R~ ~ B ~4~ 5) ~b) '~7) R . Z ~J Hy se9 /Y ~~ae � Rs ,p . . , ~1~ ~3~ - . , . Figure 6.18. Structural diagram of ineasuring the envelope level Key: 1. Input device 5. Detector 2. F-78 band f ilter 6. Integrator 3. F-120 band filter 7. Vertical deflection amplifier 4. Switch . - r0~ 1 1 B B,x,: ~ Br . ~ ~f ~ - B~ 1 ' 1 ~i .C" t I/ , ~ 1'r ' -0~ N ~ (lo) � i ? ~ ~~'3 ll.r. d; ~r~ 7::. ~ ,rA, . ~ i ; ~ ~ i 12~ ~ . yv9 , ~ rOt t 1 I B>r';: IR A;]~ - ~ Ama G ~ g''- � ~~.b,~,' ~ . . ~l, ~1 E, 11. ll~ I ~ Z,s~ , ~,.;�i~ i~p~ a ~ rr7.'.'~ ~ I~ 1 1 �:c~ z- ~ ~ ~3i ~ i ~ ~ d i ~ ~1~ � m ~r~ ~r'!~'' ~ ?-i-----J--i-----J ~ ~ 'y-~P i~5) ~3~ t s ~0~,. ~,V,-: . f , L_~ ~ nua N . , . ~6~ Figure 6.19. Structural diagram of monitoring the constancy of the input resistance modules of the feeder lines Key: 1. Measuring f eeder 10. Integrator 2. Measuring transformer 11. Switch 3. Resistance box 12. WO vertical deflection - 4. Att amplifier - 5. From the shaper 6. Electronic commutator 7. PFNCh low-frequency band filter 8. 78 kilohertz band f ilter 9. 120 kilohertz band f iler 225 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY The modulus of the input impedance of the feeders is measured by the structural diagram in Fig 6.19. In this caee the voltage goes to the feeder from the buses of the transformer substation through the measuring transformer and the resistor R1. A circuit made up of the resistor R2 and the resistance box is connected in parallel to the autput of the measuring transformer. The magnitude of the'resistance R2 is 20 times that of R1. If the resistance is set on the resistance box so that the drops on both resistors will be identical, this means that the resistance of the box is 20 times greater than the input impedance of the feeder. Thus, in order to measure the modulus of the input impedance it is necessary, awitching the resistances of the box, to equalize the voltage drops on R1 and R2 and reckon ZinP of the feeder by the box scales (a difference of 20 times is considered during calibration). The voltages are measured on the resistors just as the program levels are - measured. The voltage is~fed through the switches and the transformer to the filters which pass the currents of the program, on the frequency of which the measurements are made. On the programs II and III, measurement is made an carrier frequencies, and on program I, in the frequency band of 400 to 800 hertz. Although the operating rules require performance of the measurements of Zinp only on a frequency of 400 hertz, if the filter band of program I is made very narrow, the voltage at the filter output will be small, and the greater part of the time it will not exist at all, for the voltage components with a frequency of 4-0 hertz in the spectrum of the broadcast program occur rarely. Therefore in order to facilitate the measurements the filter band is made relatively wide. From the f ilter output the voltage goes to the integrator, and then through the electronic switch and the vertical deflection amplifier, to the cathode ray tube plates. The electronic commutator alternately includes the switches and simultaneously shifts the beam horizontally. In this case two strips - will be obvious on the screen of the eathode ray tube which move vertically in accordance with the broadcast transmission level. Turning the switch of the resistance box, it is necessary to set it to the position in which both strips will be at the same height, and then read the modulus of the input ~ resistance of the feeder by the box scale. The PI-STR is a highly accurate instrument; its error in the mode of - simultaneous monitoring of the dynamic levels of all three programs does not - exceed +10%, and the additional error as a result of the presence of the voltage of additional programs does not exceed +4%. The values of the moduli of the input resistances can be measured with an accuracy of +10% in the range from 160 to 1000 ohms and with an accuracy of +10 ohms in the range from 30 to 100 ohms. The structural design of the PI-STR provides for the installation of the panel on the STR-5 frame without any adjustments. If the modules for monitor- ing the programs, measuring the input impedance and the pulse meter are - installed in advance on the frame, it is necessary to remove them and install the PI-STR panel in their place. The panel f eed is from the STR-5 feed module, but since the cathode ray tube and the transistorized stages 226 - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY require additional rated values of the stabilized voltage, an additional feed module is installed on the PI-STR. 6.12. Problems of Introducing Meters The above-enumerated instruments do not completely correspond at the present time to the operating needs. One of the main peculiarities of the triple- program wire broadcasting is the use of a variable carrier. This factor gives rise to signif icant difficulties in measuring the voltage distribution on tlie wire broadcast networks. The instruments used quite precisely measure the voltage if the carrier is tone modulated, that is, when the carrier remains constant. The tone line measurement can be made when the TPV net- works in the given region have only just been created. However, when the network has already begun to operate, it is inadmissible to carry out the current tone measurements for entirely understandable causes (preventive, operational or operative). It is possible to say the same thing about the measurements when searching for damage and determining the degree of influence on the voltage distribution along the f eeder of the newly connected leads. The readings of the voltmeters the lineman's indicator and RTPV-2 essentially depend on the nature of the broadcast transmission (voice, music), and they can lead to invalid conclusions. This leads to the necessity for making individual measurements. The creation of an instrument, the readings of w!Zich will not depend on the level and nature of the broadcast program appears to be difficult. Therefore it is more expedient periodically to change the operating conditions of the transmitter: to convert it for some . time to operating conditions with nonregulatable carrier. Then during this time the carrier will be constant, and by the readings of the instrument reacting to the existing voltages it is possible quite precisely to d etermine the transmissian coeff icient of the various elements and the level distribu- tion on the network. The disconnection of the carrier regulation, however, is connected with an increase by 20 decibels of the crosstalk interference on ttie high-frequency channels from program I which can turn out to be noticeable for the subscribers. The noticeability of the crosstalk can be reduced to the minimum by reducing the time during which the~transmitter con- ditions change. It is obvious that this variation must be of a periodic (pulse) nature. The pulse duration, the buildup and decay fronts, the repetition periodic ity are to be determined by theoreticaly and experimental work. . It is also necessary to develop and install the corresponding auto- matic devices in the transmitters that have already been produced and newly developed. There is a theoretical possibility of determining the transmission coefficient of the lines and the devices by measuring not the maximum values of the signal, but the residue of the carrier frequency voltage in the intervals (it does not depend on the level of the broadcast programs). This measurement procedure does not require introduction of an automatic device into the ; transmitter, periodic disconnection of the regulatianof the carrier, and it does not lead to .an increas~ in the crosstalk interference. 227 ' - FOR OFFICIAL USE ONLY i ~ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY At the present time the problems connected with the development of the AM signal generator to measure the high quality indexes of the individual channels and the TPV devices have been basically solved. There is a necessit,y for oscillators vf three types: a) High quality (standard) oscillatorsfor checking the KPU; b) Oscillators required to organize the production of the receivers and amplif iers; - - Oscillators designed to check out the fitness and simple repair of the receivers and the DPU at the point of their installation. These instruments have been developed. The first type includes the modulated attachment, the second type includes the generator and the test signal sensor and the third type, the device for monitoring the UKT channels. The KPU monitoring d evice which permits measurement of the quality indexes of the transmitter and subscriber point channel will sati~fy the operating needs. In order to measure the complex resistances of the lines and lthe devices, the PI-STR, IKS, VIG-3 and UKT instruments are used. The PI-STR and the . VIG-3 instruments are stati4nary. A deficiency of them is the fact that they mea~ure the input impedances only on the carrier frequencies. There is a necessity for developing a stationary instrument which will permit _ measurement of the r esistance in the entire frequency band of the high- frequency channels, which will permit more exact and complete estimation of the quality of processing the TPV networks. A similar goal is being fulfilled by the IKS instrument, but the measurement of th~ resistances with this help is inconvenient, and errors are possible in the recalculations. The measurement of the resistances by the VIG-3 instrument is much more convenient and more precise. It is expedient to develop a new instrument in which the advantages of the both instruments will be combined. The operative measurements that do not require high precision when processing the lines, when searching for and eliminating failures on the networks are realized by the portable UKT instrument. - The manufactured IPTV-1 fault finder, although basically satisfying the operating needs, still has a deficiency: when finding short circuit points using the search coil, the sensitivity increases with an increase in frequency. This complicates the search for the short circuit points. It is necessary to develop an instrument which will be free of this def iciency. In addition, usually the lineman carries the IPTV-1 instrumen~ and the lineman's indicator with him when searching for the damaged points. It is expedient to combine the functions of a detector and an indicator in the new instrument. 228 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 = FOR OFFICIAL USE ONLY CHAPTER 7. HIGH-FREQUENCY PROCESSING OF THE LINE PART OF A CHANNEL ~ AND HIGH-FREQUENCY LINE DEVICES 7.1. High-Frequency Processing of Lines In ord er to create traveling wave conditions in the lines for high-frequency signals and match the individual channel elements (MF [main feeder]-TP [transformer substationJ, overhead wires and cable, and so on), it is necessary to carry out high-frequency processing of the lines and channel devices from the transmitting station to the subscriber units. It reduces to inclusion of the devices which provide for transmission of all three programs without nonlinear and frequency distortions and with sufficient level at various points of the lines, and which lower the mutual effect between the channels. The quality of processing the lines using high-frequency devices depends on the parameters of the devices themselves and the precision of matching the various sections of the channel. This quality can be determined by measuring the distribution~of the voltage levels and the harmonic coefficient on the higher modulating frequencies along the line. This type of operation is diff icult; therefore it is nossible to determine with sufficient accuracy the degree of ~atching, measuring the input impedance of the line in the frequency band of each channel, and with respect to the input resistance, the nonlinear distortions. The theoretical calculations and practical measurements have demonstrated that if the modulus of the input impedance on frequencies that are +4 kilohertz away from the carrier differs from the modulus of the input impedance on the carrier itself by no more than 1.4 times, the phase angle will not exceed 15�, then the harmonic coefficient will be no more than 3%. When these conditions are not satisfied, the match- ing must be carried out more exactly. In order to process the distributing and main feeders with leads and cable inserts, passive devices are used which are basically made up of LC-elements. The short f eeder leads kl~d 2. ohma Here n is the number of distributing feeders at the given transformer sub- station (excluding the feeder for the outdoor public address system FUZ, which must be processed by a band-elimination filter). When measuring the input impedance of the transformer substation from the high-voltage side the - lead-in of the ma in feeder is first disconnected from the overhead wires (Fig 8.14). All of the distributing feeders must be connected to cotnmon buses. If the transformer substation has reserve feed with respect to all programs, the measurement is repeated twice: once with the lead-in and the UPTP of the feeder A(basic), another time with the input and UPTP of the - Feeder B(reserve). When measuring the basic complex, the contactor of cell B of the STP scale must be in the nonoperating position ar~3 the door of this cell is open. The IKS instrument together with the ZX terminals , connected to it by two identical inductance coil L1 and L2, the connection point of which is grounded, are connected to wires running to the UPTP input (in cell A of the STP bay). The IKS housing must be grounded. Then _ the armature of the contactor in cell A is mechanically fixed in the pulled position, the door of this cell is closed and measurements are taken. When measuring the complex B the procedure is analogous. Tr.e induction coils are designed to protect the operator and the instrument in the case of random contact of the wires of the distributing f eeder and the electrical network wires. Their resistance to currents of ineasuring frequencies of the IKS is several kilohms and has no influence on the measurement result. These coils are made locally using a ferrite core of the NM-2B30 type with magnetic permeability M=2000, 75 turns and an inductance of no less than 9 millihenries. _ 269 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY - ~ The moduli of the total input impedances of the main feeders on frequencies of 78 and 120 kilohertz are measures of the input terminals of the UPP through which the given line is fed. The transmitters and other UPP are disconnected from the terminals. The terminal 7 is grounded by the require- ments of safety engineering. During the measure~ents on a frequency of 78 kilohertz the IKS is connected to the terminals 3-7 of the UPP; the terminals 4-7 are connected by jumper. For measurements on a frequency of 120 kilohertz the instrument is connected to terminals 4-7, and terminals 3-7 . are closed. The moduli of the input impedancea of the pairs of 3-pair house networks are measured on a frequency of 400 hertz. The input of the measured pair is disconnected from the correspQnding terminals of the GPTV and are connECted - to the ZX terminals of the IKS instrument. 8.7. Electrical Measurements of Quality Indexes of High-Frequency Channels and Parts of Them On the parts of the "transmitter input and actual transmitter load (UPP.input)" channel and the "transmitter input and transformer substation (common buses of the STR)" channels the frequency characteristics, the harmonic coefficieut _ with respect to the envelope and the magnitude of the crosstalk interference from the adjacent transmitter are measured. On the "transmitter input and subscriber radio point of a single pair house network" channel the frequency characteristics, the harmonic coefficient, the magnitude of the crosstalk interference from the low-frequency channel and from the adjacent high-frequency channel are measurad. The measurements must be taken with respect to every high-frequency channel at two subscriber - points of each transformer substation fed from different distributing f eeders. During per iodic measurements the numbe~ of subscriber points subject to measurement is selected from the calculation of H=N/2000, where N is the total number of subscribers f ed from the given OUS, including the single program radio point. The points fed from different transformer si=~�- stations are selected for the measurement. Or~ the "transmitter input and subscriber radio point of the three-pair house network" channel the amplitude characteristics, frequency characteristics, harmonic coeff icient, background and noise voltages and magnitude of cross- talk interference from the adjacent high-frequency channel are measured. The measurements are performed raith respect to each high-frequency channel at one subscriber point of the three-pair house network �ed by the GPTV. During periodic measurements, one radio point each out of M three-pair networks of each Oi?S is selected for measurements, where M=m/5; m equals the number of GP"iV in the given OUS. 270 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFiCIAL USE ONLY The part of the high-frequency channel "transmitter input and actual load" is measured by the circuit in Fig 8.15. The remaining parts of the high- frequency channels beginning with the transmitter input are measured by the same circuit, but the KPU and the nonlinear distortion meter, depending on which channel is measured, are connected to.th.e output of the transformer sub- _ sta~ion or to the subscriber point. ~ ~ r-- 9 -To l , ' ' - - ~ . ~ - , � ~ ~ n~:ram- ~A'!-3 S?1~ ~4) . ' , ry ~ . ~ ~ ~1~ ~ . ~ ~ Xi?-u Srllil ~5~ ~ � Ri ~ ~ I ~ 1 ~ ry!=Z71- _ � . : ~ y, . R ~~o-I1 . . . . . ~ + - -4-~ ~ i . . IPy ~ - q . ~ NA3l Il;l.~l - . . . ~ s V . . j ' . , _ � ' ps ~ . ~ ~6) 90i � . ~ Figure 8.15. Circuit for measuring the parts of the high-frequency channel Key: 1. Oscillator 6. E01 oscillograph 2. 78 kilohertz transmitter 7. KPU 3. 120 kilohertz transmi.tter 8. NNM 4. to the lst UPP 9. E02 oscillograph 5. to the 2d UPP The parameters of the resistors R4, R5, R6 in the given circuit correspond to the parameters of the resistors R3, R4, R5 of the circuit in Fig 8.1. The indexes are measured at the inputs of the first and second groups of UPP connected to the corresponding outputs of thE transmitter. The UPP groups are replaced using the II2 switch. When measuring the remaining high- frequency sections of thp channel the depth of ~adulation and the carrier frequency voltage are monitored using the E01 oscillograph and the V2 voltmeter at the output of the UPP group to which the ma in feeder feeding the transformer substation and the distributing network where the measure- _ ments are taken is connected. The duration of the sendings of the measuring signal in the sound frequency spectrum must be minimal. The checking is done by feeding the signal with a frequency of 50-100 hertz and with a level of 30 decibels below rated - to the input of the transmitter. The presence of the signal at its . connection point is checked using the KPU. 271 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY 'I'li~~ ~~:~~~L.LLuLur l:r.~~c~u~~n~.y Lun.Lng and t~clting ot thc rc~quirc~J ~evr.lt~ ol measuring signals must be carried out when loading the osciilator for the resistor with a resistance equal to the rated input impedance of ~he trans- mitter, that is, for position 2 of the switch II1. In order to obtain a stable value of the output voltage of the oscillator in the frequency band when connecting it to the input of the transmitter (position 1 or 3 of the =~j switch II1) the output impedance of this oscillator must be an order less than the input impedance of the transmitter. When measuring the sections of the channel it is necessary f ixst to measure the background and noise level, the crosstalk and then the frequency c:~aracteristic and the harmonic coeff i~ient. _ = Before the measure~ents the sensitivity of the KPU instrumenfi is calibrated by the carrier level in the interval. This replaces feeding a signal with a frequency of 1000 hertz to the input of the transmitter to establish the rated level at the measurement point. For measuring the background and noise levels the signal source is disconnected from the input of the trans- - - mitter of the tested channel and together with it a resistor is connected in the screen with the resistance equal to the modulus of the output impedance - of the signal source. When taking the readings of the KPU in decibels the _ calculation formula for calculating the signal/background and signal/noise ratio has the form: D=20-(x+y), where D is the signal/background and signal/noise ratio, decibels; 20 is the depth of ad~ustment of the carrier, decibels; x is the value of the reading with respect to the output attenuator, . decibels; y is the instrument readings, decibels. When measuring the crosstalk interference level, the mea.suring signal with a frequency of 1000 hertz, rated level and duration of 5-10 seconds is fed to the input of the influencing channel. Here the output voltage of the _ terminal modules of the equipment is monitored, and if the high-frequency channel is influencing, then also the modulation depth is monitored. If - the low-frequency channel is influencing, then trie low-frequency signal with rated level is fed only to ~he transformer substation on the lines of which the measurements are taken. All of the distributing f eeders of this sub- station must be connected. On the two-element network the measuring signal is fed only to the distributing feeder on which the measurements are taken. The crosstalk interference le~Tel measurements are taken with the "noise" position of the filter switc:h in the KPU. If the interference level exceeds by less than 6 decibels the noise level and if it is belew the noise level, , then the measurement is taken in the 1 and 2 kilohertz positions. In this ' case the level of the crosstalk interference is determined by the formula A~ = 20 201g . . ~ Y~l~ . U1 and U2 are the crosstalk interference voltages, volts, on frequencies of 1 and 2 kilohertz. 272 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 ~ - FOR OFFICIAL USE ONLY ~ Wi~~~i~ m~~;isuring the inter~crcnce level in the "noise" position and taking tize readings of the KPU instrument in decibels the interference level is determined by the formula A.~=20 -(x+y), decibels. _ In ur~l~~r ~u nu~~iriur~� lli~~ I~r~�~~u~~n~~y ~~lirirricl~,rlr~l I~�~ ;t vult~i�c~ ul 0.2~i vul.lr+ - !s Ced lo the input of the transmitter on a frequency of 110, 160, 1000, _ 3000, 4000 and 6000 hertz. Initially a measuring signal is fed with a fre- quency of 1000 hertz for 10 to 15 seconds. The input attenuator and calibration regulator K are used to set the pointer of the KPU instrument - to the -4 decibel position, with a position of the output attenuator at - 0 decibels and the "measurement" position of the calibration switch. Then the instrument is read successively on all frequencies. The harmonic coeff icient is measured on frequencies of 2000 and 4000 hertz for the rated output voltage of the transmitter and modulation depth M="70% and signal duration of no more than 60 s~ :onds. Measurements are taken in _ the "noise" position of the ~agulator b} KPU using the nonlinear dis- tortion meter. ~ When measuring the quality indexes of the channel with the group receiver, initially the harmonic coefficient is measured, then the background voltage, - - the noise of the crosstalk interference and then the frequency characteristic. The Itcirmonic coeff icient is measured on a frequency of 1000 hertz with rated volt;i}.;e at the transmitter output. For the meas;~rements it is possible to use Clie nonlinear distortion meter of the S6-1 type connected by the symmetric input tc the house network. The voltage of the measuring signal can b~ monitored by the KPU in the "voltmeter" mode. Before the measurements of the background, the noise of the crosstalk inter- - ference and the frequency characteristic it is necessary to ~eed a preset signal to the input of the transmitte~,c with rated frequency level of 1000 hertz to maintain a value of the amplif ication coefficient of the GPTV - having automatic gain control. Directly af ter f eeding the preset signal - the KPU instrument is used to take measurements in the "voltmeter" mode with the channel switch position at low frequency. The duration of the preset si~nal is 3 to 5 seconds. The background and noise voltages can be read for 20 seconds; otherwise the amplification coefficient of the GPTV varies and distorts the measurement result. The signalr,,ackgzuund and signal/noise ratios are determined by the i:ormula ~j - 201g~~~~2~ ~ cm) ~ (1) Key: l. background (noise); 2. preset signal _ where Uy is the preset signal voltage measured by the KPU; Ubackground and Unaise are the background and .~oise voltages measured by the KPU in the corresponding positions of the filter switch. r 273 FOR OFFICIAL USE ONLY _ APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY Inp~2~ ~ ~np~3~ . ~ . - . - )!I V ' . Figure 8.16. Circuit diagram of the measuring instrument connection to the three-pair GPTV network I:ey: 1. KPU; 2. program II; 3. program III In order to measure the crosstalk incerference from the signals of the adjacent high-frequency channel, the preset signal lasting 1 second is fed to the input of the transmitter subjected to the effect. By using the switch II1 a measuring signal lasting 8 seconds is fed directly to the input of the transmitter of the influencing channel. By using the KPU in the "voltmeter" mode the interference voltage Ui.~ is measured, ana any voltmeter - with symmetric input or a lineman's indicator is used to measure the voltage U2 of the influencing signal on the same pair of the three-pair network which belongs to the influencing channel. Then the points of connecting the KPU _ and the voltmeter to the three-pair network change places (see Fig 8.16) and by using the switch II~, the measuring signal is fed to the input of the transmitter to which the preset signal was fed. The KPU is used to measure the interference voltage U2.~ (for 8 seconds), and the voltmeter is used to measure the voltage of the influencing signal Ui. The signal/crosstalk ratio in the two high-frequency channels is defined by the formulas: U, A,~ = 201g u a. Ab~ 201g , ASl~ (1> Key: 1. decibels - The time diagrams of the voltages at the outputs of the transmitters (in the measurement process) are presented in Fig 8.17. In order to measure the crosstalk interference from the low-frequency signals the preset signal lasting 1 second is sent to the input of the transmitter subjected to the effect; then the measuring signa.l is f ed for 3 to 5 seconds. _ The interference voltage is measured ~ising the KPU. The same method is used to measure the interference in the second high-frequency channel. The sign,al/interference ratio is determined by the above-indicated formulas. When measuring the interference voltage in the "noise" position the inter- ference voltage is read d3.re.ctly by the instrument scale. If the measurements 274 - FOR OFFICIAL USE QNLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 P'UK UP'P'll:lAL US~: UNLY qB /lepe9ttmv~r ~g ~rr~ (u.o~c ~2o~r~q) . ~ i?8 ~3) ~1) ~ ' . g ' � ~,e . O f . � 9 - lT . . . . . . . . . . . . , , ~ . - qB. Ilepe~~tmvu~r ~Ktwl~Rrt ~axfr~ ~2j ~ ~ _ ta~o . . _ . . ~t . . . . e , ~ � ; ~ . . ~7 t~e (4> Figure 8.17. Time diagrams of the voltages at the output of the transmitters ~ Key: 1. 78 kilohertz (or 120 kilohertz) transmitter ' 2. 120 kilohertz (or 78 kilohertz) transmitrer 3. U, volts 4. t, seconds - are taken in the positions 1 and 2 kilohertz, the magnitude of the i.~;.er- ference voltage is defined by the formula UA = ~/~U~ UZ~ . � (1~'. , . . : . . Key: l. interference, low frequency where U1 and U2 are the voltages of the crosstalk (in volts) on frequencies of 1 and 2 kilohertz. The preset signa~ lasting 1 second is fed to the input of the transmitter to measure the frequency charact^ristic, then after 15 seconds, during which the level is measured, th~~ ueasuring signal with a frequency of 1000 hertz and a level of 0.25 volts lasting 5 seconds is fed. The time diagram of the voltages at the input of the transmitter in the measurement process for one measuring frequency is represented in Fig 8.18. Using thF KPU in the "voltmeter" mode and in the low-frequency position the signal level is measured. The measurements are repeated on frequencies of 110 and 6000 hertz with feed of the preset signal at the rated level before each sending of the measuring signal. - 275 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY (1) U8 yinm~ro0a~n+d (3) . ~ q cttrrru . . - ~eg m~dnr~i ~4~ ~ ~ . ~ ~ I8 t! t,C ~2~ Figure 8.18. Time diagram of the voltages at the input of the transmitter Key: 1. U, volts 3. Preset signal � 2. t, seconds 4. Measuring signal ~ 276 FOR OFP'ICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 ~ FOR OFFI~IAL USE ONLY APPENDIX 1. QUALITY INDEXES OF THE HIGH-FREQUENCX CHANNELS (FROM THE DRAFT OF OST "CHANNELS OF THE THREE-PROGRAM WIRE BROADCAST HIGH-FREQUENCY SYSTEMS. BASIC PARAMETERS") Table II 1.1. Quality Indexes of the Through Channel Names of indexes Norms Reproducible frequency band, hertz 100-6000 Nonuniformity of the frequency characteristic, in accordance with decibels, no more than Fig 3:4 Harmonic coefficient, no mcre than, on frequencies of : above 100 to 200 hertz g/q above 200 to 2000 hertz 4/2 above 2000 to 4000 hertz 5/2, 5 - Signal/background ratio, decibels, no less than 40 Signal/noise ratio, decibels, no less than 55 Signal/intelligible crosstalk ratio, decibels, no 50 less than Notes: ~ 1. The indexes of the through channel are normalized with the three-program speaker corresponding to class II of the through channel. 2. The unaltered value of the nonuniformity of the frequency characteristic ~S2 can be shifted within the limits of ~S1 (Fig 3.4). 3. The norms for the harmonic coefficient indicated in the numerator must be withstood for the rated signal level at the end of the through channel, and in the denominator for all levels reduced with respect to rated from 6 to 20 decibels, for channels with devices having two-cycle low-frequency stages. 4. Signal/background ratio; signal/noise ratio; sjgnal/intelligible cross- talk ratio are normalized in the interval. - S. Signal/background ratio is given for the channel with three-program - speaker corresponding to class II of the through channel. For the channel with group receivers the norm in decibels is na less than 50. ' 277 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY Table II1.2. Quality Indexes o~ the Operating Channel and Parts 1 of It Norms for the quality indexes of the operating channel and parts of i~ Numr o f 1 ndexer~ a~ v~~ a~ ~ I a? ~�a o ~ .c s~ .c w a~~i a~i " ii w~ o w o o " u ~ 00 J~ W+~ O H rl W 1.~ .G F+ W iJ .G W i.~ - 0 7+ o�~ o~+ o~+ ~ a? a~+ o Y+ ~ o a~ I f3 E~3 s.i W e0 p G1 Q N 7 ai aA a.~ m~ ao a~ a~ m u~+ ~ aL a~ ao C1 G~ ~-I ~~a~~n ~ama~a~co ~~m,~a? a~o a~d,~ co.c a~a m N n~ acaa,.~ u q ~ ~ ~ ~ w ~ ~ w ~ o .c a ~ N ~ d a? H J.~ H i~ O i~ M H iJ W 1�1 d-~ QJ N J~ ~ N id Reproducible frequency 100-6000 - 100-6000 100-6000 band, hertz Nonuniformity of the fre- In accord- - In accordance In accord- quency characteristic, ance with with ance with decibels, no more than Fig 3.6 Fig 3.5 Fig 3.4 Harmonic coeff icient, Z, _ no more than, at frequencies: more than 100 to 200 hertz 4.0/2.0 - - 8.0/4.0 more than 200 to 2000 hertz 2.5/1.3 - - 4.0/2.0 more than 2000 to 4000 hertz 2.5/1.3 2.8/1.4 4.0/2.0 5.0/2.5 _ Signal/background ratio, , decibels, no less than 60 - - 50 Signal/noise ratio, - decibels, no less than 60 - - 55 Signal/intelligible cross- talk ratio, decibels, no less than: from the low-frequQncy 60 55 53 50 channel from the high-frequency 60 - 57 50 channel 278 FOR OFFICIAi~ USE ONLY - APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY APPENDIX 2. EQUIVALENT PARAMETERS OF THE DISTRIBUTING FEEDER LINES Table II2.1. Equivalent Parameters of the Bimetal (BSM) Circuit with Wire Diameter of 3 mm Load subscriber transformer TAG-10 , . liapas~ }ra �acrore 78 KJt~ $ Tlapax~rpH aa aacra:e t~0 xCu S~ Zea ~3) ~ ~ za+ ~3) ~ ~9 'rP/+~ _ ~1) p~ yron AB/~at pap/xi~ uo Os~ roa ' ~ 4~~6 5 6 7 ~5 ) ns/ 6~ D~ - b~ 633 2�20' 0.76 1~59 602 -0�36' 0,45 2~54 ~10 6~l5 4�; S' 1,~0 1,~5 5~fi -1�l2' 0~65 2~57 ~5 656 7�24' 1~50 1,52 588 -1�42' 0~86 2~51 ~ 20 . 664 9�s8' 2.50 1~49 576 -1�42' 1.Q~ 2~64 ~ 25 670 13�12' 3~1 1,45 568 -2�18' 1~25 2~68 . 30 672 16� 3~? 1~43 556 -"~4' 1~43 2~71 35 6T1 18�54' 4,40 1,41 544 - -3�24' 1~61 2~74 ~ 6~,5 ?1�48' 5.0 1,39 53~# --3�24' 1,8 2,78 ~ -t9) ~'PY~-a6axe~xe ~rpaec.~opnsa~rog~ TAI'-25 ' , 5~ 658 14~4' . 3.? 1,44 624 4� 1~65� 2~4? - 10 633 29�12' ?.5 1~37 623 8� 3,10 2,44 !5 53? 33'~S' 10~8 1,40 622 11�~' 4,5 2~43 2a 472 ~5�1S' .13.? 1.46 . 612 15�3~' 6.0 2,43 25 41? 48�5fi' 16,2 1,5~ 559 18�18' Z~4 2~44 ~ 30 378 51� i8;4_ 1.62 583 21�48'_ 8~7 2~45 Key : ~ . . . _ ~ . l. S, tr/lan 2. Parameter on a frequency of 78 kilohertz 3. zBe 4. Modulus, ohms 8. Parameters on a frequency of S. Angle 120 kilohertz 6. Decibels/lan 9. Load subscriber transformer 7. Rad/km TAG-25 279 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY Table II2.2. Equivalent Parameters of a Steel Network with Wire Diameter of 3 mm Load subscriber transformers TAG-10 ~_(2~Iapaxerp~ es sa:rorax 76 xI1a s) iiapattcrps aa ranra:e 12u xl~t g~ Zss~3) " as za~ ~3 as ~ - ~P/~ (1) `~m'r Csyro~ 1q~/xx p(~)y ~4) ~SJ A~ ~ , (b 5~ 820 --6�10' 3,5 I,SS 762 -6�40' 3,8 3,d? 10 23T~ -3'35' 4,! 1.91 ?50 -6� 4~2 3,10 15 ~ 850 -4�43' 4~8 t;8~ 740 -5�30' 4,5 3,13 20 860 2� 5~5 1,80 7:~ -5� 4,8 3,1T ~ Z5 86S 5� 6,3 1.T5 719 -4�40' S.0 3.21 3~ 8S7 7�40' ?~1 l.72 ?10 -4'10'- b.4 3.25 � . 35 862 10'30' l.67 700~ -3�Z5' 5.6 � 3,39 ~i0 855 l4�20' 8.7 D.62 6SD -3�2b' 5,g 3.33 . - ( ) ~'PY3~a-aboee~~rcec~te 'rPaxc~wPn~a~roPd TAI'-25 . . . 5 g60 7�35' 7,0 1.T2 ?87- -3�15' 5,21 2~93 IO ?~0 23�10' 11.7 1,58 ?81 0�5U' ?y0 2,a9 . la 675 ~2�t0' 16.0 1.56 ??5 4�50' .8~75 2~85 20 594 37�45' 19.T 1.59 -?60 8�25' 10.~ 2.84 25 550 40�30' 23,2 1.64 ?42 12� ~ 12.3 2.84 30 . 515 42�~0' 26,6 1.70 ?20 1~� 14.1 ~.i~ ~ - Key : . . - . � ' ' . . . ~ . : . � 1. S, tr/lan 2. Parameters on a frequency of 78 kilohertz 3. zBe 4. Modulus, ohms 5. Angle 6. Decibels/km 7. Rad/km 8. Param+eters on a frequency of 120 kilohertz 9. Load subscriber transformer TAG-25 280 - - FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY APPENDIX 3. MAXIMUM ADMISSTBLE LOADS OF A STORY (IN POINTS) OF TH~ STAIRCASE WIRING LINES Table II3.1 LIHGio tORP1t H8 BTa.~E. rtOpx: ~CQ~f~h~C K.C~aOa Jna:slst 7~lCTgttQ~ - ~2~ Ao8 apo~oJ~t. IIPs Am~a rc~~pre:pao;t npoec~~sa. K . Ib 90 jt~r.csa ~ r:ecrs$apo3 ~3) Aa?~a a~P~aaxoR ~ryoao~xa. x - nDoao~s~ ~ n c~ ~ o ~ 0 4~ �~t 4)�~ 0 4)a ~4) (.1) - ^ o ,,e " � o ~4~� A %1 o d /1 A . ~ n~o~oA nTBhc�zx i,2 ~s~ (GjAO 1S 6 6 6 6 - 6 6 6 4 > 15 Ao 2? 6 5 4 2 6 2 2 - > 27 s 36 6 4 3 2 4 - - ~ >36 ~ 48 4 2 2 - 2 - - ~ > 48 a 60 2 - - - - - - - : (4) ~ . . : . . IlpoBOA IIByi{.2~5 ~6~ . . ~ ~t4)Ao15~ 6 6 6 6 6~ 6 6 ,6 >15Ao2T~ 6 6 6 4 6 ~ 3 a >27 ~ vS 6 6 5 3 5 3 3 ~ >36 ~ 48 ~ 6 4 ~ 3 ~ 2 3 2 2 >4g , 60 3 ~ 2 2 - 2 - - - ~ ~ . T1poPOA I1B-1~5 (PSL3�2X1~5i (7)" ~ ' ~ ~ > 15 ~AO Z? 6 . 6 6 b 6 . 6 6 4 >Z7 s 36 6 6 6 6 6 6 6 3 > 36 s 48 6 6 6 6, 6 6 8 3 ~ >48 ~ 60 5 ; b 5 b b 4 3 2 ~ >6fl s 80 4 4 4 3. 3 2 2 - Key: - ~ Length of the staircase wiring line, meters z. No of points in a story connected to one staircase wiring line; with a length of the residence line, meters 3. Length of attic wiring, meters 6. PVZh-2,5 wire 4. to 7. PV-1,5 (PPV-2x1,5) wire 5. PTVZh-2x1,2 wire _ 281 FOR OFFICIAI, USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFI~CIAL USE ONLY - APPIIIDIX 4. CALCULATION OF THE INDUCTANCE AND CAPACITANCE OF THE RESIDENCE CIRCUIT Lre3, ~res ~ THE REACTANCES X~ AND XL ON CARRIER FREQUENCIES OF 78 AND 120 KILOHERTZ Table JI4.1 fp=78 kilohertz fp=120 kilohertz 1 1 Lres - 4170 C , millihenries Lres = 1750 ~~picofaradsJ' ~illihenries [picofarads] _ 1 1 ~res = 4170 , picofarads C1e3 = 1750 L , picofarads L[millihenries] [mil.lihenries] XL = 0.49 LjmillihenriesJ~ kilohms XL = 0.75 L~millihenries]~ kilohms 1 X~ = 1.95�103 ~ , kilohms X~ = 1.33�103 1 kilohms [picofarads] ~[picofarads] 282 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 _ FOR OFFICIAL USE ONLY BIBLIOGRAPHY 1. Kantor, L. Ya. MNOGOPROGRAA'Il~INOYE VESHCHANIYE PO RADIOTRANSLYATSIOIJI.'70Y SETI [Multiprogram Broadcasting over the Radio Relay Network], Moacow, Svyaz'izdat, 1962, 60 pp. _ 2. Rivkis, I. T.; Shteynobuk, L. I. RADIOTRANSLYATSIONNYYE SETI TREKHPROGRAIrII~INOGO VESHCHANIYA [Radio Relay Networks for Triple-Program Broadcasting], Moscow, Svyaz', 1971, 96 pp. 3. Goron, I. Ye. RADIOVESHCHANIYE [Radio Broadcasting], Moscow, Svyaz'izdat, 1944, 363 pp. 4. Bezladnov, N. L.; Glikman, S. Ye.; Pozdeyev, B. G.; Savina, N. A. STANTSIONNYYE USTROYSTVA VESHCHANIYA PO PROVODAM [Station-Type Wire Broadcast Units], Moscow, Svyaz'izdat, 1955, 492 pp. S. Nyurenberg, V. A. OSNOVY TEKHNIKI PROVODNOGO VESHCHANIYA [Fundamental:s of Wire Broadcasting Engineering], Moscow, Svyaz', 1964, 87 pp. , 6. Yefi.mov, A. P.; Slepova, G. M. MNOGOPROGRAMD~IOYE PROVODNOYE VESHCHANIYE (POD!~CHA PROGRArIIri, UPRAVLENIYE I KONTROL') [MULTIPROGRAM WIRE BROADCAST- ING (PROGRAM FEID, CONTROL AND MONITORING)], Izd. VZEIS, 1969, 32 pp. 7. Yef_xmov, A. P. SISTEMY I STANTSIONNYYE USTROYSTVA PROVODNOGO VESHCHANIYA [Wire Broadcast Station Units and Systems], Izd. VZEIS, 1965, 60 pp. 8. 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Hydraulic Communications, UKAZANIYA PO PROYEKTIROVANIYU GORODSKIKH RADIOT~RANSLYATSIONNYKH SETEY [Instructiona on the Planning and Design _ of Municipal Radio Relay Networks], Moscow, Svyaz', 1964. _ 23. Dzyadchik, V. Ya.; Khabarov, N. A. "Analysis of the Volumetric Indexes of the Municipal Wire Broadcast Networks," TRUDY KONFER~NTSII PROFESSORSKO-PREPODAVATEL'SKOGO SOSTAVA VZEIS [Works of the Conference of Professorial and Teaching Staff of the VZEIS Institute], No 6, Izd. VZEIS, 1971, pp 56-63. 24. State Co~nittee on Civil Construction and Architecture under the USSR Gosstroy, NAPRAVLENIYA RAZVITIYA ZHILISHNOGO STROI TEL'STVA V SSSR [Areas of Development of Residential Construction in the USSR~, - 1969, 41 pp. 25. Shamshin, I. A. "Introduction of Triple-Program Wire Broadcasting in Moscow," VESTNIK SVYAZI, No 3, 1969, pp 30-31. 284 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102/08: CIA-RDP82-00850R000200040065-4 FOR OFFICIAL USE ONLY - 26. Dzyadchik, V. Ya.; Fomin, G. V. "Two-Channel Intermediate Amplifier for the Triple-Program Wire Broadcast Networks], VESTNIK SVYAZI, - No 6, 1969, pp 15-19. 27. Dzyadchik, V. Ya.; Piitronin, V. A. "Analysis of the Operating Efficiency of the Wire Broadcast Networks," TRUDY NIIR [Works of the Scientif ic Engineering Institute of RadioJ, No 3, 1969, pp 138-145. 28. Shenberg, M. M.; Dubuit, P. Ya. "Stereophonic Broadcasting over the TPV Networks," ELEKTROSVYAZ' [Electrical Communications], No 9, 1971, pp 19-25. 29. Dubult, P. Ya.; Shenberg, M. M. "Measurements of the Triple-Program Networks," ELEKTROSVYAZ', No 9, 1971, pp 37-41. 30. Dzyadchik, V. Ya.; Khvatova, L. M. 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"Device for Multiprogram Wire Broadcasting," USSR author's certificate No 284065, published in the BYULL. IZOBRETENIY, No 32, 1970. , 38. Dzyadchik, V. Ya.; Zaslavskiy, S. A.; Shapunov, L. Ye. "Device for Receiving i~ultiprogram Wire Broadcasting," No 278769 (USSR), BYULL. IZOBRETENIY, No 26, 1970, 39. Dzyadchik, V. Ya.; Zaslavskiy, S. A.; Yudayeva, Ye. Ya. "Triple- Program Wire Broadcasting Radio Transmitter," USSR author's certificate No 295175 (USSR), published in the BYULL. IZOBRETENIY, No 7, 1971. 285 FOR OFFICIAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 I MUL BY YA. DZYRDCH I K, S. R. ZRSLR~SK I Y 31 JRNURRY i980 B. N. F I LRTO~, R. ~J. SHER~HAKO~A C FOUO ) 4 OF 4 APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4 APPROVED FOR RELEASE: 2007102108: CIA-RDP82-00850R004200040065-4 FOR OFFICI~L USE ONLY 4C English patent No 228746, kl. 40(4), published 27 Apr.il 1955. r 41. English patent No 723024, kl. 40(4), published 2 F'ebruary 1955. 42. English patent No 730974, kl. 40(4), published 1 June 1955. 43. English patent No 864773, kl. 40(4), pub~.ished 18 June 1961. 44. Swiss patent No 313268, k'l. 120b, p~.~lished 16 May 1956. ` 45. Itadio broadcast channels, All-Uniori State Standard 11515-65, classes. - Basic quality indexes, Moscow, 1965. ~ 46. GROi~COGOVORTTELI ABONENTSKIYE [Subscriber Speakers], All-Union State Standa.rd 5961-66, Moscow, 1966. ` 47. "Radio Broadcast Receivers," A~.1-Union State Standard 5651-64, Moscow, - 1964. 48. "Stationary Radio Broad~:ast Transmitters," All-Union State Standard 13924-68, Moscow, 1968. - 49. USSR I�finistry of Communications, VTU 526-58, KANALY RADIOVESHCH~iTEL'NYYE. NGR*~IY ~IA OSNOVNYYE KACHESTVENNYYE POKAZATELI [Radio Broadcast Channels. S*_andards for Basic Quality IndexesJ, Moscow, Svyaz'izdat, 1959. 50. ELEKTRICHESKIYE NORMY PRnYEKTIROVANIYA RADIOTRANSLYATSIONNYKH SETEY [Rlectrical Standarde for Designing Rac~io Relay Networks], Moscow, Svyaz'izdat, 1961. - 51. Lebedev, V. M.; Rezvyakova, 7.. Ya. "Stereosound over Wires," VESTNIK SVY~,ZI [Communications Vestnik], No 4, 1973, pp 22-23. COPYRIGHT: Izdatel'stvo "Svyaz'," i974 ~ 10845 CSO: 8344/0265 - - ~86 - FOR OFFICZAL USE ONLY APPROVED FOR RELEASE: 2007/02/08: CIA-RDP82-00850R000200040065-4
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