JPRS ID: 8896 TRANSLATION MULTIPROGRAM WIRE BROADCASTING BY V. YA. DZYADCHIK, S. A.ZASLAVSKIY, B.N. FILATOV, A.V. SHERSHAKOVA
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1
MUL BY
~'R. DZYADCH I K, S. R. ZASLR~JSK I Y
~l JRNUARY 19~0 B. N, F I LATO~, R. ~J. SHERSHAKO~A C FOUO ) 1 OF 4
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J~'RS L/8896
31 January 19@0
Translation
Multiprogram Wire B~oadcasting
ey
~ V. Ya. Dzyadchik, S. A. Zaslavskiy
- B. N. Filatov ,~A. V. Shershakova
F~IS ~OREIGN BROADCAST INFQRMATION SERVICE
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JPRS L/8895
31 .7anuary 19 8 0 -
_ MULTIPROGRAM WIRE BROADCASTING
Moscow MNOGOPROGRAMMOYE PROVODNOYE VESHCHANIYE in Russian 1974
signed to press 17 Sep 74 pp 1-303
Book by V. Ya. D~yadchik, S. A. Zaslavskiy, B. N. Filatov and
A. V. Shershakova, "Svyaz" Publishers, 11,600 copies
CONTENTS PAGE
Foreword 2
Chapter 1. Multiprogram Wire Broadcast Systems 4
_ 1.1. Basic Characteristics of the MPB Systems 4
= 1.2. MPB System Using Physical-Artificial Lazge-Capacity
Cable Networks 5
1.3. Multiprogram Wire Broadcast System over the City T.elephone
Exchan~es g
- 1.4. Switchboard Type Multiprogram Broadcast Systems Based on
the Television Distribution Network 20
1.5. Multiprogram Wire Broadcasting in Foreign Countries 24
Chapter 2. Triple-Program Wire Broadcast System (TPB) 26
2.1. Structural Diagrams of tine City WB Networks 26
2.2. Basic Principles of Constructing the Low-Frequency
City Networks 33
2.3. Basic Principles with Respect to Creation of tlle -
MPB System 36
2.4. Nu~ber of Programs, Carrier Frequencies atid Type of
Modulation 38
2.5. Determination of the Initial Voltages of High-Frequency
Signals ir. the WB Channel q2 ~
2.6. Structure of the High-Frequency Channels of a TPB System 46
2.7. Structure of the.Station Part of the High-Frequency Channel 46 _
2.8. Structure of the Line Part of the High-Frequency Channel 60 ~
- a - [Z - USSR - F - FOUO]
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2.9. Structure oi the Receiving Part of the High-Frequency
Channel 64
2.10. Interference in the TPB System 69
2.11. Methods of Decrtasing the Interference with the liigh-
Frequency Channels of the TPB System 79
2.12. AM Signal with Regulatable Carrier and its Application 88
~ 2.13. Stereophonic Broadcasting in the TPB System 101
2.14. Basic Principles with Respect to Equipping Links of the
TPS system 104
Chapter 3. Introduction of Narms for the TPB System 1.18
3.1. General Information 118
3.2. Introduction of Narms f~r the Low-Frequency Channel 118
3.3. Introduction of Norms for the High-Frequency Channels 119
3.4. Determin~tion of the Through Channel 120
3.5. Definition of the Normalized Parts of the Through
Channel 121
' 3.6. Qual~cy Indexes of the Through Channel and Parts of It 122 ~
3.7. Introduction of Norms for the Tr.an;~mitters and Repeaters 126
3.8. Introduction of Norms for Receivers 129
3.9. Introduction of Norms for High-Frequency Devices and
Lines ~ 136
Chapter 4. Transmitters and ~tepeaters 145
4.1. General Information 145
4.2. Automatic Gain Control of the Car*-ier Frequency 148
4.3. UPTV-200 and UPTV-400 Transmitters 153
4.4. UPTV-60 Transmitter 161
4.5. Connection of the Transmitters to the TPB Circuit 162
4.6. Ztao-Channel Intermediate Repeater (DPU) 168 -
4.7. Prospects for Improving Transmitters and Repeaters 176 _
Chapter 5. Receivers 178
5.1. General Information 178
5.2. Riga Type GT 181 ~
5.3. Avrora Triple-�Program Speakers [GT] 183 ~
5.4. GT with Low-r'requency Channel Gain (Fig 5.5) 186 -
5.5. GPTV-3 G-~up Device 187
Chapter 6. Measuring Devices and Instruments 196
6.1. General Information 196
6.2. Modulation Attachment 197
6.3. Lineman's Indicator 199
6.4. Comp~ex Resistance Meter (IKS) 202
6.5. High-Frequency Oscillator (VI~3) 205 _
J _ b _
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6.6. Fault Detector (IPTV-1) 210
6.7. ITPV-2 Type Triple-Program Wire Broadcast Pulse Meter 212
6.8. Monitoring Receiver (KPU) 213
6.9. Channel Monitoring Device (UKT) 22p -
6.10. Test Signal Pickup (G-78/120) 221
6.11. Measurement Panel of the Distributing Feeder Frame
(PI-STR) 223
6.12. Problems of Introducing Meters 227
Chapter 7. High-Frequency Processing of the Line Part of a
Channel and High-Frequency Line Devices 229
7.1. High-Frequency Processing of Lines 229
7.2. Bypasses 230
7.3. Compensators 232
~ 7.4. Matching Devices 234
7.5. Band-Elimination Devices 237
7.6. Devices for Connecting Transmitters 23g
%.7. Transformer Substation Switching Devices 242
Chapter 8. Tuning and Measuring the Parameters of the Devices,
the Lines and t~~e Channels for Three-Program Wire Broadcasting 246
8.1. General Inforiaation 246 !
8.2. Electrical Measurements of the Transmitters 247
8.3. Electrical Measuremen;.s of the Group Receivers 254
8.4. Tuning and Electrical Measurements of the High-Frequency
Devices 25g
8.5. Electrical Measurements of Intermediate Amplifiers 265
8.6. Electrical Measurements of the Lines 267
8.7. Electrical Measurements of Quality Inde~oes of Aigh- -
Frequency Channels and Parts of Them 270
Appendix 1 2~~
Appendix 2 � ~79
Appendix 3 2g1
Appendix 4 2g2
Bibliography 2g3
- - c -
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PUBLICATION DATA
English title : MULTIPROGRAM WIRE BROADCASTING `
Russ ~an title ; MNOGOPROGRti ~II~IOYE PROVODNOYE
VESHCHANIYE
Author (s) ; V. Ya. Dzyadchik, S.A. Zaslavsk3y _
et al. _
Ed:itor (s) ,
Publishing House , "Svyaz "
Placc of Publication , Moscow
Date of Publication , 1974
Signed to press . 17 Sep 74 ~
- Copies . 11,600
COPYRIGHT , Izdatel'stvo "Svyaz 1974
- d -
F OR OFF IC IA L US E ONLY -
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r~
UDC 654.195.2
,
MULTIPROGRAriLJIRE BROADCASTING
~ ~ i'r~
- Moscow MNOGOPROGRAMI~NINOYE PROVODNOYE-VESHCHANIYE in Russian 1974 signed to
press 17 Sep 74 pp 1-303~
- [Book by V. Yz. Dzyadchik, S. A. Zaslavsiciy, B. N. Filatov, A. V. Shershakova,
Svyaz', 11,600 copies]
[Text] A study is made of va~ious multiprogram broadcasting systems combined -
with other forms of communications; the ac:vantages and disadvantages of the
- various methods of creating triple-program broadcast channels based on the
existing overhead wire broadcasting networks are analyzed; a study is made
of the problems of interference and standardiza~ion of the quality indexes
of the channels and in3ividual devices; a description is preser~ted of the
station and subscriber equipment, monit~ring ar:d measuring instruments and
high-frequency devices.
The book is designed for Qngineering ar.d technical workers involved with
the design, introduction, operation and maintenance of the triple-program
broadcast system. -
1
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FOREWORD
_ In the Soviet Union, the triple-program wire broadcast system (TPB) has been -
introduced in all large cities. In spite of the rapid development of
radio and television broadcasting, multiprogram wire broadcasting will in
- the future be one of the prospective broadcast media.
The TPB system was developed by the Scientific Research Radio Institu*e in
in 1960. The system has recentlq received further development. Can~sidering
_ the operating experience and the results of the investigations, new improved
transmitting and receiving devicps have been developed, a set of m~onitoring
' and measuring instruments has been built, and new high-frequency c~evices for
the wire broadcast networks have been developed.
- However, the future development of the wire broadcasting network (WB) will
be greatly influenced by modern civil construction distinguished by the fact
that instead of the continuous construction of buildings of equal height,
local microdistricts w3th high-rise complexes of varying heights are being
organized. This is changing the structure of the WB network.
The overhead lines running on supports on the roofs of the variable-height
buildings present problems in construction and maintenance. Difficulties
will also be encountered in taking the line from one local micrndistrict to
another as a result of the wide outside thoroughfares and streets.
A way out of the situation which. is already realizable in practice is partial -
or complete conversion of the distribution network to cable construcCion
using the city telephone exchange lines, the basements of buildings, service
corridors and the introduction of cable inserts in the overhead lines.
Accordingly, the question arises of rebuilding the WB networks and creating
new layouts for the city broadcast networks. It is possible to propose
that the development of a city wire broadcast system will proceed along the
path of combining the system with other communication networks.
In this book a study is made of the problems of building multiprogram broad-
- cast systems combined with other forms of communications. The advantages '
and disadvantages of various methods of building the TPB channels based on
2
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the existing overhead WB networks are analyzed, the problems of interference
and standardization of quality indexes of the channels and individual devices
are investigated, descriptions are given of the station and subscriber -
equipment, the measuring instruments and high-frequency devices, and a study
is made of the measurement techniques and methods of tuning the devices.
The chapters and divisions of this book were written by the foll~wing:
Chapter 1, ��2.1, 2.2, 2.14, 4.6 by V. Ya. Dzyadchik; ��2.4, 2.5, 2.10-2.13,
4.1-4.5, 4.7 by S. A. Zaslavskiy; Chapter 3, ~�2.3, 2.6-2.9, and Appendices
1-4 by V. Ya. Dzyadchik and S. A. Zaslavskiy jointly; and Chapters S, 6, 7
and 8 join~ly by B. N. Filatov and A. V. Shershakova. The book is designed
for engineering and technical workers of the maintenance enterprises, the
workers of the design organization~ engaged in the introduction of the TPB
system and it can be used as a tea!t for students in the middle and higher -
communications schools.
The authors express their deep appreciation to the reviewer of the book
L. Ya. Kantor and the responsible editor V. I. Shanurenko for valuable
recommendations and suggestions.
Comments on the book shuuld be sent to Izdatel'stvo Svyaz' (101000, Moskva-
Tsentr, Chistoprudnyy Bul'var, 2).
3
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:
CHAPTER 1. MULTIP't20GRAM WIRE BROADCAST SYSTEMS ~
1.1. Basic Characteristics of the MPB [Multiprogram *+1ire Broadcast] Systems
_ The wire broadcast system is the set of devices designed to shape and
amplify~broadcast program signals and distribute them by means of a wire
distribution network to the subscriber receivers with subsequent conversion
of the electric signals to acoustic. A riecessary element determining the
technical essence of such a system is the lines and line equipment, the ,
purpose of which determines the name of the given wire broadcast system.
Accordingly, the MPB systems can be based on the following wire distribution
networks: telephone communications, collective television reception systems,
the domestic broadcast network, and on the basis of an autonomous low-freque-~cy
signal-program broadcast system.
Depending on the method of transmitting the broadcast program signals, two
versions of the MPB systems are distinguished: low-frequency and high-
_ frequency.
In the low-frequency version the signals of all programs are transmitted in
the initial low-frequency spectrutu.
In the high-frequency version, the program signals are transmitted in the -
- form of modulated high-frequency signals. -
With respect to methods of construction and use of the distribution network
the MPB are separated into the following: uncommuted systems using one
physical network to transmit the broadcas~ signals and other types of -
information, the cot~utation type systems using one physical network to
_ transmit the signals of all programs and the commutation type systems using _
several physical circuits for transmitting the broadcast systems and other
types of information.
Each system is characterized by another quality class and number of channels,
the frequency band used by the modulation method, the type of receiver and .
tthe technical-economic indexes.
4
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1.2. I~B Systems Using Physical�and Artificial Lar~e-Capacity Cable Networks
The structural diagram of the system using a multiprogram cable is illuatrated
in Fig 1.1. On the transmitting side thE broadcast signals are fed to the
line at comparatively high voltage (60 or 30 volts). On rae subscriber side,
the simplest receiver is used. This type of system is ~~lia~le, convenient
in cperation and maintenance, but it requ~.res a large nusnber. of physical
circuits in the cable equal to the number of transmitted programs.
,yilLl.'!!IllW7i~AlQA ~ . .
~ ~ ~ ~l) Pesr.ve~~onr.~ASrmo sem~ (5) ~ ~
_ -f2~ ~ ~ D ,
. . . e
~I ~ i : ~ ed
b
(3)'~d,~ ~ y~ .
4 ~p ~ . ~o'E,? '
_ ~ ) 1 nv 1\ ~
~ ~ a 3 d~ g~
- J - 4 y ~'G~a~ ~ 6) ~ r~h~N. 6)
. . y~,'~ ' Ut~Q
Figure i.l. Structural diagram of the low-frequency MPB system
Key: :
1. Repeater station 5. Distribution network
2� Iprogram 6. Subscriber sets
3� IIprogram 7. To other subscriber sets
4� Illprogram
In practice the version of this system is used where along with the physical
networks artif icial, so-called phantom networks are used (see Fig 1.2).
Th~ operating principle of this t}~pe of system consists in the following:
th~ signals of four programs are transmitted from the repeater station to
the distribution network. Three programs are f ed to the subscriber network
over three physical circuits. Program IV uses the physical networks of =
programs II and III, and it is connected to the midpoints of the secondary
windings of the transformers Tpl. On the subscriber side the signals of
program IV are picked up from the midpoints of the primary winding of the
TPZ transformers. In order to create the phantom circuit chol:es are more
frequently used. With a complete equivalent circuit from the point of view
of symmetry and equality of the halfwindings of the transformers TP2 and Tpl
- the magnetic fluxes created by the signals of program IV and the voltage
as a result of asymmetry are equal to zero in the circuits of programs II
and III.
The subscriber network is made up of a four-pair cable. In each subscriber -
set a pro~ram switch I is provided by means of which the corresponding _
program is selected~ Ho~wever, considering the high signal voltages in '
such a system, careful symmetry is requirec~. Asymmetry of th~ circuits
caused by deterioration of the state of the cable (for example, as a result
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. l~aameaax~ ~ (2) ' ~ . . . . . . ~ . -
. ~1) ava,~~rru Pccipat~amrn~~c~ anK ~ ' : .
~ -~3~ j~, p ~ . . . ~ ~ ~ ~ .
. ~ ro,
(4). l,'v D ~ ! I 1 _
i
~5>" t,~ , ' . ~
. ~
' � ~ TP~ ~ Tps -
.
c~) ~rA,,.~. ~ . a y ~
: ~ b
- I , . . _ , ^ ~
- ' ~ ~ . : : . ~ (7 } A1ds~~~R eu n~ b )
. . . : . _ _ : Q
. f. ~ ~ -
- ~ ~ ' ~ i{~ .
a
? .
Figure 1.2. MPB system using physical and artificial large- -
capacity cable networks
- Key:
1. Kepeater station 7. Subscriber sets _
2. Distribut~ion network 8. Subscriber network
, 3� Iprogram
4� IIprogram
5� IIIprogram ~
6. I~program
_ of a change in insulation resistance) and also failure of the transformers
will lead to a decrease in the crosstalk attenuation betweQn them. An
important difference between the phantom circuit and the physical circuit
is that they have different primary equivalent parameters. By comparison
with the physical circuit, the resistance of the phantom circuits is
approximately half; the inductance is approximately a third, and the
- capacitance of the line is approximately threefold. This leads to the fact
that the frequericy characteristic of the phantom circuit is worse than that =
of the physical circuit. In addition, as a result of increasen capacitance,
- overleading of the terminal stages of the program repeaters is possible.
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Fig 1.3 shows a version of a phantom circuit which eliminates the indicated
- def iciency.
~ ~ 9'cvaamt~Eyarv cma~~ (1) ~ ~ . . .
_ - r~ g a ~ .
0 . ~ .
, ~ ~ . I _ .
_ ~ ~
L--- . . ~ . . . ~
~ c2) (2) . , . . . . . .
. . ~ � ~QP ~tP ~ � .
.
. _ .
~ : ~ ~
� . .
_ . : . � po~ 3 0 0
: ~2 ~2~ ~ - - -
~ c'. . ,4p. _ ap_ P~
. , . _
~ ~'a~a
~'r � s0� ~
~ n d. -
. p~ , .~1
' lr a6oHaMm~~rrrr 7~,
- qcnporiomlaN (4)
_ Figure 1.3. Version of the MP'B s~stem using the phantom circuit
Key:
1. Repeater station
2. Choke
3. Transform~er
4. To the subscriber sets
The signal voltage at the beginning of the phantom ci:cuit is cut in half
by comparison with the ordinary circuit, and on the receiving side at the
subscriber their level is equalized. This is achieved by selecting the
corresponding coefficients of the output and subscriber transformers. As
- a result, favorable operating conditions are created for the repeater, the
frequency characteristic of the phantom circuit improves, which now is -
loaded on both ends by a corresponding lower load resistance. In the given =
_ system the phantom circuit is created by using four chokes with midpoinLs,
and the signals of program III are transmitted through it.
As illustrated in Fig 1.3, programs I and II are fed to two subscriber sets
A and B. When selecting programs I and II, the voltage is fed from the
- volume control Pr to the entire winding of the subscriber transformer Tpab
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(positions 1, 2 of the swirch II). In the case of selecting a third program
- (position 3 of the switch II) only part of the primary winding of the trans- `
former is connected to the volume control. As a result, the~subscriber does
not notice the difference in the voltages, independently of which ctrcuit
is used, although only half the signal level is fed through the phantom circuit.
The practice of creating phantom circuits indicates that the stable crosstalk
attenuation does not exceed 50 decibels (with a requirement of to 70 decibels).
Tt must be noted that the indicated version of ths system can be used for
the single-element networks in the repeater-subscriber section. Its applica-
tion also on the existing distribution network is possible when it is
- necessary to increase the number of programs transmitted to the subscriber
distribution network. In this case only the subscriber network will be =
changed, and the distribution lines will be kept the same.
1.3. Mult~program Wire Braadcast System over the City TelepY~one Exchanges
General Information
Inasmuch as the MPB system is based on the city telephone exchange, measures
must be adopted to see that they are completely compatible technically
= and organizationally. When building the MPB system, the following require- _
ments are imposed on it: -
1) Introduction of it nust not interfere with the telephone circuitry or
have any noticeable effect on the quality of the telephone conversations;
2) The MPB system equipment must not interfere with privacy of the tele-
phone conversatior?; ~
_ 3) The MPB system must be designed so as not to introduce significant
changes into the telephone and office equipment.
Commutation Type MPB System
- Inasmuch as each subscriber line is used little in ~:ime, the idea has come
up to use the telephone system to transmit broadcast programs. In order `
to create such a system, low-frequency repeating equipment has been
installed at the automatic telephone offices [12] for each WB channel, and _
station switchboard equipment l:as also been installed. A receiver made up
of a program selection unit, low-frequency repeater and loudspeaker is
installed at the location of che telephone network subscriber. The program
is dialed si.milarly to how this is done in telephone communications, as a
result of which the subscriber telephone line is disconnected from the
telephone distributing fr~~C a~~u ii. ~onnected to one of the broadcast
repeaters. By using tr~is technique, the telephone network is used both
for telephone conversations and for broadcast jointly, but not simultaneously.
' In order to eliminate the interf erence of the broadcast program sign,als
on other telephone circuits the voltage of the broadcast signals is
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_ kept small, ar_d their ~amplification occurs in the subscriber receiver.
- However, the gain of the receivar must be so smull that it does not inter-
fere with privacy of the telephone conversations. The danger of hearing -
telephone conversations increases with a decrease in the crosstalk attenua-
tion between the .:able circuits. A significant disadvantage of this system
is the fact that the subscriber is offered the possibility of using the
network to obtain only one type of informatiion in each time interval:
when a telephone call comes in the sub3criber must int~rrupt the broadcast
- transmission.
Fig 1.4 shows a system which implEments the indicated MPB system. This
version of the system was proposed in the USSR in the 1930's by
A. V. Vinogradov, but it was not implemen~ed at that time as a result of a
number of technical deficiencies.
- � AODNCNG9~ 1 ~ , : . . , ~ ~CrMhCf~,YDM,y flCl?7?ll1WIM ~ 6 ~ _
{
r ~P (3) ~ . .
, " ~?~8 4~ , .
r r~va- ~i~B'3 ~ llnpe~sm~ f ~ .
. ( pI1C~4F ~ ~mel16 ~Rpr. ~ ~ -
.~DCS~G ~ ~M/IB~I~ I PUt 0 Op'! .~QA?N
rM/!Bd yNy ~(12~ ~ ~8) ' .
~ ~ : .
. _ 1 ~ ~
~ . . : . ~ . ~ ~ . .
~ j. i r r ~ -
~ ~ ; d~~ur~mrnac npc~pa,~M /IB g � - ~
. .
_ Figure 1.4. Schematic diagram of low-frequency WB over a
telephone .line with program selection
Key:
1. Sub~criber 8. Program selection relay
2. Telephone line 9. WB program repeater
3. Telephone 10. MPB receiver
4. MPB 11. Low-frequency repeater
5. Mode of operation relay 12. MPB program switch
6. To the connector
_ 7. To the preselector
_ High-Frequency MPB System
The procedure for us.ing the telephone network for each system consists in
= transmitting the broadcast programs on the high-frequency band.
- 9
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Let us consider the factors which must be considered i?z creating such an
MPB system. First, it is necessary to consider the possibility of broad- -
cast interference from the telephone systems as a result of the station
switcliing equ:ipment and the subacriber dials. Low-rrequency filterfi
cc~nnectecl on botli encle muat uttenuntQ the effect of Chiy tnCErrCerence in
t}iQ occupied broadcast band.
- Second, interference is possible from the radio broadcast stations, the
level o� which determines the minimum signal voltage at the subscriber.
Thirdly, it is necessary to consider the different attenuation of the side
- frequencies causing noticeable nonlinear distortions. For eff icient use of
the AM repeater power, all of the lines connected to the telephone office
are grouped depending on the length of the line, and each group has the -
requirQd level of high frequency signals at the input to maintain a
suff icient signal level at the end of the line [12]. I
The schematic illustrating the principle of the construction of a high-
frequency wir.e broadcast system is prQSented in Fig 1.5. Tra~smitters
each with its own program, are installed at the telephone office. Tr~e _
broadcast programs can reach these transmitters from the informaiion soiir~es -
by various paths.
'Che l~ign-frequency signals from the transmitters are fed to common bust.s and
by means of the station connection filters (SCF), to the subscriber tele-
phone lines. The station connection filter contains high and low-frequency
~ filters cormected in parallel. The low frequency f ilter does r.ot pass the -
MPB si~nals, and it also eliminates the effect of the interference caused
by the commutation devices of the station. The high-frequency filter
prevents penetration of the low-frequency signals into the high-frequency
equipment. The subscriber f ilter (SF) is installed at the end of the
subscriber telephone line. It is also made up of high-frequency and low-
frequency filters having analogous purpose. The terminal receivers are
connected to the corresponding output. In order to simplify the station
connecticn filters and the subscriber filters, inasmuch as they are an -
= important element of the system, the fr~quency band occupied by the MPB
signals must be selected as far as possible from the frequency band occu- �
pied by the telephone channel. Considering the admissible damping on the
city telephone exchange lines and the possible use of radio broadcast `
receivers, the frequency of the long-wave band is selecred from 150 to
350 kilohertz. -
Fig 1.6 shows the structural diagram of a six--channel MPB system. The six-
carrier frequencies are modulated in the transmitters by the corresponding
signals of different programs, and they are transmitted through the filters
Cl-C6 to the wide-band high-frequency repeater or channel repeaters KY
if greater power is required. The carrier voltage of each broadcast
channel is about 5 volts. When using signal-channel repeaters, it is _
10
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~
� 7b~orm? sa,~a,rq~ Po~rx~4~v?[2~ ASonrHm ~3~ . ' -
. ~1.~ a.vs;:s~a ' -
' { ' ; . ~.W~r1/~ %
1'6 ~ ~ ~
, . ' ~ I I ~ ~ ~
6//~ ~ "
� ..E4~ ~ '
- ' ~'vc~re~m ~5) ~ I ~sv ~ ~a' ~ (7)
/ru~NAT ~ ~ r ~ .
. . . - ~ ~ .
F
. ~ ~ ~ ~
~ ~ ~
- ~
. , . ..-1. . _
�
~ ~ ~ I ~ ~ c8>
. n, ~ . . ' ~ ~HVr9 I ~
. ~
' c-~ l ~ . . . . ~ ' _ . . . ~ ~a ~ .
� i f .._:I . . ~
, ~ ~ �
~ ~ naFy~N . ~ .
. ~ :3 a6oae~ra,rr~v~ ~ ~ ~ , ~ ~ . _ - . . . .
n.~- ~ (].1) ~ . - I . ; . : , . . . .
. . . ~.f~~.~ . . . . . . ~ ~ ~ . - ~ ~
(1~)a
B OG,~ae ~rab?~i Ar,~eBM~. ~i~ . ~ . ~ ~ . , . � .
Figure 1.5. Structural diagram of the high-frequency MPB system
based on the telephone network
Key:
1. Telephone office
2. City telephone exchange distribution iines
3. Sub~criber
4. To the automatic telephonE of�ice selectors
5. Station connection f ilter
6. High-frequency filter 11. To the other subscribers
7. To the MPB receiver 12. Co~on buses in front of the MPB
8. To the telephone set 13. 2~B transmitters
9. Low-frequency filter
10. Subscriber filter
possible to obtain a volta~e of about 25 volts at the output of each
channel.
Dep~ending on the length of the line, one wide-band repeater can feed up tn
several hundreds of subscriber lines.
11
FOR OFFICIAL USE ONLY
I
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~ "o�~ cl> . . -
. . ~ -
~
-
" i ~
,
= ~ . . IPacnpcdenvsmend' C~11dN1(UONNIJLI -
~ ~ N~c u~~rNd ~r~a6mp ( ) ~
3
. . . ~ . � .
v
E
- _
~ . _ ~
iE . , . . . .
' . - ~ ~ . , .
~,t - . '
_ ~ _ ~z ~ . : " ' .
~ .
~ , ( ~ . ~ .
. _
~Iep-~r~t M ,~r~rmo- ~
par - - -
S/
~ X~ I ~ ~s-mcnrc v . - e~ ~1d~S~ ~p~~. .
D D ~ ~ ~
~,J
g I ~j ~ o
- . D ~a , ~ . _
' ~ a ~ ~ E:
b
"~t D ~ D (i3)
� ~ ~rly~'R 8 Qy ~ _
:r~ D 9� . :
~ ~ ~'i ~ I ~ . .
_ ~ . ~1~i D ~6 _ .
� � 3y0 ~ ~ $ : � '
~ ~ . = . ; ~ ~ p ~ . ~ ~
~.:Il~~il~ , . .
. . BXO~ NY ~ ' . ~16)
. ~ (1.5 ) . . ~
Figure 1.6. Schematic of low-frequency MPB
- Key:
1. Telephone network distributing frame 9. Repeaters
2. Distribution buses 10. Filter outputs
- 3. Station filter 11. Wide-band repeaters
4. To the switchboard equipment of 12. Distributing transformer
the telephone offices 13. To the other telephone offices
5. Transmitters 14. kilohertz
6. Modulators 15. Low~frequency input
7. Filter inputs 16. Channel repeaters
~ 8. ~ = filters
12
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~ , � _ .
~ ~ . ~ ~~~,~6x~ y~~,~~~ . ~ -
. ~ ~l>> . � cls) Tq c qcnr-E~it
dirA nco~Qdre~ (ig)
.
~ ~ ~ N~ nc~eX �
Ap ~~a- ~ y~mp~ricm0o .
�NrmeA~ ~ AodX/liOilON(dp I ~ j"- ~p-~ .
~ (20). ~ ' (22)
I ~21~ L._.
r ~ ~ T!! .
- ~ ? u�n
m,~o ! ~ ~ c~I.~o
~
~ . , ~ ~ - dna0br-. ~23).
" 0~
~ ( ~ u j 1-- - n~~ �ap~,uwb~ _
. ~ Mns .
L. c22~
,
~ ~ ~ ~ Ilar,~ymQmop~~25~
~ j_ _ Coanacya ~e ' ' � ~ . . .
w w , yc~%pou~cm~o (26) - .
~ I ycmpcucmOo nadxn~yen?ua ~
L; . J ~zz~ Mna ~ .
. /y mp p~ � . PuducnpueM . � � .
- (30) i 29)~ ~ ~ . /Ip-~ ~22~ -
- . . - ~ ~ ~ ~ L. . .
~ ~ ~ . . . . .
. ~ ~ i . . , i - ~p_~~22>
- . ~ . ~ .
. ~ . ~ -
, . . . . r� ~ .
. . . -
. ~ ~ ~ ~ ~�~-,~c22~
. . . . . . .
. _ .
of the city telephone exchanges
Key:
17. Subscriber line 25. Switchboard
18. Subscriber sets 26. Matching device
19. Telephone with interference 27. MPB connection circuit
= suppressor 28. Radio receiver
20. Fuse 29. MPB
21. Device for connecting the MPB 30. High-frequency transformers
22. Receiver
23. Telephone with MPB program
selection device
24. Input filter
13
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The complex made up of six single-c}.iannel repeaters can be serviced by
several thousands of subscriber lines.
On the receiving side the MPB signal~s can be picked up on a special receiver
or a long-wave band ratio broadcast receiver.
Fig 1.6 sho;as versions of the u;ae oF an ordinary radio broadcast receiver as -
the receiver. It is connected to the MPB network by a device made up of a
symmetric transformer and switch per.mitting conversion from reception over
the MPB network to radio reception by coaxial cable (the subscriber line 1). -
It is possible to connect several receivers tu one subscriber line through
the matching device (line 3). If part of the sutscribers use the services
of the MPB system of the switchboard type, and it is necessary to send
high-frequency MPB signals over the same subscriber line, then in addition
to the matching device it is necessary to connect the low-frequency input -
filter in front of the telephone sets of the subscribers using the switcl?-
board type system (line 2). -
A special MPB receiver having high acoustic fndexes can also be used. It
is constructed by the direct repeating scheme and is made up of filters
tuned to fixEd frequencies, a detector and repeater. -
Co~isidering the organizational principles of the MPB system over the
telephone network it is possible to note that the filters introduced on
both ends of the Iine are important elements providing for the absence of
- influc~~ce of the systems on each other (tne telephone and broadcast systems), -
The introduction of the filters increases the ohmic resistance of the lines
for the telephone systems with centralized feed, it increases the damping
of the low-frequency telephone conversation signal. The attenuation in
the low-frequency f ilters must not be more than 0.2-0.25 decibels. In this
case the quality of the telephone conversation transmission will not be
negatively affected. On the other hand, as was pointed out earlier,
privacy of the telephone conversations must not be disturbed. In Fig l.b
it is obvious that the voltages of the high-frequency signals are fed to a
common bus to which the high-frequency station filters are connected. Thus,
the subscriber lines connected to this bus are connected to each other '
through the low-freauency station filters, and there is a danger of intelli-
gible crosstalk.
In order to avoid mutual influence betwepn the subscriber lines, the
equivalent resistance of the distribution transformers on these frequencies
is made small. The attenuation on the low-frequency station filters on
the order of 90 decibels is entirely sufficient to guarantee i.mpossibility
of hearing intelligible telephone conversations even with the help of
repeating equipment. It is possible to hear conversations only in an
emergency when all of the low-frequency f ilter coils are short-circuited.
14
FOR OFFICIAL USE ONLY
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. ~ 1) ~l~ ~4TC f
~ �
' i ~
. i ' -
~ i ~ ,
~ ~ ~
~ ~
. ~
t~ / ~ . ' ,
-
. i _-t~ ,
- ~ .
t ATC _ . : .
~9TC
Figure 1.7. Structural diagram of the construction of the
MPB system over the city telephone exchange lines
_ (without junction formation):
1-- central wire broadcast station; 2-- terminal wire broad-
cast station; connecting lines of the city telephone
w exchange used for MPB; connecting lines of.the city
- telephone exchange u~ed only for telephone communications
Key:
1. automatic telephone office
Depending on the structure of the city telephone exchange, two versions of
constructing the high-frequency MPB system are possible. The first version
is for division of the city telephone exchanges into districts constructed
by simple junction formation by the principle of "each-to-each" couplings
between the automatic telephone offices. The second version is with .
complex junction formation of the city telephone exchanges of large cities
with several simple networks of district city telephone exchanges. The
structural diagrams of such MPB systems are presented in Figures 1.7 and -
1.8 respectively. The MPB system uses frequency multiplexing of the
connecting lines between the automatic telephone offices and the siibscriber
telephone lines in both versions. The multiplexing of the connecting lines
is provided for over a separate pair in the interoffice communications
cable isolated specially for this purpose. The subscriber lines are used
_ simultaneously for MPB and telephone conversations. In the first version
a central wire broadcast station is set up at one of the automatic telephone
offices, for example, 1. The broadcast program signals are fed to this
automatic telephone office from various sources: the radio broadcast
equipment r.oom; from local studios and isolated receiving stations. In the
second version the central wire broadcast station is equipped either at an
automatic telephone office or at the incoming communications junct3.on (3,4).
The terminal wire broadcast stations which service the subscriber network
of the given automatic telephone office are set up at the remaining auto-
matic telephone offices (2).
The structural diagram of the equipment for the central wire broadcast
station is presented in Fig 1.9. It includes the following: program -
sources 1, a transmitter complex 2 made up nf modulators for each program;
15
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band filters 3; multichannel repeaters 4 and high-frequency matching
transformers 5. The multichannel repeaters can be installed to feed
several connecting lines or one having high attenuation. In a~.dition,
terminal wire broadcast station equipment with single-channel repeaters 7,
with band filters 3, station subscriber filters 6, the number of which is
equal to the number of multiplex subseriber lines, is set up to f eed the
subscriber lines of the given station.
' ~b~ RTt t (b) ~PJr J . .
- ' I ; - . : ; .
i ~ s y ~ ~
~s ~ ~c '~c~ y~C ~ ` ~ _ (b)
~a~ ~b ~ : . 9BC ` yHC ~ ; . ~ .
~ i~~~ _ `
i i % ~ ~ '
i
- i . ~ i . - ' ~ ~ . �
; _ .
~t qfCt ~
. ~b ~ ~tc ,vrcl
? .
Figure 1.8. Skeletal diagram of the MPB network over the
city telephone exchange lines (with junction
formation):
1-- central wire broadcast station; 2-- terminal wire broadcast -
station; 3,4 intermediate wire broadcast stations; connect-
- ing lines of the city telephone exchange used for MPB;
connecting lines of the city telephone exchange only for telephone
~ communications
Key: ~
a. low frequency
b. automatic telephone office
c. UIS outgoing comm~~nicat~_ons junct~on; WS incoming communications
junction -
With respect to the isolated physical circuits (the connecting lines) -
between the automatic telephone office from the repeaters 4 to all other _
ATS-2 [automatic telephone offices] high frequency broadcast prog.ram
signals are fed. In order to equalize the broadcast signal attenuation in
the different channels, equalizing circu~ts are installed at the ead of -
the line. The structural diagram of the terminal wire broadcast stations
is presented in Fig 1.10. After correction (the equali.zing circuit 1)
the high-frequency signals go through the band input filters 2 to the -
single-channel repeaters 3 where they are repeated to the required level
and are added by means of the signals in a common load in the form of high-
frequency transformers 4. Then after grouping, the signals are fed to the
station subscriber filters 5 for distribution over the subscriber lines
- running to the automatic telephone office distributing frame.
16
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, _
~1~ ~ + ~ -=C/l . ~2~ �
A?~rr~d7uoyKOy '
� il~,rydo0arup~l~
. 3 . .
y 0 ~ ~ pp~ (3)
I n' ~ . ~ '(5) �v (4
- D ti
~
d ~ , -
~ n ~ D ~ ~ '
D ~
. p .Y- D ~ s 6 ~A~6~ .
r n ~ D ~
- B n ~
J r t~~ a p f ~
Figure 1.9. Structural diagram of the equipment for the central
wire broadcast station for MPB over the city
telephone exchange located at the automatic
telephone office -
Key:
1. connecting line
2. to the station equipment of the automatic telephone office
3. automatic telephone office distributing frame
4. low frequency
5. high frequency
6. subscriber line
7. program
For the city telephone exchange with complex junction formation (Fig 1.8)
where the junctions for the incoming and outgoing communications exYst
by means of which communications are realized between the groups of
district automatic telephone offices located in various junction districts
another station object is introduced the intermediate wire broadcast
station which is organized in the incoming or outgoing communications
junctions. The structural diagram of the intermediate wire broadcast ~
station equipment is presented in Fig 1.11. The high-frequency amplitude-
modulated signa.ls are fed over one of the interstation communication lines
in tandem through the intermediate wire broadcast station to the frequency
equalizer, and af ter repeating they go over the connecting lines to the
automatic telephone office or to the communication ~unctions.
17
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. � ~ ~ . ^ ~ . " (3) A'cr.~a,rqreHyca~/- ~
~ . . . : ~PYIoB ~rtax~
. _ : _t~ ~ : _ . ~ . ~ . .
. . : . ~ ' ' : . . . . (4, t~ ~ Nv (5~ . .
. , . . . . , . : ' ~5~ Ny ~p~l
. . ~ D 6 a .
~ p ~ ~ s I ~ ~q . .
~i~ - ~ f ~8~ ~
C/I ~ D y
eK ~ D ~ ~ y s 'RJI(~~ -
~Z j . .
_ ~ ~ ~ ~ ~ D ~ ~ � ~
- . . ~ D ~ . . � _
~ a a s ' ~ ~ a" ~ ~ . . ~
Figure 1.10. Structural diagram of the equipment of the terminal
WB station for MPB over the city telephone ~
exchange located at the automatic telephone office
Key:
1. connecting line
2. switch
3. to the station equipment of the automatic telephone off ice
4. automatic telephone office distributing frame
5. low frequency
6. high frequency
7. subscriber line ~
8. subscriber -
When the equipment of the central wire broadcast station is located at one
- of the communications junctions, the structural diagram varies, and only
the terminal wire broadcast station is set up at all of the automatic
telephone offices. .
~ . . _ ,
U ~ 2 . QP ~1~ .
� . . j ' ~ . . . . I[fl Ay (3) ASI Ay .
' ' ' ~V
- f . �
t Blt ~
~1> 2 i ~1~ . ~4~ -
: . ~ ' ~ ' . . . . . . `n (5> TA (6) -
U"" % - ~ - . ~ . .
Figure 1.11. Structural diagram of Figure 1.12. Circuit diagram
the intermediate wire broadcast station of the receivers
equipment placed at the outgoing communi- Key: 1-- group rectifier;
cations junction (incoming communications 2-- subscriber set; 3--
junction) low-frequency filter; 4
Key: 1-- connecting line high-fr equency filter; 5--
2-- switch ~ connecting line; 6-- telephone
18 -
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From the investigation of the indicated diagrams of the MPB system it follows
that it turns out to be rigidly connected to the telephone communications
system. Common station and line equipment are used. However, in order to
receive the MPB broadcast program aignals it ie necessary to be a telephone
network subscriber.
As was demonstrated in Fig 1.6 there is a method of f eeding the broadcast
_ signals to several subscribers over one telephone pair. The subscriber
uses an individual receiver with autonomous feed as the receiving set.
The system using the subscriber line for simultaneous f eed of the high-
frequency programs and feeding the subscriber sets from a common rectifier
is also of interest. This type of system is presented in Fig 1.12.
For simplif ication of the subscriber set under new conditions when semi-
conductors are being widely introduced, it can be expedient to use the
group rectifier and the autonomous network for simultaneous feed and
supply of the MPB signals.
As is obvious from Fig 1.12, the MPB signals are fed from the automatic
- telephone office over the connecting line to the telephone. Simultaneously,
this line is also used for telephone communications; here the telephone is
- connected by the usual method. Through the special device the high-
frequency f ilter shown in Fig 1.13 - the MPB signals are fed to a common
autonomous network into which the feed by direct current is also input.
Requirements are imposed on the high-frequency f ilter to connect the
two networks electrically and not pass low-frequency speaking signals and
call signals to the autonomous network. The direct current feed goes to
the autonomous network from the group rectifier through the low-frequency
filter (Fig 1.14). The rectifier is fed from the household electric net-
work.
iw ~ ~ ~
I I.
L 1)_~B~ ' i .
- _
Figure 1.13. Filter circuit ~ gram
Key:
1. high-frequency f ilter
For reception of high-frequency MPB signals, the subscriber set is used,
the simplif ied schematic diagram of which appears in Fig 1.15. The high-
frequency signals are fed through the high-frequency input filter to the
detector and the low-frequency repeater. The constant feed valtage is
fed to the repeater of the subscriber set through the low-frequency filter
which does not transmit the MPB signals inasmuch as it has greater attenua-
tion with respect to high frequency. The attenuation is insignfficant for
19
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APPROVED FOR RELEASE: 2007/02148: CIA-RDP82-00850R040240040065-4
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direct current. The expediency of creating the investigated autonomous
network is especially obvious if the repeater in the subscriber set is
macle from transistors. It is necessary to have only one voltage rating
_ for operation a DC voltage to 50 volts is sufficient. The networlcs with
this voltage simplify the satisfaction of the safety engineering conditions,
. and therefore they can be made of cheaper materials. On the ~ther hand
- the receiver is also simplified. It does not contain circuits under
dangerous voltage, and the feed unit is absenC in general. As a result,
the structural design is simplified, and the ~ubscriber set becomes
cheaper. In the subscriber set designed to receive several programs, a
switch is used. A deficiency of the investigated system is dependence of
' the operation of the MPB receiving network on the state of repair of the
autonomous feed network.
_
L ar ~ ~4~ ~ -
.~1) -.i ~ ~ ~ ~ I ,Q. yNy -
1 . ~
~ ~ � ~
. ~ ~2~ ~ ,
1 ' .
� ~ ~ I " . ~ ~Ny (2) ~ -
i ~ _ ~
Figure 1.14. Diagram of a group Figure 1.15. Structural diagram
rectifier of the receiver
Key: Key:
1. group rectifier l. input
2. low-frequency filter 2. low-frequency f ilter
- 3. detector
4. low-frequency repeater
1.4. Switchboard Type Multiprogram Broadcast Systems Based on th e
Television Distribution Network
At the present time in the ~oviet Union and abroad there is a great deal
of interest in cable television systems. This is connected with the fact
that the problem of improving the quality of television broadcast and
increasing the number or programs is diff icult to realize as a result of
"crowding of the airwaves." In addition, microwave television f inds it
difficult to get along with the new civil construction with its multi-
story complexes of different heights constructed from reinforced concrete,
as a result of which the so-called "television shadow zones" and multiple -
repeated reflections of the high-frequency television signals appear.
20
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t
in addition, the movement away from individual antennas is connected with
the esthetic requirements of arch~.tecture. Collective cable television
- systems are appearing on the scale of the individual buildings, the
individual block and microdistrict of the city.
Fig 1.16 shows the structural diagram of a WB system constructed on the
basis of the television distribution network made of a large-capacity
symmetric cable for transmitting low-frequency broadcast signals. Tt is
designed for simultaneous transmission of the broadcast signals and the -
television signals to a large number of subscribers over one physical network.
Ncmoyxu ' . ~ � ~ .
� !n~/lCBt[3. Qm uC1170
HIUfCB I1lC~1~DlL3(LON.907J
(1) cuzHr.nod ~ 3ByKOBOdO OCIL(0/Ae/ldN6/X G1fltNQQOQ -
~r ( 3) Pacnpedenume~~Har~ cem~ . J
Om ucmoyau- 1
~r4~7 30 ~~46i L,- .
~ y n n~i ~Z ~t ~~t ~t ~ Z
G, Be~~TC~a- ~ I ! I
~ ' N6!X C!lzXd/M~~ J ~y~ ~
(4) c6) ~ c6 . �
~ NrN c~rrt y� po~2r,m a
/fcmOVN OCUd~UA ,
~ " �
H~n~ (5) /ra0o~eam,cxuM ycmpotit~Od~ '
. (S) meneovd~~v~ ~ `
Figure 1.16. Structural diagram of the low-frequency MPB over
- the television. distribution network
Key: ~
' 1. Source af television signals
- 2. From the television and sound broadcast signal sources
3. Distribution network
4. From the sound broadcast signal sources
~ 5. Source of broadcast signals
6. Subscriber connection circuits
7. To the subscriber broadcast equipment
8. To the subscriber television equipment
The investigated MPB system must provide for transmission of television
- and broadcast signals along the distribution line without noticeable
attenuation and absence of their mutual effect. In additian, the great
difference in frequency simplifies its realization. At the beginning of
the line only the sound broadcast signals are f ed to one pair in the dis-
tribution network made up of a large-capacity cable, and the television
and wire broadcast signals are fed to the others by means of the connection
circuit which in the simplest case can be made up of an induction L1 and
a capacitance C~.
~1
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The subscriber connection circuits which can service one or several
subscribers are used for connection to the distribution line. The inclu-
sion of the subscriber connections increases the attenuation of the ltne;
therefore the requirement of decreasing the effect of the low-frequency
devices on the television signals and vice versa is imposed on it. ~
The diagram of the subscriber connection circuit iF depic;:ed tn Fig 1.16.
It contains the inductance L2 and the capacitor C1. For low-frequency
signals the resistance of the inductance of the subscriber connection
circuit is of significar~e. For high-frequency signals the device is a
high-frequency transform This type of device provides for connecting
one or several subscribe~ sets without a significant increase in losses to
the high-frequency lines. Each indivi3ual pair of the large-capacity cable
has its own sound broadcast and television program transmitted over it.
For selectionof the program a multiposition switch is used on the subscriber ~
- end.
The use of individual circuits for transmitting each program offers the
possibility of transmitting television signals of different programs on -
one carrier frequency, getting along without selective circuits it makes
it possi~-le to simplify the receiver and to use an ordinar~ nonspeaker
For the sound broadcast programs. Thus, the advantage of the switchboard
system is the possibility of using relatively low-frequsncy symmetric
cables and simpler subscriber sets. This type of MPB system has found appli-
cation in England. _
' The investigated MPB system makes it possible to use the simplest broadcast
receivers without amplifying (active) elements in the channels, and it
offers the possibility of using coaxial cable as the distribution line,
for example, to create a matched te~evision and WB network in an apartment
building.
There are MPB systems which provide for the possibility of all-around use
not only of the distribution network, but also other elements and ~unctions
of the system, for example, transmitting station equipment and receiving
subscriber sets, as a result of which the system elements, and in particular,
the receiver, are simplified. A version of such a system is depicted in
Fig 1.17.
The distribution network is made up of the 1,2 large-capacity cable. Two
- different television programs are f ed to two physical circuits shielded
_ from each other, on the same frequency; the sources of the sound programs
which can be sound accompaniment of television programs and simply broad- -
cast programs, are connected to the circuit simultaneously.
The station equipment of the system includes the carrier frequency generator
I' on 6 megahertz. The output of the generator is fed directly through the -
buffer stages to two modulators to which the signals come from the video
program sources in the range from 0 to 3 megahertz. The modulated signal
22
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~
~
~ ~ � 3
. � . � ~
' � ' . . . . � r ~ , . . . C~S O t'+
. � . � ' 1~ O
~ ~ ' . ~ ~ ~ ~ O f~-i ~
I _ ` q�
I .n o�10 ~
. e cv ~ ~ ~ o
^ v g ~ j V�~"
' O i Q~~t ~ N N
t~ I ~ j ~y~ 'o i ~y ~ b ~ ~ ~
I ~"t ` I~ � j I o 0�1o u i
i Q~ ~ ~ .
~ ~ ~a ~n
~ __J ( j R~ ,.~.1 ,N-t u~i ~ ~
~ N ya ~
~ ~ ~ ~
~+I I~' ' eat~ I ! = y= Q ~ ~ w ~ .~E
~ ~ ----J ~ � ~
x s~
; � . u i m
~ ~ b
_ ~ ~ ~ . � , , � ~
~ y ' ' o p ~ j
v a ~ a ~ a v~ . i.i O~
~ 1~ tU M
Ol (!1 r'~ ~ r'~
v ,r~ ~ ',i~
� ~ �w
u~ b u
~ ~ aa �~a~i~ F
~ ' ~
. ~ i -
" ~ � . ~ . ' u r~~ u
~ � - 1'~ ~ ~ . � ' ' - ' y � ~ 3 O
~ ~ _ . ~ . Oal r~l
' v ` 4-~1 G~! I ,I
, i ~-''~i 1~ y'~ ~ i = ' ,~3 aa'i ao ~
L _ f"1 _ . o cv -
~ ~ ~ w ~ � . � _ ~ I ~ N
' L G! I CCl � ^ },i
v ~ ~ ^ , ~ ' , ~ r. . . J~J N i-1 C~.+ iJ
. ~O ' ~ ' . � . � O rl ~ .
a v
~ ' ~ v~ � ' . i _ ~ N LS GaJ
F+ U I (2) . I (4) .
. (6) Ay Ay ~6>
~ ~ .
Figure 2.1. Functional diagram of a wire broadcast system
Key:
1. Source of broadcast programs
2. Preamplif iers
3. Broadcast feed channels -
4. Powerful repeaters and transmitters
5. Wire distribution network -
6. Subscriber receivers
Thus, the wire broadcast system has three distinct sections (Fig 2.1).
The first section I is characterized by low broadcast signal levels. The
formation of the program and the transmission of the signal to the second
section II takes place in this section with given quality indexes.
Basic repeating (obtaining of the defined power) of the broadcast signal
takP~ place in section II with minimum distortions for the low-frequency
outgotng signal and commutation of it to the distribution network.
- 26
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The third section is the fastest section III. This is the wire distribution
network which realizes distribution of the broadcast signal power over the
cable or overhead line networks to the subscriber receivers, without intro-
ducing noticeable distortions into the quality indexes of the broadcast
signal.
- The receivers are passive subscriber units loudspeakers, which convert
- the electric signals to acoustic signals, or special receivers with active
elements. The subscriber sete are designed for the use of a defined power
of broadcast signal and reproduction of it with given quality (acoustic)
indexes.
There are several versions of constructing the city WB networks. They all
have the above-enumerated functional sections, but they are distinguished
by the volumetric indexes: the number of service subscribers, the nur~ber
of program feed channels, the extent of the connecting lines for the first
, section, the number of stations, the power of the repeaters;and transmitters
and their nu;nber, the presence of passive power distribution elements and
the number o~f transformer substations, the different types of distribution
lines and their volumetric indexes for the third section and also types of
subscriber sets used.
The investigation of the development of the WB [wire broadcasting] in the
cities indicates that the first and third sections have changed little.
Great changes have occurred in section II. The basic purpose of these
changes has been most advantageous distribution of the active elements
of the network over the territory and insurance of mutual redundancy of the
_ active and passive station equipment [3, 4, 5, 7].
Depending on the structure of the station and line installations of the
WB network, they are divided into several types distinguished by their -
structure. It is necessary to point out two types of indexes which
determine each WB network. The first type characterizes the electrical
data of all the elements and assemblies ir. the final analysis influencing
the quality of the electroacoustic parameters. The second has no influence
J on the quality, but characterizes the structure complexity of the net-
work.
Let us assume that the electroacoustic data must not depend on the type or
complexity of the network and must be insured in equal measure for.the
subscriber. This is insured by calculating t~e elements according to the
recommended procedure and the electrical design standards. Let us consider ~
only the volumetric indexes characterizing the structure.
_ The simplest diagram of the city network is presented in Fig 2.2. The
following are indicated in the diagram:
= YC WB repeater station. The complex of repeating, transmitting and
commutation equipment (the transmitters of programs II and III of the
TPB networks) is characterized by the type of repeating equipment and the
complexity of the commutation equipment;
27
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P~ the distribution feeder line. The number of distribution feeder lines
depends on the number of service points and density;
AT subscriber transformer. The number of subscriber transformers depends
on the number of service suhscribers and the density of the load;
H~ intrabuilding distribution network char~cterized by the wire length
and number of. subscriber sets;
AY subscriber set;
uCn~ central wire broadcast station realizing preamplification of the
broadcast program signals, feed of them to the repeater station and providing
for the functions of monitoring the entire WB network. It is combined
with the WB repeater station.
Tlxus, the structure of the network is characterized. by the following data: -
the number of connecting lines of the central wire broadcasting station
to the repeater station; the number of repeaters (transmitters); the
operating power P required to service all of the subscribers; the number ~f
distribution feeder lines; the number and power of the subscriber trans-
formers; the number of service subscribers N. -
, --1 ~ -
r qcna ~ c ~ .
. . ! ,5 ~I . ~
~ ~
- ~1~AT ~n ~ ~
P~ ~2
(2~- yG~6 J . .
. . . . . . (2) pT AT (1) -
. . AT ' 7 ) -
Ay
. . I . 1~c ~
~ ~ Ays~~ .
. c~~
Figure 2.2. Diagram of the centralized WB network
Key:
1. Subscriber transformer 6. Repeater station
2. Distribution feeder line 7. Subscriber set
= 3. Central wire broadcast station 8. Intrabuilding networks
= 4. Program feed connecting Zine
5. Remote control and remote
monitoring connecting line
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~ qcne~ (1) .
I I
c2~ �I ( ~~L _
. I y
(4 )
(3) ~ N~3r ~ ~6~ -
T/l, TIh T/!r 7 )
i: i i i 1
~l p': ~ p'~? ~ j''~ -
Figure 2.3. Diagram of the centralized WB network
with two-step power distribution
- Key :
l. Central wire broadcast station
2. Remote control and remote monitoring connecting line
3. Transformer substation
4. Repeater station
' S. Distribution feeder line
- 6. Ma.in feeder
7. Transformer substation
This type of wire broadcast network is called a centralized wire broadcast
network. It is characterized by the fact that the equipment performing
the function of the central wire broadcast station, as a rule, is in the
same facility with the repeater equipment and the switchboard equipment of
the repeater station. The network has only one active broadcast signal
power distribution junction.
Fig 2.3 shows a more complicated structure of the network in ~ich the
following are indicated:
~ C~T~rIrI - program feed connecting line; nwnber of them depends on the number
of programs and the number of repeaters and transmitters of the auxiliary
high-frequency programs installed at the repeater station;
C.1ITK _ remote control and remote monitoring connection line; the number of
lines is determined by the number of controlled ob3ects. In the given case
with invariant active station part of the system, the form of the power
distribution varies.
The power of the broadcast signals from the repeaters and transmitters of
~ the repeater station goes to several local distr{bution networks via the
passive distribution junctions of the transformer substations.
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- The line connecting the active distribution junction of the repeater
_ station to the passive ~unction of the transformer substation is the main
feeder line.
The transformer substation is the station passive equipment complex which
is used to transmit the power to the distribution feeder lines.
The power of the transformer substation is determined by the number of
distribution lines, their structural specifications and magnitude of the
load. In order to control Lhe remote monitoring of the operation of the
transformer substation, connecting lines are used.
Tt~e distribution network remains unchanged and is similar to the distribution
network of the system in Fig 2.2. Inasmuch as all of the notation adopted
previously is kept f~r all layouts of the network and the distribution
network is identical in structure, hereafter it will be designated simplified.
The wire broadcast network is called centralized with two-step power
distribution when it has one active power distribution junction and several
passive distribution junctions. The central wire broadcast station is _
territorially combined with the repeater station, which is illustrated in _
the diagrams by the dotted line.
Since the main feeder line operates with increased transmission voltage,
the range of the system is expanded. The voltage is stepped down at the
transformer substation using special transformers. Additional indexes
, appear in this network: the number of transformer substations, the main
feeder lines, the remote control and remote monitoring connecting lines.
Fig 2.4 gives che diagram of the WB ~network in which its station part is
altered by comparison with the greviously investigated one (Fig 2.2).
In the given case the power Pop required for normal operation of the entire
network is distributed among several objects of the repeater station with
different value of it. In this system the network structure is characterized
by two additional indexes: the repeater station power and the number of
repeater stations, and it is called the decentralized network.
The powerful repeaters are installed separately in several territorially
separated repeater stations which receive the broadcast program signals
over c~nnecting lines from a single centralized repeater station (the
- centralized wire broadcast station) which can be combined with one of the
repeater stations. Here the WB network has several active station power
distribution junctions in its makeup.
Fig 2.5 shows the layout of the network with further complication of the
structure. The broadcast program signals from the central wire broadcast
station (as a rule, isolated) are fed to several reference repeater sta-
tions at which they are repeated to defined powe and are distributed by
means of the transformer substations throughout the serviced territory. �
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: ~ : ~ucne ~ (1) ~ ~
_ ~ .
_ c2~ cnnn nr~r c3)
. c~rx) cnra~cn~;
(4) yCi ~ ~IGZ ~ yC~
- (S) p ` 1 P ads ~ p~di
L
111 ' ~it ~ 1:~ ~
~6~ . ~P~~ .~,P~~
Figure 2.4. Schematic of a decentralized WB network
~ Key: _
~ 1. Central wire broadcast station
2. Program feed connecting line
3. Remote control and remote monitoring connecting line
4. Repeater station
5. Pop
6. Distribution feeder line
. (1 . 6~11Yf T/1 � _C/1TIf Tll . ~ � -
qcne . ; ~
cann ~T~ 1 c~nn T"~ .
~ 2~ OyC, \ LO!!C
J/~ OyCt . .
\
' P%
~~~o ~!!9; M~ :
. ~3~ j ~-~r.Q,p ,
T/1, T/Ij (4) T/l, Tllt . ~ ,
~ ~ ~~~j (5) ~ sA; ~ ~ .
Figure 2.5. Schematic of the decentralized WB network with
two-step power distribution
Key:
1. Remo~te control and remote
monitoring connecting line
of the transformer substation ~
2. :;eference repeater station
3. Main f eeder
4. Transformer substation -
5. Distribution f eeder line -
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In this network layout there are main feeder lines which connect the
transformer substations to the adjacent repeater stations of the re�erence
repeater stations. This method of transmitting the signals to the trans-
formers eubstation is called two-way feed of the transformer substations.
On Eailure of the main f eeder which is feeding the transformer substation
at the given time, the distribution network of the given transformer sub-
stations switches to another feeder which has been in reserve up to this
tune.
On failure of the reference repeater station, the transformer substation
switches to other reference repeater stations. At the repeater stations
provision has been made for additional power Preserve both in the form
of a~eparate powerful repeater or transmitter and in the form of a reserve
of installed power of the repeaters or transmitters ~f the reference
repeater stations. Continuous operation of the network is insured in this
complex structure.
The city network constructed by this principle is called a decentralized
network with two-step power distribution of the broadcast signal; in
practice it is frequently called the improved three-element system. The
network has several active and passive power distribution junctions. The
- WB distribution network for this structural layout remains unchanged in
theory.
In the investigated WB network, several other indexes are being added:
the number of repeater stations of the reference repeater station; the
number of reserve main feeder lines; the powers of the repeaters of the
reference repeater station operating and auxiliary (used for reserve
for the repeaters in the given station or the rep eaters of adjacent
reference repeater stations).
Each investigated layout of the network has its own advantages and dis-
advantages. The advantages of the centralized networks can include the
following: the construction of the station in one location (where it is
easier to insure an uninterrupted power supply), simplification of the
_ ~edundancy of the active station transmitters, monitoring devices, power-
ful repeaters and their maintenance.
- Deficiencies include the following: complexity of the distribution network,
longer lines and less eff iciency correspondingly, less operating stability
of the WB network as a whole.
The advantages of decentralized system include the following: high operating
stability under emergency situations with high eff iciency of the d~stribu-
tion network, simultaneous simplification and shortening of the distribu-
tion lines and improvement of their operating reliability. The
deficiencies include the following: greater complexity of the: operation
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and maintenance of the station devices and difficulty in insuring autonomous
power supply sources. However, the last deficiency is felt less and less
in practice, for the reliability of the city power supply has increased.
'1'I~~~ modern city WB network.g are aimilar to those deacribed, and, as a rule,
ll~c~y ar~~ Ln tl~~ Lorm oL a set of the deacribed eysteme und v~ry in AccordAncc
with the development of the given city.
It must be noted that unfortunately there are no strict calculated bases
for the selection of one version or another, and the remaining, it would
appear to be obvious, principles frequently turn out to be contradictory.
Thus, centralization of the active station objects is convenient for opera-
tion and maintenance, but it implies the application of long distribution
lines having increased attenuation and frequency distortions. The applica-
tion of one powerful, high-power repeater is more advantageous with respect
to expenditures of equipment and maintenance than several low-power
repeaters. However, in a number of cases, considering redundancy, this
- leads to an unsubstantiated increase in the installed power of the repeater
stations. Therefore, the choice of the optimal WB system must be preceded
by technical-economic calculation of several versions of the station and
line structures.
2.2. Basic Principles of Constructing the Low-Frequency WB City Networks
The modern WB network in the cities is built consirlering optimal economic
and operating indexes in ac~:ordance with the specific conditions, dimensions,
configuration of the city, the number of population, and the prospects for
civil construction.
~ In the ma~ority of cities in the USSR with a popula~.ion up to 50,000 (wit~
a number of points to 10 to 15,000) predominantly centralized wire broad-
cast networks are being built with two-element distribution network. In
- this case all of the repeater, re~eption and switching equipment is concen-
trated at one station. The f irst: element of the network is the subscriber
lines which feed the subscriber ,~ets, and the second el~ement is the
distribution feeder lines to which the building networks and subscriber
lines are connected through the step-down subscriber transformers. The
rated low-frequency voltage for the city feeder lines is 120 and 240 volts.
In larger cities (population to 150,000), centralized wire broadcast networks
are being constructed with mixed construction. In such networks, as a
rule, there is one WB station in which the basic power of the low-frequency
- repeaters is concentrated. Several distribution feeder lines (from 5 to 20)
go out from the sta*,ion to supply the subscribers flf . the main residential
area of the city and une to two main feeder lines with simplif ied type
transformer substation to feed the network located in remote parts of the
_ city. Sometimes high-voltage rural type feeder lines with a voltage of
480 to 960 volts are built to supply the network of adj acent populated
areas or the suburbs.
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In cases where the construction of the main feeder line is connected with
large expenditures or technical disadvantages, to feed the network of the
remo;e part of the city a repeater substation is constructed with remote
control and monitoring and program feed from the basic station, that is,
- a decentralized network is created with two-element distribution network.
In the republic and the ma~ority of oblast centers decentralized WB networks
are being built.
The station powers are distributed with respect to several ref erence repeater
stations. Each reference repeater station feeds several ,transformer sub-
stations with a sound frequency power of 5 or 7.5 kilowatts each through
the 960 volt main feeder lines. At the transformer substation the voltage
_ is stepped down from 960 to 240 or 120 volts and goes to the distributing
feeder lines which feed the subscriber network of the part of the city
serviced by the given transformer substation.
Redundancy in which each sound frequency transformer substation receives
two-way feed from two reference repeater stations over two main feeder
~ lines is characteristic of the system. Each of these lines can be operating
or reserve. When there is damage to one of these lines the automation
response, deenergizing the damaged line and the feed of the transformer
substation is automatically switched to the main line from the other
reference repeater station which is in a state of repair. In case of any
emergency taith the reference repeater station (deenergizing, damage to the
connecting line or equipment), its load (tranaformer substation) is remotely
switched from the central wire broadcast station to the ad~acent reference
repeater station by remote control equipment.
When it is impossible or economically inexpedient to build a reserve main
line, the reserve f eed of the transformer substation located in a remote
= part of the city is provided from the substation block in which the existing
repeater equipment is most frequently us~ed.
The program feed to all the reference repeater stations, repeater stations
and substation blocks, the remote control of them and monitoring of their
operation and the operation of the transformer substation are centralized
Erom the central wire broadcast station over the so-called connecting lines,
for which the telephone pairs of the city telephone exchange especially
corrected and selected in the large ~anacity cables are used.
_ In Table 2.1 values are presented from the basic volumetric i~dexes of the
city WB networks, excluding Moscow and Leningrad.
The analysis of the volumetric indexes of the city WB networks indicates
that for the majority of the city the average number of reference repeater
- stations and repeater stations does not exceed 5. The average number of
- main feeder lines (operating) emerging from one repeater station is equal
to three, and only in an emergency, on total failure of all of the �repeaters
of the adjacent ref erence repeater station or the electric power supply
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Table 2.1
Values of index
Namc of. index Minimum Medium Maximum Units of ineasure
~Power of the repeater �
- station 5 14.2 35 kilowatt
Operating power of the 2.4 4.4 5.2 kilowatt
transformer substation
Number of transformer sub- 1 3 6 pieces
stati^.ns connected to
one re~Pater station in -
the operating mode
_ L2ngth of the main op~rating 1.7 4.4 7.6 km
f eeders
Length of the main reserve - - 13.0 l:m ~
- f eedei
Length of the distributing 1.5 - 6.0 km
feeder
Number of subscriber trans- 5 - 40 pieces ~
formers per km of line
Load of the subscriber 22 f3 97 radio pointsl =
transformers �
[1Translator's note: the Soviet name for a loudspeaker connected to a
_ local wire broadcast network.]
network feeding it, the number of simultaneously included main feedei� -
lines can reach 6. The cases of a larger number are extremely rare.
- In the cities with decentralized WB network and a three-element schematic
for constructing its linear part, the required installed power of the
reference repeater stations does not exceed 35 kilowatts, and in the minimum,
5 kilowatts, and the most frequentl.y encountered, 15 kilowatts. The
reference repeater stations are made up of standard high-frequency repeaters -
with an output of 15 and S kilowatts, the commutation and auxiliary
- industrial output equipment.
In Moscow ancl Leningrad, the reference repeater stations with a power of
60 and 30 kflowatts are widespread. They are equipped with repeater
modules with an output capacity of 30 kilowatts of specialized manufacture.
In the WB networks, light elements are used i~~ large quantity; a standard
subscriber line armature has been built, all of the basic assemblies of
the structures have been standardized, the rated voltages in the various
elements of the channel have been established.
The main distribution feeder lines, the subscriber lines and the household
~ circuits ars constructed on the basis of the specific planning and design.
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For construction there are c]ear technical recommendations. In Table 2.2
- values are presented for the attenuatiuns and the transmission coefficients
with respect to the power of sections of the WB channel and with respect
to the low frequency channel.
Ilowever, Lhe c~ptimril solut tans f~r the single-program Wii networks obtained
_ as a result of many years of generalization of experience, do not al~ays
coincide with the requirements for the MPB system.
Table 2. 2.
Attenuation Transfer co-
Segment of the channel of the ef.ficient with
channel res ect to ower
_ Output of the active circuit - input 1.5 decibels 0.9
of the distributing circuit
Beginning-end of the distributing line 3 " 0.45
Primary winding of the subscriber 1/8 0.95
transformer output of the sub-
scriber network (household network)
Beginning-end of the subscriber 1 decibel 0.98
line (household line) of the network
(at the end of the line)
Total attenuation 4 decibels -
Total power transmission coefficient - 0.38 ~
2.3. Basic Principles with Respect to Creation of the MPB System
The necessity for creating the MPB system in the USSR was caused first of
all by the multinational structure of the population of the country, the
- requirement of providing the WB listeners of the union, autonomous
_ republics, autonomous oblasts with full-value natir~nal programs without loss
of the union programs. In those parts of the country where broadcasting
is in one language, the in troduction of MPB permits noticeable variation.
of the transmission considering the interests of the individual population
groups.
- The creation of the MPB has required the consideration of the state of the
technical level of the communication means and a number of social and -
economic conditions arising at the beginning of the 1960's. These basic -
principles are reduced to the following. A widely developed WB system has
come about in the country with a multimillion fleet of simple, cheap single pro- _
gram receivers (by the end of 1962, there were 32 million of them). The -
system has recommended itself as sufficiently reliable for information
transmission, and it was for ma.ny subscribers the only source of operative
information and high-quality broadcasting. At the same time the city
_ telephone exchanges at that period were inadequately developed. Under these
conditions it would be most correct to solve the problem of MPB in the
USSR only by creating it on the basis of the single-program broadcast net-
work using a low-frequency channel.
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The next argument determining the mass nature and popularity of the MPB
system :[s ttie~�cost of the subacriber receiver. It must not eignif icantly
~+xr~~~~~i t I~t~ ruN~ ~~f rhe a In~IP-proqram .inudA~~tikar and muwt ~18 16flH thai~ tlie
l.lit~ ~�lu~,i~~ r~ullu I?r~~~ei~IcuNt recclvcrr+ tliemd~lve~A. Unl.y unclrr Huch -
ccmciltlonH 1H lt poRaible ~o count on tl~e mase production uf tl~e MPB aystem. -
According to the economic requirements the MPB system must be introduced
with minimum capital expenditures and not cause significant additional
operating expenditures.
The end of the 1960's is chdracterized by broad application of electrovacuum
devices in all the technical means of air and wire broadcasting and the
beginning of use of transistors in the individual equipment developments
willi I~?w nut~~ul ~~~~w~~r, rt~latively nan-~w hand nf re~rndii~thle fre~uettries
:in~l I~iw c~uotl.lly Iii~IE`XE'f~.
Use of the single-program broadcast networks as the base for creating the
MPB system required mutually matched decision ma.king between the existing
low-frequency channel and the auxiliary program channels of minimum possible
mutual loss for each of them.
The WB networks developed in the cities are different, and the MPB system
must be inscribed with minimum devi~ations in these versions of building the
networks. Requirements of insuring higher quality indexes than the indexes
achieved during radio broadcasting in the long and medium wave bands,
guarantees of given auxiliary program signal levels at all of the subscriber
WB points for various types of wires (bimetallic and steel), in the
presence of cable entries, for the distributing network of different con-
figuration (with different number of f eeders, different extent of the
distributing feeder lines and different density of the subscriber trans-
formers) are imposed on the MPB system. -
In addition, it is necessary to insure sufficient mutual, protection between
the air broadcast and the WB systems. The introducti~n of the MPB system _
based on the single-program WB network requires the development of the
remote control and remote monitoring systems.
It is necessary to provide the MPB system with additional high-quality,
reliable sources and channels for transmitting the broadcast programs. The
discussed basic principles were adopted as the initial prerequisites when
creating the Soviet MPB system.
When creating the MPB system it is necessary to determine the following:
number of transmitted programs, the carrier frequencies, the type of modu-
lation, the levels of the high-frequency signals in the WB channel consider-
- ing electromagnetic compatibility with the radio broadcast and communications �
- systems, the versions of constructing the MPB system for the various '
structural layouts of the WB network; the quality class of the high-frequency
channels of the MPB system and standardization of them. '
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= 2.4. Number of Programs, Carrier Frequenciea and Type of Modulation
The indicated characteristics are completely determined by the possibilities
of the single-program wire broadcasting system and obtaining the minimum
cost of the subscriber receiver. The transmission of the low-frequency
signal at high levels over the overhead wire network determines the possible
range of frequencies for creating additional channels. This frequency _
range is bounded below by the frequency spectrum of the low-frequency pro-
gram with upper normalized frequency with respect to quality class I of -
10 kilohertz, and it is bounded at the top by the beginning of the long- -
wave band a frequency of 150 kilohertz. Considering the high signal
levels of the low-frequency program and, consequently, the significant
levels of the harmonics of the low-frequency signal, it is necessary to
" separate the spectra of the high--frequency signals from the low-frequency
signals.
Theoretically, considering the possible filtration of the harmonics of
the low-frequency signal at the output of the low-frequency repeater of
channel I, it is possible to use the frequency range beginning with
30 kilohertz. In adopting the frequency range to the beginning of the
long-wave band of 10 kilohertz, it is possible to consider that for fre-
quency multiplexing of the WB system there is a frequency band of 30-140
ki.lohertz. When transmitting programs with two-band amplitude modulation
_ in this frequency band with a reproducible frequency band of ~F=6 kilohertz
corresponding to quality class II of All-Union State Standard 11515-65 and
with frequency clearance between the channels of 3 kilohertz, the number
of possible transmitted programs n determineifrom the condition
140 - 30 = 2A F n-}- 3(n -1), ~ 2,1 ~
is potentially seven.
The obtained number of MPB channels is potentially possible on their recep-
tion on the superheterodyne type receiver which similar with respect to
- cost to the radio broadcast receivers. Actually, the number of possible
_ transmitted programs with the WB network decreases significantly in -
connection with a reduction in the actually admissible frequency band for
the MPB purposes.
This reduction on the part of the lower part of the frequency band is
caused by the presence of significant additive interference fram the low-
frequency channel sufficiently noticea.ble in the frequency band to
100 kilohertz although this interference could be appreciably reduced by
installing the corresponding low-frequency filters at the input of the
main and distributing feeder lines connected to the low- frequency repeater.
- The most significant obstacle to the use of low-frequency part of the
free frequency band is significant increase in the multiplicative i?ter-
ference from the low-frequency channel increasing with a decrease in the -
carrier frequency. The cause of the appearance of this interference is -
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the presence af distributed and concentrated nonlinearities in the WB
channel which tlie steel wire and poor contacts have.
The solution to ti~e problem of modulation and demodulation with the simplest
~w~~-I~anJ Ampill�uclc ?nodululion preaents known diFficultie:~ with a low rutto
of ttie carrier and tlie modulating frequenciee. In addition, a further
diff iculty in the use of this part of the frequency band is the more notice-
able difference with respect to the conditions of transmitting the upper
fB and the lower fH side frequenciQS. The difference increases with an
increase in the ratio
~ t~it~ = cto + Fa~c~o = F~. ~ ~ ~ ~ 2 . 2,
where Fg is the higher modulating frequency; f0 is the carrier frequency. -
With an increase in the carrier frequency the indicated ratio approaches
one, which indicates the equal conditions of the transmission of the side
frequencies of the AM signal spectrum. It must be noted, for example,
that the transmission of the 15 kilohertz modulati.ng frequency band with -
the least carrier frequency of 178 kilohertz over a uniform matched telephone
pair in the Italian MPB system is simpler than the transmission of the
6 kilohertz modulating frequency band with a carrier frequency of 78 kilo-
hertz over a, nonuniform, branched wire broadcast network in the Soviet
TPB system, in spite of the closeness of the ratios fg/fH for the given
cases.
- As is known, increasing the difference in the transmission conditions of the
upper and lower side frequencies corresponding to one modulating frequency
leads to an increase in the nonlinear distortions of this modulating fre-
quency on reception.
The limitation of the actual frequency band for the MPB in the upper part -
is caused by the greater damping of the WB lines in this frequency band
and the nature of the appearance of mutual inferf erence with the radio
broadcast long-wave bands.
On the whole, the use of the possible frequency band with a frequency of
f~X 140 kilohertz and fmin 30 kilohertz for the ratio of f~~/f~iri 4.7
presents significant difficulties from the point of view of insuring the
optimal transition conditions for all the MPB programs, As an exa.mple it
is necessary to note that the ratio f~ /f~in in the Italian MPB system
on transmission of six programs is f~X~f~iri 358/163=2.2; in the Swiss
system with this number of programs, with the reproducible frequency band
of 10 kilohertz, fmax~fmin 350/165=2.12 respectively, at the same time as
in the ~.dopted Soviet TPB system for two programs transmitted on the
high-frequency spectrum and the reproducible band of 6 kilohertz, this _
ratio is 126/72=1.75.
39
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Thus, the presented arguments indicate the necessity for constricting the
frequency band for transmission of MPB programs and conversion of it to
tl~e upper part (to 120-130 kilohertz.
Un ~lie otlier t~and tlie requirements following from the necessity of creating -
a simple, inexpensive subscriber receiver lead to somewhat different conclu-
sions. The complexity, cost (C) of the receiver are related in a defined
way to its input parameters: _
, 17
L' . r es fot rloi
- ~ l~ 2.3
~ \Vorz ~ foi ~ U ( )
oa /
(2) - .
Key: 1. input; 2. 0 input -
where Zinput is the modulus of the input impedance of the receiver;
UO in~ is the sensitivity of the receiver; fpl, f02 are the carrier fre-
- quencies of two adjacent programs (here f pl
~
Thus, for further investigation of the process of the appearance of
multiplicative interference, it is possible to take the following simplified
model of the transmission channel (Fig 2.25), in which i~(t) is the low-
frequency signal current in the line; ew(t) is the emf of the high-frequency
signal source (transmitter), Zg is the wave impedance of the steel line
matched at the end. For the circuit it is necessary to determine the
voltage uw(t) at its output:
um~~ Z~~ ~Q~t)].-~-zs e~~t~~ ~2.10)
i.~~ ZA~liQ lt~J .
~ft,, . .
- ~ Za
ti .
Figure 2.25. Equivalent diagram of the steel line for determining
the multiplicative interference
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As the initial signals let us zake the voice-frequency, low-frequency
- signal:
. iQt~=lQcosS~,~t ~ (2.ii>
and the amplitude-modulated signal with modulating frequer~cy SZ2:
em = E~ tl m cos S2s ~ cos ~a t. ( 2. i2)
Considering that ZR is proportional to the length of the line, and Zg is
constant, and consi~ering the cases where the lines are sufficiently long
and the interference is large and also considering the different nature of
the resistances ZRW close to inductive and Zg close to active, it is
possible to consider Z~w�ZB and neglect the value of ZB in the denominator
(2.10).
Using expressions (2.9), (2.10), (2.11) and (2.12), we obtain
~ . � . -
u~, = Eo (1 -i- m cos S?~ t~ cos cuo t .Z, -
. . . . ..1
~ : ~ ~ ~ . ~ ' . ~ . ~ ~ � . ~ a bIQ coss Ql ! ' .
= E�'Z, ra (1 -I" m cos Sts ~-f- Z bIQ (1 oos 2SZi t~-~-
~
: -I- 2 bmlQ c~os St, t I bmlQ cos(2S?,~-~- . . ~ ' '
. 4 -
-I- S?,~ t -F- ~ 1 bml
~ cos (2St1- 52~ f cas.~ t ~ - . .
. _ 4 , . .
. . . . , . (2.13)
,
Expression (~.13) is an AM signal, modulated, in addition to the useful
frequency 522, by the frequencies connected with the frequency of the low-
frequency signal: 2521, 2S21+S22, ( 2S21-SZ2
The obtained AM signal spectrum at the output of the investigated channel
is presented in Fig 2.26.
The noise/signal ratio at the output of the receiver for interference with
a frequency of 2521
~ � ~ b1Q _
v~s~ = 2 1 ~ ~ (2.i4) -
� ~ . . . ~ Ca + Z. b~~ !
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;~nd fur inter~erence with �requencies of ~ 2S2L+S~2 ~
~ � - 1 8d~ � . � . . . , :
. ' Il/S = 4 . � ~ . . - : (2.15)
. ~ . ~ : . ~ . a -E- 2 b!Q - . . : : .
. , . , . . . = ,
' . ~ : � . _ . , ~ . . ' . .
, _ . ~ . ~ ~ _ .
. - . . _ .
� , . ~ . . . - . � - .
~~~*Q~ ~r
p~i ~i~~ ~~~t ~i ' ~'Qt ~+~i
~s~ ~if2Q~ Cv,K1Q~+~~
~ > ~ /lDaex~c (1) /laoa.~we~~i c~raNQ~ (2~ ' /Icwe,~r~c ~3~
Figure 2.26. Spectrum of the AM signal formed on joint transmission
of the AM signal with the carrier frequency wp,
the modulating frequency SZ2 and the low-frequency '
signa.l with frequency SZl over steel wires
Key:
1. Interference
2. Useful signal
3. Interference
For high nonlinearity, when (1/2)bI~�a, the exp~essions (2.14) and (2.15)
acquire the following form respectively:
~N/S 1 ~ . ~ (2.16)
and ~ ~ - ~M
- ' .`~~S = ~ . (2.17)
. 2 .
Expressions (2.16) and (2.17) must be considered as the maximum worst value
of the N/S ratio. In r~ality, for steel wires it is posaible to consider
the nonlinearity small, for it in practice does not create nonlinear dis-
tortions of the low-frequency signal, that is, it is possible to set
a� (1/2)bI~ and the exgressions (2.14), (2.15) assume the form:
~1/S - 2 ~ ; . : (2.18)
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N~S = 4 a ~s . (2.19)
Thus, the noise/signal ratio depends on the nonlinearity b/a and sharply
(by a quadratic law) on the low-frequency current (interf ering current)
of the signal, and it does not depend on the amplitude of the AM carrier
signal. The magnitude of the interference with frequency 2521 does not
depend on the presence of the useful modulation, the values of the inter-
ference with. frequenc~es of ~2StL�S221 are proportional to the depth of the
useful modulation. Therefore, for frequencies of 2SZ1 the noisei signal
ratio and, consequently, the noticeability increase with a decrease in
depth of the useful modulation (Fig 2.27) and in the useful signal interval
it will be the worst case, and for frequencies of ~ 2S2L+SZ2I the noise/signal
ratio remains unchanged (Fig 2.28); the interference disappears together
with the signal in the interval. The pres.ented arguments indicate that
the interference with the frequency 2St1, especially in the useful signal
interval presents the greatest danger. The investigated noise/signal
ratio pertains to all the levels of the useful signal in the dynamic range,
- for it permits estimation of the noticeability of the interference for
any levels (depth of modulation) of the useful signal.
~ - ~
C ' ~
: 1 7
_ . . . ~ . .
. _ . . . � .
~It ~ . � ~
.
. . p . 1 01
. , ;
. - �1 ~ . _ . . .
Figure 2.27. The noise/signal ratio Figure 2.28. The noise/signal rat,io
as a function of depth of modulation as a function of depth of modulation
m of the useful signal for the m of the useful signal for inter-
interference with a frequency ference with the frequency of
2St1 I 2~~~2I .
Hereafter the given noise/signal ratio will be called the instantaneous
ratio; in contrast to it, the assumed normalized ratio of the interference
in the useful signal interval to the rated magnitude of the useful signal
_ will be called noxiaalized (N/S)n.
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The ratio (N/S)n 0 for interference with frequencies of ~ 2St1+St2 but
this does not indicate tha actual noticeability of this type ~f inter-
ference. .
For interference frequencies of 2St1 ~
, ti~i'S)n = 2 Q~~ ~ . (2.20)
- Key: 1. max ~ . . ~1~
- Zk,m . _ . ~ t,~#~ . . .
- - .
. . i
. . . I ~ .
. . _ . . ; . - ~ . ' . �
, . ' . . _
.
~ . . . � - ~ S j T'~,'~i t
' � ~ P'
. . ; .
~ . - -
M'
~w
Figure 2.29. ~ Variation of the Yine resistance with respect to _
high-frequency under the effect of a low-frequency
signal current
The graphical representation of the origin of the interference with a
frequency 2521 is illustrated in Fig ~.29. In one period of variation of
the low-frequency s~gnal current the resistance ZQ~(t) varies twice as
frequently as a result of symanetry uf the function Z~w (I) Uith respect to ~
the y-coordinate axis. This modulation of the resistance ZQW with double
interference frequency also leads to the appearance in the AM signal
spectrum of interference with a frequency of 2SZ1. Thus, it is possible
to consider the process of the appearance of multiplicative interference
in steel wire the result of parametric modulation by variation of the
resistance ZQW by the law ,
. . . ~
~ Z~ _ - z � .
_ a~+ ~'~s ~t~ .
The presented process of the appearance of multiplicative interference with
a number of simplifications reflects only one energy ~spect. On the whole, ,
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the multipld.cative int.e,~forence of the steel wire must be defined as the
f unc tion N/ S= IQ ~ l~ Fl ~ where k is the length of the line; Fl is the
. ~
fo
low-frequency si~*nal frequency; f~ is the given carrier frequency. The
analytical representation of the dependence of tlie magnitude of the non-
linear crosstalk interference on the ratio of the low-frequency and high- ~
frequency signal frequency presents great complexity; it requires determina-
tionof the frequency dependence of the ferromagnetic properties of the
steel wire and at the present time has not been obtained.
The experimental dat~ obtained clearly indicate the dependence of the
relative 'level of the crosstalk interf erence (N/S)n on the low-frequency
signal current,and the frequency ratio (Fig 2.30) also confirms the
quadratic dependence of the crosstalk interference on the low-frequency
signal current.
The noticeable dependence of the nonlinear crosstalk interference on the
length of the line is manifested under the condition ZR~>ZB; therefore, it
is possible to consider that for steel liaes ~aith load at the end, the _
magnitude of the crosstalk interference increases proportionally to the
lize length (for a length of more than 1 km). For the ma~ority of actual _
distributing fe~der lines with distributed load on the line the crosstalk
interference does not increase proportionally to the length, for in each
subsequent section the low-frequency signal current decreases ~~d at the
sas.e time the increment in the interference with respect to the ui~-
branched li~e decreases. _
~1jG/~ : . , - ~
, 1~p6 .
1 ' ~3~ . .
. ~ ~�~r- .
4~~1 ~ fM - y6nl~ (4 )
fQ~7BKtq ~5)
/
..4~ j � f ~?OO~q ~6 )
2) ~ -
~1 oC~' ! . _
~p ~ ~i
a / . ~ -
/ ~
~1 i .
/ ~ i~ ' !7l
~ i ~ .~.~i�~-
_ 0 -as ' ~0 I~,A
Figure 2.30. Relative level of the crosstalk interference on
steel lines for ordinary amplitude modulation
~ (line length 4 km, load at the end, steel wire
4 mm)
Key:
1. (N/S) ; 2. 4000 hertz; 3. F1=1000 hertz; 4. f01=46 kilohertz;
_ 5. f~2=7~ kilohertz; 6. ~1=200 hertz; 7. I~, amps
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'I'lic CCUHHCFIIIC interference thnt nrises betwc~en tht~ lilgii-frec~uency 9tgI1A1.A
as ~l result of nonlinearity of the wires is negligibly small as a reault
- of the small currents of the signals. The line trarisformers in practice
do not introduce crosstalk interf erence, which is explained by the weak
influence of the ferromagnetic material of these transformers on the
transmission coefficient on the carrier frequencies. -
Another cause of the appearance of nonlinear crosstalk interf erence in the -
lines is the poor contact .at the points of connecting the wires having
nonlinear properties. The mechanism of appearance of multiplicative inter-
ference in the poor contacts is analegous to the appearance of cross- _
- modulation in the nonlinear elements (tubes, transistors).
The devices in which muZtiplicative interference occurs include the trans-
mitters and tandem (intermediate) high-frequency signal repeaters. In the
transmitters the nonlinear crosstalk interference occurs in the output
_ stage, as a rule, between the high-frequency signals by crossmodulation in
the nonlinear amplifying elements or f erromagnetic high-frequency trar~sformers.
In the tandem repeaters this , ~e of interference occurs in the input and
output amplifying stages. How~;*er, the interference level created by these
devices is 1ow and can be reduced by increasing the selectivity of the input -
~ and output frequencies separating circuits. _
_ Ti?e additive interference in the WB channel can occur as a result of direct
incidence of the outside signals in the low-frequency signa.l spectrum,
incidence of the foreign signals in the AM signal spectrum; reception of ~
foreign signals not entering into the spectrum of the useful AM signal,
with insuff icient selectivity of the receiver.
The additive interference with direct ir..cidence of the outside signals in
the spectra of the useful low-frequency signal can appear in the low-
frequency program feed channels at the WB statior by line crossovers
between adjacent lines. On the receiving side, this type of additive
interf erence can appear as a result of the incidence of the low-frequency
program signals from the input of the receiver at the input of the low-
frequency repeater of this device. Thus, this type of additive interference
appears before and af~er the multichannel TPB channel.
The second type of ad~?itive interf erence incident in the AM signal spectrum
appears in cases where the WB network recei=-es (the antenna effect) signals
of other services operating in this frequency spectrum. In addition,
this interf erence is also manif ested as a result of the low-frequency
signal harmonics incident in the transmitted spectrum of the AM signal.
As a rule, this additive interference is unintelligible.
The third type of additive inter�erence is manifested only in the channel ~
_ of the receiver and can be expressed in the form of hearing adjacent channels
of the TPB system and also the WB stations.
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_ 'I'li~~ lnt~~rfcren~~~~ c~l tl?~~ hiickhround un~ no~yi~ lypr oi~ th~~ htglrLrequcncy
cl~auiiels is maniLested only in tlie AM signal receprlon nnd tranamiysion
devices.
In th~ receiver the background and noise appear basically in the low-
frequency channel. Considering the quite high signal levels of the TPB
system, the noise level can be neglected and the background level con-
sidered.
- 2.11. Methods of Decreasing the Interference with the High-Freq~sency
Channels of the TPB System
The procedures for decreasing the int~rferance of the high-frequency channels
are determined depending on the nature of the origin of the interf erence and
the location of its occurrence. The most important role in the existing
TFB system is played by multiplicative interf erence from the low-frequency
channel to the high-frAquency channels occurring basically in the li:ne part
of the WB channel.
.The necessity for decreasing this nonlinear crosstalk interf erence is
deter~ir~ed by the fact that its magnitude greatly exceeds the other types
of interf erence, and the methods of decreasing it are not simple.
The physical process of the origin of this interference was investigated
above, and by using some simplifications, the analytical expressions were
derived for the noise/signal ratio (N/S).
The magnitude of this interference basically determined for ~he steel lines
by the low-frequency signal current, the line length, the frequency ratio
of the low-frequency signal and the carrier. Consequently, the decrease
in nonlinear crosstalk interference from the low-frequency signal can be
achieved by decreasing the indicated paramefiers.
The simplest and most obvious means of significantly decreasing the nonlinear
crosstalk interference would be replacement of the steel aires by bimetallic
wires, which would lead to a decrease in attenuation of the high-frequency
signals. However, this replacement would require great expenditures of
copper and means on rebuilding the WB network.
Hereafter it is proposed that the WB networks be converted to cable lines,
and the situation with nonlinear crossta.lk interference will improve
significantly, but in the first stage of introduction of the TPB system
an~i at the present time the steel feder lines are a reality, and this
reality will exist for a significant time to come, Therefore, other solu-
tions to this problem are needed. _
- The dependence of the crosstalk interference and the attenuation of the
high-frequency signals on the line length proposes the problem of reducing~
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- tlie length of the steel lines. Ttiis solution would require rebuilding the
TPB network in the direction of increasing the number of such station sites
~s tl~e tranaformer substations with A reduction in the service radius of
cacli substation. tt ls natural ttiat tl~le solution too would require lurgc
expenditures of ineans and time of its implementation.
Thus, the solutions with respect to redesigning the WB network in one form
or another, in spite of the radical -improvement of a number of indexes of
the TPB system could not be adopted, for ~hey would.require significant
- ma~erial means, capital investments, reconstruction operations and time.
Therefore, the search for the solution of the given problem will be aimed
at electrotechnical measures. -
Considering the significant dependence of the given crosstalk interference
on the low-frequency signal current, a solution to the problem can be a
decrease in this current. This is achieved by using the low-frequency
GT repeater for amplifying the low-frequency signal ("active version"),
which permit~ a significant increase in the input impedance (to 30 kilohms)
of the GT when receiving the low-frequency signal. The effectiveness of
applying the "active version" is determined by the volume of its introduction. -
In addition to the solution to the problem of reducing the low-frequency -
signal current in the overall WB network, the introduction of the "active
version" will permit a decrease in this current in the individual sections
of the subscriber network, which, in turn, will lead to a reduction in the
nonlinear crosstalk interf erence in these sections as a result of poor
contacts.
The noise/signal ratio for the basic interference with a frequency of 2521 -
according to (2.18) will be defined by the expression
s/N.
_ 1 6 Js
~ ~ 2 am Q~ ~
Consequently, on reducing the low-frequency signal current I~ by n times
the N/S ratio decreases by n2 times, and the normalized signa/noise ratio
expressed in decibels
(S/N)' = S/N + 401g n, (2.21)
where S/N is the initial signal/noise ratio, decibels, before decreasing
the low-frequency signal current.
Thus, if we take S/N=30 decibels, the value measured on the steel lines,
as the initial ratio, then assuming potentially n=10, it is possible on
steel lines to obtain a value of (S/N)'=70 decibels, which corresponds to .
the class II requirements of All-Union State Standard 11515-65 for channels
with respect to the signal/noise ratio.
80
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~
'Cl~r m~~tlwJ:+ ut cl~.creusing thc cros~tulk luterference Kucli ~A tite upplleatiott
of Lrequency modulation and single-band modulation without carrier,
increasing the carrier frequency, the introduction of frequency distorti.,:.~
on the transmitting side were investigated and partially tested. The
application of frequency modulation required significant expansion of the
transmitted frequency band to 60 kilohertz for one channel. A decisive
deficiency of the frequency modulation and signal-band modulation without a
carrier is complication of the subscriber receiver.
Increasing the carrier frequency of the high-frequency signals permits a
reduction in the level of the crosstalk interference in connection with an -
increase in the service effect for the high-frequency signal current and
correspondingly a decrease in the magnetic i~teraction in the stee~. wires
_ of the low-frequency and high-frequency signals. However, a significant
increase in the carrier frequencies of the high-frequency signals is impossi-
ble as a result of an increase in the attenuation and limited na*_ure of the
free frequency range before the beginning of the radio broadGast range.
Some increase in the signal/noise ratio can be obtained by a~a increase in
depth of modulation according to the expression (2.18) on frequencies in
sound range having reduced level, that is, by introducing distortions in
the form of a rise in the level of the upper modulation frequencies in the
transmitter with the corresponding reduction of it in the receiver.
The effectiveness of this method is highly limited with respect to magnitude,
on the order of several decibels, and with respect to frequency spectrum
above 2-3 kilohertz modulating frequencies.
Under these conditions the most acceptable turns out to be the method of
decreasing the cross talk interference by using amplitude modulation with
an adjustable carrier frequency amplitude proposed by L. Ya. Kantor when
developing Soviet TPB system [1].
Decrease in the Nonlinear Crosstalk Interference by the Application of
an AM Signal with Adjustable Carrier Level
The basis for this method is the proportional dependence of the crosstalk _
interference at the output of the receiver as a function of the carrier
_ frequency level.
Beginning with expression (2.13), the amplitude of the interf erence _
, envelope with a frequency of 2521
1 z .
U~a = 2 bIQ~Z.Eo. ~z.z2~
Consequently, decreasing the amplitude of the carrier frequency E~, it is
~ possible to obtain the corresponding decrease in the crosstalk interference
at the aitput of the receiver.
81
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However, this should not be understood as a decrease in the initial rated
voltage with constant carrier frequency voltage, for in this case,
according to expression (2.18) no gain takes place with respect to the
nai4e/signal ratio.
A decrease in the noise/signal ratio with ad~ustable carrier frequency
voltage can be achieved with respect to the constant voltage of the carrier under
the condition that all the levels of the useful broadcast signal at the
output of the receiver remain the same as for constant carrier voltage.
Inasmuch as the signal at the output of the receiver is determined for
linear detection by the magnitude of the AM signal envelope Uenv, in
order to reduce the constancy of this value it is necessary that the
following condition be satisifed for any signal level:
Uor ~~IltpUp = 1rizUpx, ~2. 23)
Key : 1. env
where mp is the depth of modulation corresponding to some level of the
broadcast signal, with constant voltage of the carrier frequency Up; mX is
the depth of modulation corresponding to the same broadcast signal level
with unchanged carrier frequency voltage UOx�
From expression (2.23) we have the basic condition of proper voltage
regulation of the carrier freque:~cy:
Uo m~ .
U~~ - ~ (2. 24)
The noise/signal ratios for some level of broadcast signal with constant
carrier voltage (N/S)p and variable carrier vol'tage (N/S) X can be
represented in the form:
.
� (N/S) = 1' b J2' Vo -
~ 2 a maUo . (2.25)
~y~a = 1 6 ~ U�r
X 2 a~' mxUox ~ ~ 2. 26)
~
Consequently, a decrease in the noise/signal ratio with adjustable voltage
of the carrier UpX with respect to the constant voltage level
' ~~/S)X/ ~N/S~~ _ Uox ~
~Uo (2.27)
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The signal/noise ratio expressed in decibels for any voltage of the
carrier frequency UOx
_ ~s ~ `~5~-~ ~o~ -
yl + g ~ . c2.28>
: o uc
Inasmuch as the initial voltage of the carrier frequency with maximum
broadcast ;signal remains uncl:anged and is maximal, the degree of increase
in the ratio (S/N)X is determin~3 by the decrease in voltage for the
reduced le~vels of the broadcast signal. Graphically the function (S/N)X=
`~~UO max~UOx~ is presented in Fig 2.31; the crosshatched region corresponds
to the additional gain with respect to the signal/noise ratio.
_ (~)X a6 . . _ . . .
cl~ ~
~~)o ! .
. ~2~ , . . . . _
. . . .
. 1~.:. 6 ~ . . . 10 ~ -
� _ � - . ox
Figure 2.31. Signal/noise ratio with relative reduction in
carrier voltage
Key:
1. (S/N)~, decibels
2. ~S/N)0
3. Up max~UOx
It is necessary, however, to note that the adjustment of the carrier frequency
voltage does not permit a decrease in the second type of interference with
the combination frequencies ~2S21�SZ2~. This form of interference is propor- _
tional witil respect to its magnitude to the amplitude of the envelope AM
of the signal mXU~X which remains invariant with respect to the condition
(2.23) for any level of broadcast transmission on variation of the carrier
voltage. Cansequently, the noise/signal ratio for this interference remains
unchanged when regulating the carrier frequency voltage.
The regulation of the AM carrier signal voltage beginning with what has
been stated cannot be accomplished other than as a function of the level
of useful modulating signal U~.
In general form the law of this regulation "
UO - ~ ~UQ~ (2.29)
can take any form when observing the condition (2.23) and the condition -
83
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~;~X. The gain with respect to the transition interference for any level
of broadcast signal would be determined by the form of the regulating
function (2.29); therefore, it is important to discover the limiti.ng form
of this function given the greatest gain with respect to the crosstalk inter-
ference. According to (2.28), the gain with respect to the interference is
proportional to a reduction in the carrier voltage; consequently, it is
necessary to determine the maximum possible voltage of the carrier frequency
for any value of U~. On making the transition from the constant carrier to
variable, the voltage of the variable carrier ~for any level of the broadcast
signal
' Uos - m jJo, (2 . 30) -
Considering that with the DC carrier m~=nU~, where n is a proportionality
coefficient and that for the greatest decre~:~e in voltage UpX it is
~ necessary to observe the condition mx=mmaX const and also considering the
initial unregulated voltage UO=U~ ~X, we obtain
~ ~o t~exc U
jf~ = s, ~2.31>
Key : 1. max ,
- that is, ~
U~ = kUQ~ (2. 32~
where k = ~0
~~'x~ �
~.+rucc (1) .
Key: l. max
Thus, the most advantageous witti respect to interference is the rectilinear
function U~X(U~) known as amplitude modulation with constant modulation
coefficient (C:~IC). In Fig 2.23 and 2.33 graphs are presented for the
functions Up=~(U~) and m=~,(U ) for the AM signal with constant carrier and
CMC, where UO rated~ mrated~~S2 rated are the rated (maximu~ values of i:he
carrier frequency voltage, the d~pth of modulation and the low-frequency ~
signal voltage at the input of the receiver respectively. After obtaining _
the optimal relation for the carrier voltage as a function of the modulating _
signal voltage, it is possible to compare the function (N/S)X f(U~) for the
AM signal with DC carrier and CMC for interference with the frequency
of 2521.
For constant carrier . ~
r1 _ 1 blQt_ l~b~`~ ~
_ ( S ` Z ant 2 a . ' ( 2 . 33 )
~
84
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thal iy . � � .
N ~
~ (~}o =,U~ � (2.34) .
where N=(1/2)(b/an)I2S21 is the generalized proportionality coefficient.
~ . . ~ .
~ ~ ~
_ . U i
�
u,~ - . , ~
~l m ~ ~
- - .
~ ~ : . . , ~
.o -
. ~ ~
~ : ~ ~ ~.1)
Figure 2.32. Depth of modulation as a function of the magnitude
of the modulating signal with constant carrier
Key:
1. rated
� - - . ~ � . ~ ,
~ . ~ � . ~ :
. - �
U~ .
. (1) m ~ .
m,r,~,
_ (1) , $ ~ ~
: I
. ~ _ . . ~
. . . . . : ~i~.
Figure 2.33. Carrier voltage as a function of the magnitude
of the modu3.ating signal with a constant modulation
coef f icient
Key: ~
1. rated ~
For a:variable~carrier -
t b U~ ~ 1 b ~Q r~
1 � CL.35~
~1s a.~' ~z~1os 2 a f~j knetu
~ . . .
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Consequently
� ~ s t((JQ~~ a COI1St. (2.36)
cs .
~
- Thus, whereas with a constant carrier the N/S ratio and the noticeability
of the interference increas~s with a decrease in the broadcast signal level
and reach a maximum in its interval, with CMC the noise/si~naZ ratio re- '
mainds unchanged.
In Fig 2.34 the functions N/S=f(U~) are presented for constant carrier and CMC.
~ : . .
. ~ _ . . . ' �
m~~'On~st -
~ ' ~ �
� - , - ~
� . ~
Figure 2.34. Graphs of the noise/signal ratio as ~~unction of _
the magnitude of the modulating sigaial with constant
carrier (U~=const) an3 CMC (m=const)
Key:
1. U~, kilohms -
The total magnitude of the noise/signal ratio for all interference with _
frequencies 2521~ 2S21+S~2~ ~2St1-SZ2~ With CMC do~s not depend on U~, and it
is determined by the following:
. ~ (i) ~ (1) -
_ - _ (t7 ~ -
. ~~,�+C ~ s + .C ~_Q a.
. . . ~ , \ II~ , ,I .
. . ~ z~ c~~ ~2~
~
a r2~ JQl I b~i 1 b~' ~ ~
. , : ` ~ ~4 a , . C4 a
~
. ~ ~ b ~ . 1 ~ . ~ .
1
~ a j~! ~ m ~ � . . (2.37)
Key: 1. N; 2. S
The total value of (2.37) exceeds the noise/si nal ratio for the basic ~T
interference with a frequency of 25~1 by oniy 3/2-1.22 times (1.85 decibels)
for a value of m=1.
86
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The normalized ratio of the rated signal to the interference in the broad-
cast transmission interval
r-s- ~ 2~:Cr.uc Ue Nnclo (2. 38)
bJQ U~ m ~2) .
Key : 1. max ; 2. min
where U~ ~n is the carrier voltage in the broadcast signal interval.
In the existing TPB system the ratio U~ ~/U~ m~=10, which permits an
increase in the (S/N) ratio by 20 decibels and bringing it approximately
from 30 to 50 decibels for steel lines up to 6 1~ long.
In spite of the fact that the indicated method of decreasing the nonlinear
crosstalk interference was obtained on the basis of investigating the
interference in steel wires, it is also applicable to any type of nonlinear
interference occurring in the TPB system whether from the low-frequenny
signal to the high-frequency signal or between high-frequency signals, at
poor contacts, at the output of the transmitters, and so on. This is
explained by the fact that in the majority of cases the spurious modulation
takes place with constan*_ modulation coefficient which does not depend on
. the amplitude of the carrier frequency. With a decrease in amplitude of
the carrier, the amplitude of the noise envelope decreases proportionally.
In the worst case of noticeability of the interference in the broadcast
transmission interval the suppression of the carrier and, consequently,
suppression of any nonlinear interference reaches the highest value. This ~
conclusion is also applicable to modulation of the carrier by the background
in the transmitters and repeaters, which simplifies the structural solutions
of these devices. In addition, the introduction of the adjustable carrier
increases the efficiency of the powerful repeaters and facilitates the
thermal conditions of their operation, which is especially noticeable for
transistorized systems. '
Methods of Decreasing the Additive Interference
The types of additi.ve interference and the causes of their appearance were
investigated above. The methods of decreasing this interference are
determined by the nature and location of its appearance.
The interference which falls directly in the spectrum of the low-frequency
signal in the connecting feed lines of the programs can be decreased by
insuring sufftciently high crosstalk attenuation between the connecting
lines of all the p rograms. A decrease in the same type of interf erence in
_ the receivers is a~hieved by small coupling between the input of the
receiver and the input of the lo~-frequency repeater of the receiver.
The interference incident in the spectrum of the AM signal in the multi-
~ channel transmission channel can be decreased by reducing the level of
, the harmonics of the powerful station low-frequency amplifiers in the
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frequency band of 70-130 kilohertz and also improving the syQUnetry of the
TPB lines under the effect of wireless interference. Some symmetrizing
of the subscriber transformers is achieved by applying the device in (2.35),
the series LC circuits of which are tuned to the external interference
frequency. In order to exclude the transmission of the interference to the
subscriber network over the "two-wire-ground" system, the subscriber
transformer can be used with electrostating shielding between its I and II
windings. These methods permit a reduction in the level of wireless inter-
ference by 10 to 12 decibels. The use of carrier regulation with suppression
of the carrier in practice to zero permits us to obtain suppression of this
- interference in the receiver detector by 15-20 decibels in the useful
signal interval. Obtaining the given ir.terference level between the adjacent
high-frequency channels is possible by using the corresponding selectors
in the receiv~rs.
~ (1) P~Au~wr
_ c C
_ L
_ qT ~2~
~ Figure 2.35. Circuit diagram for suppression of interference _
from a radio station ~
- Key:
1. distributing feeder line
2, subscriber transformer
2.12. AM Signal with Regulatable Carrier and Its Application
The application of the AM signal with regulatable carrier permits us to
reduce the crosstalk interference for all levels of the broadcast signal
; less than rated and especially significant in the most critical case, in
- the broadcast transmission interval. Let us now consider the AM signal
- with regulatable carrier, its characteristics, the relation of these
- characteristics to the quality indexes of the high-frequency channel and
_ the operating peculiarities of some of the devices for the given AM signal.
The usual AM signal can be represented by the expression
~
~L a Up ~ 1-{- U~ CC5 ~ t~ C~3 (~,~p ( 2. 39 )
where Up is the carrier amplitude; c is the proportionality factor betw2en
the amplitiide of the modulating voltage U~ and amplitude of the envelope.
88
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Correspondingly, the AM signal with slowly varying carrier amplitudes Up(t)
and modulat~ng signal U~(t) can be expressed as
(1 UO (l) 1-{- (t~ COS Sa t COS t. ( 2. 40)
L Vo J
For simplification let us assume that the amplitude of the modulating
signal varies according to a harmonic law with angular frequency S~A from
US2 min tO U~ (Fig 2.36). Then the variable amplitude
Ua = UQ uQ~~ ~ v~ ~~1-~- cos S~A t~. (2 . 4~.)
. �
Key: 1. max; 2. min
~
~ ` .
. ~2~ ` ~ � ~
. ~ ~
, ~
- . ~irnN ~ ~ + ,,~Si� .
f ~ t
. ~3~ . -
. ~ .
, , . ~ . ~1)
. ~ T Z~ ~r~
~nuQ
~
~~r
' As ~ C![E~Q/!a~ ~
Figure 2.36. Variation of the amplitude of the modulating
signal with respect to harmonic law
Key:
1. Envelope of the modulating signal
2. USZ max
3. U~ min ~
For U~ miri 0 expression (2.41) is simplified:
U ~l~
~Q = Q~
se r 1-}- COS SZ~ t~. ( 2. 42 )
l
Key: 1, max
The given expression is the envelope of the modulating signal.
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For the AM signal with CMC the amplitude o� the carrier must vary also bj?
law (2.42), and the expression (2.40) acquires the following form:
- - u (1) ? . _
, c
a= k= ~1 -f-.c~s~A t~ ~lj-f-'~-k cos 52t~~~at,- (2.43)
Key: 1. max
where k is the proportionality factor between Up and U~.
~ Comparing expression (2.43) with the expression for the ordinary AM signal
(2.39), it is easy to see that the signal obtair.ed is an AM signal with
variable carrier amplitude (kU~ ~X/2)(1+cosStAt) and constant modulation
coefficient m=c/k. The product (kU~ ~x/2)(1+cosS~At)coswpt of the expression
(2.43) gives two components on conversion of the term (kU~ ~X/2)cosSZAtcoswpt;
U ~1,~ u ~1~
k s 4 c~~~o +~A) t: k Q,~~ cos (~o - S~~) t~
Key: 1, max
analogous to the side frequencies of thc~ ordinary AM signal. Inasmuch as in
the ordinary broadcast signal the frequency S2A G ~
~ ~n a,~ v,~ o w oo cv ~ i~+ a~ oo ~
, ~i?�~v~iafl// ' ~ . ~ . . N t~ 3 s~ o ~ ~ ~ i b ~ ~ u~i ~ ~ ~ ~ a
~ ^ _ ' a~ t i cu a~ ~ a~ a? o~+ v~ ~ u~
, ~ _ . , . ' . a~ i i i s~ o ~ ~ i s~ w o
v . � - R!
� , , _ ~ ~ 3 U ' U ~ ~rl N ~ I I f: ~rl ~ ~ j
. . . . oo ~ a~ ~ aG i i cv a ~a a
� � o a~ ~ ~ ~G .n o r.. ~ ~ a~ o a~ ~ ~
F:+ 4~ C+' P0 G~~ �r~ U'r~i .t I~ i.~ q 4a N
106
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, o e~)1 I~ i I~ .
- ~ r i ~ v ~v
~
~ ~ ~ I ~ b ~ . Gl
O;�~tI ~ Q~b ' �G
I~ I~ ~ ~
II ~ . ~ ~w
I ~
~ ~ ~~t o ~ ~
- - - 3 1 A
~ ~ ~ ~ ~ v
~ ~ ~ trf I 0 .
6 ~ ~ ~ ~ `I ifl 4-1
~ ~ t ~ , a ~ ~ � ~ _
~
~ ( a ~ U ~ . ~ ~
E' I . a ~ ~ ( i~
a 0 ~ ~ ~ ~ a~i
~ I ~ ~ y ~
1~ ~ H
� ~ ~ I I ~
, c~ ~ e ' ~ ~ " I w a~+ ld .a
a' o a ' ~ \ I ~ ~ ~ v~i
~ ( ' I -
& ~ I . L__~o~ J ~~o~ �
1 . ~ ~
~ ~ aaa3�~
~ ' ~ ~ ~I~ ~ ~ d o~ ~ ~ ~
11 ~ , ~ I ~ ~ ~ t ~ ~ ~
~ ~ i
~7 ~ . ~l I~~ , ~ o ~ ~ '
` o~ oao
~ 4-t i~ N U
. ' r~s '~+f a ~O a o [a-~ ch
v
_ ~ N ~I - ' p ~~.+OH -
~ ` . v ~ d.C v~l ~ i
~ ~ . ~I N ~ ~ ~ ~ ~
' ~
C b ~ ~g W 'Ud 0~l ~
~ ' Q � tC 'd O
~ V ~ . ~I O~ N f~+ G~l ~.3i
~ a ~ ~ , ~ ~ ~ �n w ~
. ~ I
~ ~ ~ ~M I 00 ~r ~ C~1
~ - r~l r~l 3 ~ ~~-1
~ Q v~ A~ t~1 c0 ~ U
~ ~ C ~ d I N u1
~ CV c~ V N J.~ 1.? .p
_ v ~ ~I ~ ~ tA ~
~ ~ ,`.~~J~ ~ � , ' ~1 O GJ rl U7
~ u ub
4' ~e a ' a~ ~ i i~
~ . ---~,vnWtr~n1L , . ' . ~ ~ ~ �o � ~
, ~
~ . : - \ ; : , , : . . , ~ N
x
107
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The UUP-2 complex makes it possible to control twu re�erence repeater =
- stations or UP, BP in the preyenceli�ier andetransmitters)ntrol objects
in each of them (low-frequenc amp
, The UUP-1 set also controls two rereater stations in the presence of
each of them af no more than three control objects.
The WP-1 and UUP-2 complexes are designed for operation over the connect~zg
lines the telephone pairs. When using the WP-1 the central wire broad-
cast station must be connected to each reference repeater station by tlines. -
connecting lines, and when using the WP-2 equipment, four cor_necting
In order to transmit the control commands, individual strands of the connect-
ing l~nes are used. The programs are set by simultaneous feed to the
80 volt DC pulse (defined polarity) and alternating current line. Noise-
proofness of the system is achieved in this way. The com~nand DC mess~ounds
- fed over the "conductor-ground" network, and AC, over the "two-wire-g
network.
The command message is the switch; on return of the switches to the initial ~
position the voltage of the command message is picked up from the line. The
command output is accompanied by obtaining a verification of execution.
511 connecting line is used only to sheathe the low-frequency programs;
S12 is a reserve line. Over the "strand-ground" S13 line a control command
is transmitted for one low-frequency module; over the circuit made. up of
the other strand to ground", the control circuit for module II is low
frequency. A command is transmitted over the S13 line for modules III and IV
or for control of the transmitters of programs II and III.
The return sound monitoring with respect at the reference repeater station,
of the low frequency repeaters installed
the PP, UP and the telephone service co~nunications are realized over the
S13 and S14 telephone pairs. With respect to individual circuits (f ifth
and sixth) from the APU-3 No 2 and APU-3 No 3(Fi~ 2.50) the transmission
~ of the signals of two additional programs to the transmitters of several
reference repeater stations.
3, The equipment of the UKTP type [transformer substation connection circuit]
for remote monitoring and control of the sound transformer substations and
monitoring of the distributing feeder lines. The equipment is designed
for the control of 6 and 12 transformer substations equipped with SGR
and SGP bays. For this purpose the central wire braadcast station is
connected to each ~rinS~h~eresenceaof~feederWlinesrforfoutdoortsoundephone
exchange li~es, and P
systems (FUZ), three pdirs.
108 '
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4. The reserve pragram sources are special r~ceivers for re~eiving AM and
ultrashort wave broadcast stations, a tape recordar, sound pickup and
microphone.
:he following types of equipment are instal:led at the reference repeater -
stations:
1. Low-frequency amplifier with output power of 5 kilowatts, type TU-5-3,
TU-5-4, UPV-5 or 15 kilowatt type UPV-15. In Moscow and Leningrade more
powerful 3mplifiers are used (by 30 and 60 kilowatts).
At the newly designed reference repeater stations up to four repeate~s of
the TU-5 (OUS1) type are installed; at the ind?vidual existing reference -
repeater stations up to six TU-5 repeaters or two UPV-15 repeaters [OUS4
(Fig 2.50)] are installed. The quality indexes of the repeaters correspond
to the requirements imposed on the first quality class (All-Union State _
Standard 11515-65): rigid output vo?_tage 240 vc~lts; total power intake -
by the repeater from the feed network in the rated output power mode,
UPV-15, 33 kilowatts; UPV-5, 13 kilowatts. In the UPV-15 repeater the
tubes have forced cooling by an exhaust fan. _
2. The servo semimodule is a bay of the :JPI-�2 or UPI-1 type from the set
of remote monitoring`and control equipment of the WP-2 or WP-1 type -
(previously produced by industry) for reception and execution of control
and sending return verf iciations and also for preamplif ication of the pro-
grams :.oming from the ceutral wire broadcast station to the reference
repeater station or the servo semimodule of the TU-TK-TS equipment developed
for the TPB networks. In the UPI there is a device for automatic mutual
redundancy of the TU-5 repeaters.
The input level of preamplification of the UPI is zero (0.775 volts): The
UPI-2 bay is designed to control four controllable ob3ects, azd the UPI-1
bay, three.
3. The SVK-2 type output commutation bays are equipped with voltage
step-up transformers on sonic frequency coming from the output of the low-
frequency amplifier, from 240 ta 480/960 volts and transmission of it to _
the main feeder. In one SVK bay there sre two independent cells, each
of which is designed to connect one main feeder.
Each SVK cell contains a 5 kilowatt feeder transformer; the switching ele-
ment; protection and signalling. _
4. The set of UPV-200 transmitters made up of two program II and III
transmitters.
- For TPB, a device is installed in each SVK cell for connecting the trans-
' mitters of programs II and III (UPP) to the main feeder line. The _
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reference repeater station for insuring unint~rrupted operation requires
special ventilation units and electrical equi~~ment and the laying of power
cablea.
Other types of station sikes are encountered in the cities where the
repeating equipment is installed. These include the sut~station block
Bp and the L'SPV repeater stati~ns. The substation block is a transformer
- substation connected by the main feeder to one reference repeater station
- and equipped with a reserve repeater (instead of a second main feeder).
- A simplified device is required for monitoring and control for it.
In the BP [substation block], as a rule, the TP-STR and STP equi:pment is
installed, and for the TPB, the UPTV-200 transmitter.
The wire broadcast repeater station is designed to feed a two-~:lement or
mixed city network or remote region (Fig 2.52). The USPV is set un by
analogy with the reference repeater station. As the output switching
equipment, the STR bay is installed from the transformer subst~tion complex
with two-element network or the.AVK type bay designed for con~:er.ting 10
distributing feeders and two main feeders. The transformer substation is
� designed to st.ep down the audio frequency voltage and distribute the low-
frequency and high-frequency power of the distributing feeders.
Two bays are installed at each transformer substation: STP-1, STR-3 or
STP-2, STR-4.
In the STP-1 bay there are cells for connecting two main feeders: operating
and reserve. In each cell the 5 kilowatt feeder transformer is instal;led -
which steps down the audio frequency voltage from 480/960 to 120/240 volts.
Each transformer substation can feed up to 12500 subscriber units. Over
the ma.in feeder lines connecting the SVR and the STP equipment, an audio
frequency is transmitted from the reference repea.ter station to the trans-
former substation. The control commands for the system for starting the _
given main feeder line are transmitted over the artif icial circuit of the
"feeder line wire to ground."
The STR-3 or STR-4 bay is designed to connect 10 distributing feeder lines
and two feeder lines for the outdoor sound system. The automation elements
for remote control transformer substation are located in the bay.
The transmission of the signals of the high-frequency channels to the
distributing network takes place through the bypass of the step-down
transformer, for which a transformer substation connection circuit (UPTP)
is installed at the transformer substation, including the following:
_ a) ZFM and ZFR blocking circuits (for the main feeder and distributing -
network respectively) for the high-frequency currents. The coils of the
filters air executed from quite thick wire to insure minimum attenuation ~
of the low-frequency cu~rents going through the coils; -
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b) The by,ass for the OUTP to create a bypass of the high-fraquency
_ transformer f~r the high-frequency cu*rents and matching of the load of
the main feeder (the distributing network) with the wave impedances of
the main feeder. The transformat~on coefficient of th~ standard OUTP is
3.15; it ia assumed here that on~ tnain feeder line feeds 10 distributing ~
f eeder lines.
The high-frequency voltage st the input of the nistributing network (on the _
- STR bay) must be within the limits of 20 to 30 volts.
- As was stated above, the remote monitoring and control of the operation of
the transfor`mer substation, the diatributi-ig feeder and the FUZ are
realized on the UKTP bay of the central wire broadcast station using two
- or three connecting lines.
A structural diagram of the connection of the UKTP-1 bay to three trans-
former substations is gi�~en in Fig 2.53. The Sli connecting line is used
for resnote monitoring and control of the main f eeder. The control, monitor-
ing and signalling of the main fe~der are realized over two artificial
sll channels formed by each wire of this line and the ground. The wires
of this line are used for return sound monitoring from the buses of the
transformer substation and telephone communications TsSPV [central wire
broadcast stationJ with the transformer substation.
_ S12 is used for monitoring and control of the feeders of the outdoor sound
system over the same artificial circuits as in the sll connecting line.
The pair of s12 wires are used for return sound monitoring of the FUZ.
The S13 connecting line is provided for emergency signals (that the fuse~
are burned out at the entrance of each distributing feeder of the STR) and
remote monitoring of the voltage from the ends of each distributing feeder
line.
In the mixed network for areas with small load (2500 to 5000 radio points),
a simplified type transformer substation (UTP) is installed with one-way
feed without remote control and monitoring (see Fig 2.52).
The repeater stations and substations OUS, UP, BP and TP,as a rule, are "
placed in the facilities allocated by the local admissible organizations
- in the residential and public buildings.
In a number of cities, especially newly built ones, the plans call for the
- location of a central wire broadcast station ~ointly with the reference
repeater station [OUS] in the same building with the ATS, MTS. In the
majority of cities the central wire broadcast station is pla~ed in the
same facility with one of the OUS [reference repeater stations]. ~ _
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. . . . rn~ (4) oyc, s~ -
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/
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. ~ I 1
' - . . � . . . ' . � L7i7 ~ ' CB
: . � . , . . : Ill~Aj .
. ~ : GTP .
Figure 2,53. Structural diagram of the connection of the ~
UKTP to the transformer substation
Key: _
1. Central wire broadcast statian 7. Ma.in feeder line
2, UKTpl 8. Reference repeater station
3. S1 1 connecting line 9. SVK -
4. TP1 [transformer substationJ '
5. STP
6. STR
For powerful OUS 30, 60 kilowatts special work areas are built, in
which there is a whole set of stations including power equipment and
ventilation.
Line Structures
The line structures are a responsible part of the WB network. The introduc- -
tion of the TPB system on the existing WB networks imposes additional '
requirements on the lines considering the application of the high-frequency
channels. ~ ~
In large cities the main feeder line is a post and more rarely, pole line.
~ The wires, as a rule, are bimetal, 3, 4 mm in diameter or steel, 4 mm in
112 ~
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~ diameter. The line length is from hundre~s of ineters to 10 kilometers.
The ~�rerage length is 4 km. The inputs to the amplifying and transformer
substations are cable. Along the path of the line, cable inserts are
used which are made up of the MRM type cable and large capacity power cable. -
Tt~e rated low-frequency voltages are 480, 680, 720, or 960 volts; the
transmitted power is up to 5 kilowatts.
The high-frequency voltage is to 120 volts, the transmitted power 25-30 watts.
The voltage attenuation along the low-frequency channel (at a frequency of
- 1000 hertz) is 1-2 decibels. The attenuatio~n of the high-frequency channel
is de}ermined by the expression a~in feeder-aR, and with a matched reg~me
for tne lines without cable inserts it is within the limits of 1 to 10 deci-
bels. In the presence of several cable inserts, depending on the type of
cable used and the accuracy of matching the input impedances, the attenuation
of the section can reach 15 decibels. The input impedance of the main
feeder can diff er from wave (as a result of impossibility of insuring exact
matching) by ~-20%.
The dist.ributing feeder lines can be post, pole and cable. The wire material
is bimetal an~ steel, 3 and 4 mm in diameter and copper, 1.2 mm in diameter.
The attenuation on low-frequency (at a frequency of 1000 hertz) must not
exceed 3 decibels; on high frequency it reaches 10 to 12 decibels.
The distributing f eeders in the cities, as a rule, are lines with uniformly
distributed load. The role of the latter is played by the subscriber
transformer, the input impedance of which on high frequency is from 5 to 20
kilohms, and ~.he transmission coefficient is 0.01 to 0.1 depending on the =
power of the subscrib er transformer .and its load.
The subscriber lines post or pole are made, as a rule, from steel
wires. Their extent is from 100 to 200 to 700-800 meters and more rarely
1 km. The load of the subscriber line is the subscriber inputs ending in
a subscriber 'set. The attenuation of the high frequency voltage of the
long subscriber lines can reach 10 decibels. The layout of a subscriber
line with single program loudspeakers (OI') and three program loudspeakers
i_s presented in Fig 2.22.
The last section of the city WB network, as a rule, is the building networks.
By the building network we mean the network fed from one subscriber trans-
former. The most typical subscriber networl~ for the cities are the intra-
building networks of large apartment builaings. The building network is -
made up of attic and staircase wiring lai3 in the vertical shaft of the
building (sometimes called a"riser") and made as a~�ule of PVZh type
wire with a strand diameter of 1.8-2.5 a.n~ intraapartment wirinb made of
the PTPZh and PTVZh type cables. The Input im~ec?ance of the building net-
work on the low-frequency channel is determined by the number of speakers
connected to the network, and on the high-frequency channels, in addition,
by the parameters (primarily, the capacitance) of the wiring. _
~ 113
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On the carrisr frequencies of the TPB system the building networks acquire
new electrical properties they become electrically long lines, and ir~
a number of cases require matching to avoid th~ wave processes. The
magnitude of the input impedance of the building network on the multiplexing
frequencies fluctuates within the limits of 20-100 ohms (for 5 to I6 story
buildings) and attensation to 6 decibels. As an example, in Fig 2.54 a
circuit diagram is drawn for the length of the building network of a 16-story
building.
~e m ~ ~c ~n ~a r~ ro
~p 3S J1 ' dt �~3 J9 30 30 3~
, ~ y~~,,. ~Lh
~ e,~ '.~c (2)
. rrs~dmc (3)
.1 ~
- 1 i � 0' s Np ~a ~ 5~
Figure 2.54. Schematic of the staircase wiring of a 16-story
residential building
Key:
- l. attic
2. 16th floor _
3. 2d to 15th f loor
4. lst floor
5. NN sections
In the WB networks, single-program speakers of third or second quality class
are used as the subscriber sets. They have input impedance~in the frequency
range from 50 kilohertz to 10 kilohertz correspondingly of 3-12 kilohms
and a phase angle of 30 to 25�. In the high-frequency band these speakers
have an input impedance with respect to modules on the order of 5 to 7 kilohms
and a phase angle of 60 to 70�.
The Avrora and Mayak type three-program speakers that are manufactured have
an input impedance within the range of 2.5 kilohms, and on the high-
- frequency channel the modulus of the input impedance to 4.5 kilohms and
a phase angle of about 40�.
Additional specialized high-frequency devices are used on the TPB networks
to correct the WB lines, a description of which is discussed in detail in
- the following sections.
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Program Sources, Connecting Lines ~or Feeding the Programs, Remote Monitor-
ing and Cont7ol
The basic program source is the radio broadcast equipment(RVA) and in
- individual citief;, the interurban broadcast channels or the eegregated
recciving sl-ations (VPP).
The union central broadcasting progrms obtained over the interurban cable
lines reach the central wire broadcast station most frequently via the
RW, but in individual small cit{es they go directly to the central wire
broadcast station.
The local program sources are professional specialized AM and ultrashort
wave FM receivers of the radio broadcast stations or tape recorder and
sound pickups of the local broadcasts studios. At all of the ref erence
repeater stations, UP receiving programs from the central wire broadcast
station, professional receivers and tape recorders are installed as the
reserve sources. In ~rany cities the central and oblast broadcast programs
of the wire broadcast station a~e received by the professional receivers.
The programs are fed from the RVA to the central wire bro~dcast station in
tandem over special cables with shielded strands or with a connection to
the automatic telephone office distributing frame in a common cable in the
central wire broadcast station to automatic telephone off ice section. The
length of the cable lines in this section is from 0.1 to 3 lan.
A multipair telephone cable, most frequently type T with strands 0.5 mm in
diameter, a capacity of 150, 100, 80, 50 and 30 pairs, tne most different
length from hundreds of ineters to 2 1~, is laid between the central wire
broadcast station and the closest automatic telephone off ice. Between the
automatic telephone office and each object of distribution of the reference
repeater station, BP, UP and TP telephone pairs are used in the cable lines
of the city telephone exchange. In these sections are used with strands
0.5, 0.6, 0.7 and 1.2 mm in diameter. The skeletal diagram of the connect-
ing lines for the decentralized networks in the cities is presented in
Fig 2.55.
For the existing TPB system and standard remote control and m~nitoring equip-
ment, the following number of telephone pairs of the city telephone
exchange are required:
1. Between the central wire broadcast station and the reference repeater
station at 2~ kilowatts, 8 pa~rs, including considering the reserve, 4 pairs
for feeding the programs and 3 tor remote monitoring and control of the
low-frequency amplifiers and the UPTV-200. ~
2. Between the central wire broadcast station and the reference repeater
station at 15 and 30 kilowatts (with two UPV-15), 7 lines; of them, 4 are
for feeding the programs and 3 for resote monitoring and control.
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3. Between the central wire broadcast station and the transformer substation -
three lines in the presence of FUZ and two if they are absent.
4. Between the central wire broadcast station and the substation block,
4 for program f eed and 4 for remote monitoring and control of the substation
block.
At the present time a system and equipment for pregram feed, monitorii~g and
control are being built for the city TPB networks using modern remote control _
methods, in particular, the frequency coding systems insuring high reliabil-
ity and noiseproofness [21].
This equipment has great possibilities for operative remote control, remote
monitoring and obtaining broad information about the condition of the
remotely controlled ob~ects using only one telephone pair in all. The diagram -
of the equipment of the TPB system for the decentralized networks appears
in Fig 2.51.
- For the new remotz monitoring and control equipment (TU, TK) between the
central wire broadcast station and each OUS [reference repeater station],
UP or BP [substation block] 6 telephone pairs are required, of which
considering the reserve, 4 are for the program feed and 2 for TU-TK; there
are 2 pairs between the central wire broadcast station and the transformer
substation. .
The connecting lines in ~he sections from the central wire broadcast station
to the reference repeater station, substation block or UP have a length '
from 2 to 25.3 1~, and in the TsSPV-TP section, from 2 to 26 lan. In the
TsSPV-OUS section 67% of the lines have a length of up to 12 km, and in the
TsSPV-TP section, 78% of the lines. It is necessary to install the inter-
mediate repeaters on the connecting line for the program feed on cable
lines with strands 0.5 mm in diameter, and with a diameter of 0.7 mm, 19 km
long and more.
The existing remote control equipment operates with a loop resistance no more
than 4000 ohms, which corresponds to a cable length of 21 l~ with strands -
0.5 ~ in diameter; with strands 0.6 mm in diameter, 30 km long and 0.7 mm
in diameter, 37 km. The voltage level of the broadcast transmission at a
- frequency of 1000 hertz at any point of the connecting line must not exceed
+17 decibels. The minimum admissible voltage of the sound broadcast trans- _
mission on the load resistance at the end of the line must be no less than
0.775 volts. The crosstalk attenuation between each pair of cables used
for broadcasting and other pairs of the same cable measured on a frequency
of 1000 (800) hertz must be no less than 78 decibels for the two pairs
used, no less than 80 decibels for 6 pairs and no less than 85 decibels for
7 or more pairs. The connecting lines of the program f eed must correspond
to the indexes of one or more quality class with respect to All-Union State
Standard 11515-65. In order to improve the frequency characteristic of the
telephone lines when using them in the sections of the WB channels, correct-
ing c ircuits are used which are installed on the ends of the line.
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117
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CHAPTER 3. INTRODUCTION OF NORMS FOR THE TPB SYSTEM
3.1. General Information
The introduction of norms for the TPB system consists in establishing
- norms for the low-frequency and high-frequency channels and also individual
devices and lines entering into these channels. The introduction of norms
for the high-frequency channel is at the present time complete from the
_ point of view of the presence of materials on standardization and design. -
At the same time the introduction of standards for the high-frequency -
channel and the devices entering into it is in the state of development
and improvement; therefore, primary attention will be given in this chapter
to the problems of introducing norms for the high-frequency channel, its
' devices and Tines. _
3.2. Introduction Qf Norms for the Low-Frequency Channel
- The introduction of norms for the low-frequency WB channel is defined by
the All-Union State S~andard 11515-65 "Radio Broadcast Channels. Classes.
Basic Quality Indexes." In accordance wit~ this standard, the amount
of introduction of norms for the low-frequency channel is determined con-
sisting of the normalized objects (radio relayl channels of different types)
_ and the standardized quality indexes (the reproducible range of frequencies), _
the harmonic coefficient, and so on). The introduction of norms for the
_ low-frequency channels has been carried out in the following form: through,
from the beginning of the WB channel to the end (for example, the input of _
the central wire broadcast station to the subscriber unit), and by parts,
(for example, the central wire broadcast station and the reference repeater
station separately).
Here the standardized through LJ3 channel is electrically perfected, that
is, a channel after which the electrical signal conversi:on~ capable of
1The name "radio relay" is presented in accordance with All-Union State
_ Standard 11515-65.
- 118
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~ rtiu~ln~ u c:liung~ in I.tE; quulity indexes does not take pliice~ und the aound
c~uallty afer tliiH cl~annel ia determined in practice only by the propertiee
oC ll~e rrproclucLng sound Nyelem. Actually, between the end of the normalized
through channel (subscriber roaette) and thp voice coil of the speaker
there are only passive elements the line control and transformer enter-
ing into the subscriber speaker.
The beginning of the nomoalized through WB channels is the first station
object of the WB service: the central wire broadcast station far the
centralized WB network or tt.e WB junction station, for the centralized
network.
The through low-frequency WB channels belong entirely to the WB branch of
the Communications Ministry and from the realizational point of view, the
normalization and responsibility for observation of the quality indexes
~ are concentrated in their hands alone, which facilitates the solution of
the problems of normalization and control. From the technical point of
view the normalization of the through low-frequency channel and parts of it
also present special difficulties, for in the entire ~hannel there is only
one type of signal low frequency and all the channel elements from the -
point of view of normalization belong to two types: the low frequency
repeaters and the transmission lines, which determines the likeness of the
norm~lized characteristics and the measurement techniques. The basic goal
in introducing norms for the low-frequency channel reduces to optimal dis-
- tribution of the normalized quality indexes by parts of the through channel.
In addition to the standard, for tiie l~w-frequency channel there are
standards for the repeaters, transformers and subscriber speakers.
Thus, from the organizational and technical points of view the normalization -
of the initial low-frequency channel presents no special difficulties. In
contrast, to the low-frequency channel, the normalizati.on of the high-frequency
channels~presents great diff iculties: organizational and technical.
3.3. Intro3uction of Norms for the High-Frequency Channels
By ttie high-frequency channel of the TPB system we mean the entire set of
devices and lines designe3 to obtain high-frequency signals, transmit and
receive them. In the most complete form for the thr~e-el2ment WB network
the high-frequency channel is presented in Fig 3.1. For determination of
the volume of the introduction of norms for the liigh-frequency channel it
is necessary to define the normalized ob~ects and the normalized indexes of
these objects.
The normalized objects of the high-frequency channel must be the through
channel and parts of it as is assumed for other sound broadcast ~hannels
- and, in particular, for the low-frequency channel and also individual
devices and lines.
l l.9
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( p t;,dM~~u,r l1Q ~M~i~iuA~ Tli ( P~pUHIIA~ I AOONCI!/lICXGA
~ ~ ~ ~7~ ~ ~9~ ~ ~ , i ceme (11)
nr,~ ~e i ~ i i ; : _
~ ynn ynrn � ~
' ~ ~ ~
~i~~ ~~P.~zo ~ i i ~8~ ' i . i (~o) . i .
i i i i~~ i ,
~ ~ . I ~ ~ I i i AT ~ ~nre � -
' ~1 ~ ' ~i i i . . i i (13) .
~
~
Figure 3.1. High-frequency channel of the TPB system for the three- ~
- element network
Key: .
1. Connecting lines 8. Transformer substation connecting
2. WB station circuit
3. Trans. 78 9. Distributing feeder line
4. Trans. 120 10. Subscriber transformer
5. Transmitter connection circuit ].1. Subscriber network
6. Main feeder line 12, 3-program speaker
7. Transformer substation 13. Group-pr~gram speaker
In accordance with the specif ic nature of the normalized objects, they can
be divided into the following groups:
1) The through channel and parts of it;
2) The transmitters and repeaters;
3) Receivers;
4) High-frequency devices and lines. _
The normalized indexes are of two types:
1) Quality indexes;
2) Electrical characteristics.
The quality indexes pertain to the introduction of norms for the through
channel and parts of it and also the transmitters, repeaters and receivers. '
The electrical characteristics pertain to the introduction of norms for
all the station, line and receiving devices, and they are det~rmined
specif ically for .each type of device.and line.
- 3.4. Determination of the Through Channel
The through channel at the high-frequency channel of the TPB syste~ is
defined beginning with the most complete identity and comparableness of the -
- low-frequency and high-frequency channels among each other with respect to
normalization. Beginning with these arguments, the through channel ends
with the output of the electrical part of the individual receiver or the
1~0
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subscriber rosette in the case of the application of a group receiver.
With this def inition of the end point of the through channel, the complete
~~o:;5tbility oC comparing the low-frequency and high-frequency ciiunnels -
umonb eucli otiier t:~ acl~teved, for in both cases the electric channels ure
~ perfected, and conve,rsion of the electric energy to acoustic energy takes �
- place after them. In addition, the normalization of such a through channel
offers the possibility of defining the norms for the receivers and the
parts of the channel beginning with observation of only the basic norms
for the entire through channel. In this case the guarantee of quality
indexes is also insured with recording on a tape recorder which is done -
from the output of the individual receiver.
_ The input of the transmitter is taken as the beginning of the thro~igh high-
frequency channel, for this device marks the beginning of the high-frequency
channel, and the program feed cl:annel up to this point is normalized with
respect to All-Union State Standard 11515-65. With possible variation of
the structure of the station part of the channel in accordance with the
diagrams investigated in Section 2.7, the beginning of the through channel
naturally is carried over to the input of the first cnnversion unit for
~
converting the low-frequency cha.nnel to a high-frequency channel.
The high-frequency tk~rough channel adopted in this way is the initial ob~ect
of the normalization of the high-frequency channel and can be normalized
considering the quality classes of All-Union State Standard 11515-65.
The through channels for different types of WB networks are illusrrated in
Figures 3.2 and 3.3.
(1) 3rrc~nyama~uoHyuu mpaKm /1D ~
-
. ~ ~ TP.X
- . . _ , _ (7 ) p~a~rervmcxna ' r~er~niu-
~ ~ . pavcmKm ;~d~ru
. _ ~ns~h~to-
~I~O11JM ' OGQu/n6eS
~,~bdyw~~ ynn ~ 6 m.K~~ . .
yc~po~icr~ea ~ (4> . ~o
a . ~8) ~ -
Gmar~qc~,y,~~rA . Ppynno0ot ~ /I6~~~,vmcxuA
vdcme m,~sKmd . nprre.~yge. ~
~3~ . - ~ ' . ~ yc~Bo PaacmKCt , .
� C~eoaXOi~ mpo~m . ~9~ _ .
Figure 3.2. Schematic of the introduction of norms for a wire
broadcast channel with a three-element line section
Key:
- 1. Operating WB channel 6. Suscriber transformer
2. Transmitter 7. Subscriber rosette
3. Station part of the channel 8. Group receiver
4. Transmitter connection circuit 9. Subscriber rosette
5. Through channel 10. Three-program speaker
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3.5. Definition of the Normalized Parts of the Through Channel
The normalized parts of the through channel are defined as follows: -
1) By the limits of operating responsibility of the WB services;
2) By the selection of the channel points for monitoring and operating
measurements; -
3) The necessity for normalizing the individual devices.
The normalization of all parts of the channel is carried out with one
co~non origin the origin of the through channel and different terminal
points.
~l) 9rcnnyumrt4~a~~d~ mpa~rm AB ~ '
" . 7pe,r-
~ . . AL~oNEHmc,ras? ~ , r,;ctGgli-
~ . . ~ L~Nb~L'
po3amKa c .^'//!0-
~ p�'~mre ~9) ~dop:cm t
i~ I._;
c~'c~:
l:s~ ynll y/1Ti1 msxrrr"t 12
~ r:,:.~:;~u,n~~ mp~i+c-
~2) ~3) 4 ~'m
v
fpy,;n~Due
lr~N[;U0.9N?A ~8~ /IpiltdlJ.'OC A6nyeHmcyrwl ~
4acme m,~anma ~5~ . ycmporc- po3emKa
- � cmBo (I1)
y~cm~ mpoxm~ nepcdQ:arqee ycin;,oi~- ' ~
~6~ cmBn-BeixvdTi7 . . (10) . -
C~On3Ha~i m aKm ~
Figure 3.3. Schematic of the normalization of a wire broadcast
channel with a two-element line section
Key:
1. Operating WB channel 8. Subscriber transformer
2. Transmitter 9. Subscriber rosette -
3. Transmitter connection circuit 10. Group receiver
4. Transformer substation 11. Subscriber rosette
_ connecting circuit 12. Three-program speaker
- 5. Station part of the channel
6. Part of channel from the
transmitter to the output
of the transformer substation
7. Through channel
The entire set of high-frequency devices and lines for which the WB
services have responsibility is defined as the operating WB channel
(Figures 3.2 and 3.3). In the case of a group receiver the through and
operating WE channels coincide. The introduction of the concept of the
operating channel completely makes the low-frequency and high-frequency
channels united for the WB services with respect to degree of responsibility
for them, for the channel data end identically with the subscriber
_ rosette. '
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T~~o channel points are normalized inside the operating channel: the
output of the wire broadcast station, that is, the output of the transmitter -
(Figures 3.2 and 3.3) and the output of the transformer substation, that
is, the output of th~ transformer substation connecting circuit (Fig 3.2).
The introduction of the norms for the station part of the channel determines
all the basic initial quality indexes and electrical characteristics of the _
AM signals at the beginning of the high-frequency channel and provides a
basis for standardizing the transmitter and the transmitter connection .
circuit. The monitoring of many of the quality indexes and the electrical
characteristics at the WB station is simultaneously monitoring of these
indexes and characteristics of the entire operating channel, which greatly
simplifies the performance of the entire volume of ineasurements on the
network.
The introduction of norms for the indexes at the output of the transformer
substation ~or the high-frequency channel is carried out in order to main-
tain the quality indexes within the norms which can undergo alterations
- on transmission of the AM signals from the output of the transmitter to the
output of the transformer substation.
All of the above-investigated channels and parts of the channels are
fully or partially standardized in accordance with the adopted list of
quality inde.~ces of All-Union State Standard 11515-65. A number of the
elements of the high-frequency channel are normalized by simpler method:
two or three electrical characteristics (the input impedance, the trans-
mission coeff icient, attenuation). These elements include the lines and
the high-frequency devices of the line part of the channel, the common
purpose of which is passive transmission of the high-frequency signals
without converting the spectrum. The normalization of the lines and the
high-frequency devices with respect to electrical characteristics are
carried out separately. .
3.6. Quality Indexes of the Through Channel and Parts of It _
When developing and introducing the TPB system it was established that the
most realistic for the through high-frequency channel is obtaining a
quality class close to class II of VTU 526-58 [29], beginning with a
number of economic and technical arguments. Her.eafter when introducing
the standard for the broadcast channels All-Union State Standard 11515-65
in place of VTU 526-58, the norms for the quality classes underwent
signif icant alterations; therefor~ the normalization of the through high- _
frequency channel remains in class II of A~1-Union State Standard 11515-65.
The through high-frequency channel is normalized with respect to all the
quality indexes of the All-Union State Standard 11515-65:
The reproducible frequency band; nonuniformity of the frequency character-
istic in the reproducible frequency band; the harmonic coefficient; the
signal/background ratio; the signal/noise ratio; the signal/intelligible
crosstalk ratio.
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The introduction of norms for the indicated quality i~dexes and their
significance for the high-frequency channels have some peculiarities.
Thus, nonuniformity of the fr~quency characteristic ia normalized by the
commonly accepted "normative standard" (Fig 3.4~ only for the through
channels. For the operating channel and the station part, the nonuniform-
ity of the frequency characteristic is determined by other standards,
Figures 3.5 and 3.6. In these standards the distortions of the frequency ,
characteristic are reflected in the region of upper modulating frequencies
introduced into the transmitters. Here it is natural that the tolerance
on the magnitude of the distortions for the operating channel is increased
~ by comparison with the tolerance on the transmitting part of the channel. -
~ ' ~ (2) - ~ ' ~ .
~a~ �
c
,
e
e
~
h
v
0 . y0 D~ 6 Ol?(
' - (1)�
Figure 3.4. Nonuniformity of the frequency characteristic
of the through channel
Key:
1, hertz; 2. 3 decibels
. ~ . _ . � ~2~ ~
� . ~ ~ ~ - ~2
~ ~ ~ .
- ( ~
~
~ - QO 0 60 0/t~~i~ �
Figure 3.5. Nonuniformity of the frequency characteristic
of the station part of the channel
Key:
1. hertz; 2. decibel _
. . _ . ~
. . _ ~2~
~ ~ " ~ . � . ~ ~ ~ ~ t2~
: ' : ~ ~ . q000 . ~ 600011( (1~
Figure 3.6. Nonuniformity of the frequency characteristic
of the.operating channel
Key: 1. hertz; 2. decibels
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The harmonic coefficient is normalized in three frequency bands instead of
two as indicated in All-Union State Standard 11515-65. The normalization
of the harmonic coefficient in the 200-4000 hertz band is broken down into
two bands: above 200 to 2000 hertz and above 2000 to 4000 hertz. The
lntraducCiun uE ~lie la:~t Crequency band ie caused by un increc?se in tl~e
harmonic coeff icient in this frequency band as a result of the presence of
asymmetry of the side frequencies of the AM signal on transmission of it -
over the TPB line channel.
The harmonic coefficient is normalized just as in the All-Union State
Standard 11515-65 ~y two norms: for the rated level and the levels reduced '
with respect to the ratedlevel from 6 to 20 decibels.
The second norm pertains only to the channels with devices having two-
cycle low-frequency stages.
The signal/noise background, signal/noise, signal/intelligible crosstalk
indexes are normalized in the interval and in the All-Union State Standard
11515-65. However, when suppressing the carrier in the interval not only
does a change in the signal/intelligible crosstalk ratio take place, but
also two others. Therefore, for proper coordination of the norms with
respect to these indexes, all the channels and devices of the high-frequency
channel must be norma~ized and measured for the suppressed carrier. Consisler-
ing the different nature of the origin o~ the crosstalk interference from
low frequency and high frequency signals and the different magnitudes of
these interferences in the intermediate points of the channel, the signal/ -
intelligible crosstalk ratio is noimalized separately for interference from
low frequency and adjacent high-frequency ~hannels.
In spite of the orientation toward quality class II, some of the indexes
- of the through ehannel are lower. The basic deviation from the norms in
class II represents the signal/intelligible crosstalk ratio (50 instead of
70 decibels) defined by the effect of the nonlinear crosstalk from the
~ low-frequency channel on the high-frequency channels. However, if we
compare even the value of 50 decibels with the admissible interference of
the radi~ receivers and the long wave and medium wave bands (not talking .
about the short wave band), it is obvious that this standard significantly
exceeds the standards for the radio receiver interference. Thus, �or the -
WB radio receivers according to ~411-Union State Standard 5651-64,
selectivity with respect to the adjacent radio +10 kilohertz wide with
respect to frequency, 34 decibels for class II and 46 decibels for class I
is admissible; the admissible attenuation of the sigaial from the mirror
channel is 40 decibels for class II and 46 decibels for class I. Here the -
50 decibel standard is limited for all admissible signal/noise ratios
at the input of the TPB receivers at the same ti~ne as for the radio receivers
the actual magnitude of the interference is determined to a great extent _
by the reception conditions. On introduction of complete separation of
the carrier in the interval, the signal/intelligible crosstalk from the
low-frequency channel ratio can reach 70 decibels or more in the broadcast
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transmission interval. The increase in mutual protection between the
high-frequency channels pertains basically to the receivers and requires
increased selectivity of them.
'i'lu� K1Knii1/ba~~k~;rou~id rutlo 1~ inferlor by 10 decibele Co ttte clays li
norms on the channels only for the three-program speakers. This assumption
was adopted beginning with the low rated sound pressure of these receivers
and the correspondingly lower noticeability of the background when listening.
However, during tape recorder recording of the programs of the high-frequency
channels and reproduction of them by the devices with high sound pressure
the noticeability of the background rises. Later the signal/background
ratio for the channel with the three-program speaker in class Ii will be
increased from 40 to 45 decibels.
Insignificant deviation with respect to the harmonic coefficient from the
norms in class II of All-Union State Standard 11515-65 (5% instead of 4%)
is permissible in the frequency range of 2000-4000 hertz as a result of
specific distortions of the envelope of the AM signal occurring in the
WB lines as a result of asymmetry of the extreme side frequencies of the
AM signal.
When introducing the norms for the operating channel and parts of it, the
uormalized quality indexes for each point of the channel are defined
beginning with efficiency of the measurement of certain quality indexes
at the given point of the channel. It is known that the labor consumption
of performing the measurements in the WB channels increases in the direction
from the station to the subscriber point. Therefore, in the intermediate
channel points it is sufficient to li.mit ourselves to the normalization
and measurement of only the indexes which in practice undergo changes on
transmission of the AM signal from the preceding point to the investigated
one. Beginning with these arguments, it is sufficient to normalize the -
operating channel to the subscriber rosette of the three-program speaker
- by the n~nuniformity of the frequency characteristic in the given frequency
band. Here it is sufficient to perform the measurements of this nonuniformity
in the frequency range of 1000 to 6000 hertz and also to normalize the
harmonic coefficient in the frequency band of 2000-4000 hertz and the signal/
intelligible crosstalk from the low-frequency and high-frequency channels
ratio separately.
For the part of the channel ending with the output of the Cransformer sub-
station, the number of normalized quality indexes can be reduced to two: -
the harmonic coeff icient in the frequency band of 2000 to 4000 hertz and
the signal/intelligible crosstalk from the low-frequency ratio. The
WB station is normalized, just as the through channel, with respect to all
the quality indexes. This procedure for normali~ing the quality indexes
- of the through channel and parts of it is regulated by the draft of the
branch standard "High-Frequency Channels of the Three-Program Wire Broad-
casting System. The Basic Parameters," developed by the Scientific
Research Institute of Radio. The norms in the draft of the indicated
standard for the through channel and parts of it are presented in the
appendix. -
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3.7. Introduction of Norms for the Transmitters and Repeaters
The normalized electrical characteristics of the transmitter must reflect
tliree of ita functions: as the tranamitter of an AM aignal, as the device
connected L�o tlie Wli network, and as the tranemitter of tl~e AM signal with
regulatable carrier.
The first fact makes it possible to introduce the norms for the transmitter
with respect to the series of parameters analogously to the broadcast trans-
mitters of the long wave and medium wave bands in accordance with All-Union
State Standard 13924-68 "Transmitters, Radio Broadcast, Station. Basic
Parameters."
Accordingly, the carrier frequencies, the relative dev3ations of the ~arrier
frequencies, the rated modulation coefficient, the relative harmonic levels
of the carrier frequency, the rated powers and voltages of the carrier
frequencies, the rated input level and the input impedance of the low-
- frequency input are sub~ect to normalization.
The connection of the transmitter to the WB network requires consideration
of the actual dispersion of the load resistance with respect to modulus and
phase; therefore, the normalization of the output power must be carried out
not only for. the rated active load as for the radio broadcast transmitters,
but also for a load equal with respect to modulus to ~he rated one, and
with the positive and negative angles.
In order to maintain constancy of the output voltage of the carrier frequency
on variation of the load resistance it is necessary to introduce norms for
the output impedance of each transmitter or increase the voltage when
dropping the load analogously to introduction of norms for the low frequency
repeater.
The presence of a regulatable carrier requir~s introduction of norms for the
limits of automatic gain control of the carrier frequency, the buildup time
and the decay time. _
The standardization of the carrier frequencies for the two high-frequency
channels is necessary, for the TPB system, independently of its territorial
- application in the country, must have the same carrier frequencies; in the
given case these are 78 and 120 kilohertz, wherein lies its significant
diff erence f.rom the introduction of radio broadcast norms in which the -
frequency band is given and the carrier frequencies of the radio broadcast
stations are distributed by the territorial principle.
The standard~.zation of the relative deviation of the carrier frequencies
pursues two goals: exclusion of the noticeable draft of the carrier fre-
quencies in the presence of f ixed tuning of the receivers and the appearanc.e ~
of noticeable beats of the carrier frequencies from the two like trans-
- mitters wi.th significant parallel run of the feeder lines from~ the trans-
mitters.
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The relative deviation of the carrier frequency
~ ef _ li--fol ~ :
: . . 10 : ~o . _ (3.1)
where f0 is the standard carrier frequency, kilohertz; f is the actual
carrier frequency, kilohertz.
The relative levels of the carrier frequency harmonics basically falling
in the long wave radio broadcast band are normalized to exclude the inter- _
ference of the radio receivers .tn this band from the TPB system. -
The harmonics of the carrier frequency are normalized with respect to each
harmonic individually and this pertains only to the most noticeable
harmonics the second and third for each carrier (156, 234, 240, 360
kilohertz). The relative level of the carrier frequency harmonic is
. A~.= 201g ~Ut'~ ~ As,(.?) ~ (3. 2)
Key: 1. rated; 2. decibels
where UO rated is the rared voltage of the carrier frequency; Ufn is the
voltated of the n-harmonic of the carrier frequency.
, The rated power with respect to the carrier frequency for each transmitter
is deterneined in the active rated load resistance for the AM signal with
rated depth and modulation frequency of 1000 hertz.
The criterion for the rated power pickup by the transmitter is satisfaction
of the norm with r~spect to the harmonic coefficient for the indicated
modulation frequency; here the output power is
U~ . �
~ = ~ ~'p o~. BT, ~2) ;3.3)
R�(3) ~1~)
Key; l. rated; 2. watts; 3. load
where Up is the voltage of the carrier frequency, volts; Prated is the
rated output power; Rg is the rated load resistance, ohms.
For transmitters with t=.~o secondary windings of the output transformer the
resistances 2Rg are connected to each winding, and the output power is
defined by the formula (3.3).
However, in contrast to the radio broadcast transmitters, the basic guar-
anteed value for operation of the transmitter in the WB channel is not -
the rated power, but the rated voltage of the carrier ~ust as for the -
station low-frequency repeater it is the output voltage of the low-frequency
signal.
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'Tlie rated voltage of the carrier frequency
~p~= P~~~B. . (3.4)
Key: 1. rated; 2. load
The modulation coefficient m for a regulatable carrier has complex dependence _
on the magnitude of the modulating signal (Fig 2.40), and basically its
maximum value is normalized corresponding to the rated voltage of the
carrier. The maximum modulation coefficient is assumed equal to 0.7
considering the difficulties of detecting the AM signal with variable
carrier.
The limits of automatic control of the carrier in the given dynamic range
of leveis of the modulating signal _
. . . UG HOM~ .
: ~h~,K~ = 20~g~o~ ~ As. El) ~ (3.5)
)
Key: 1. decibels; 2. rated; 3. min; 4. max .
where UO min is the minimum. voltage of the carrier correspondjag to the
minimum given level of the modulating signal.
The voltage buildup time of the carrier frequency is defined by the time
during which the ratio of the carrier frequency reaches a value of 0.9
UO rated for feed of a voice signal to the receiver input with a frequency
of 1000 hertz and rated input level (Fig 3.7).
The time for the voltage drop of the carrier frequency is defined by the _
time during which the voltage of the carrier frequency at the output of -
the transmitter decreases from rated to 0.2 UO rated after picking up Ehe
- modulati.ng signal from the transmitter input under the conditions that
~ the limits of regulation of the carrier are 20 decibels (Fig 3.7).
4 - . ' -
~I!~ ~ ~
~7NAM
~1 ~ . :
Q?Do~ar
M~N ~ ~ _ ~ ~ ^
'S'
. tN , ~ Y~~ ~ �
Figure 3.7. Determination of the buildup time and the decay -
time of the carrier frequency voltage Up at the
transmitter output
Key:
1. rated ; 2. outside; 3. connecting line
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.
The high-frequency amplifiers installed in the high-frequency channel at
the present time include the two-channel intermediate repeater (DPU).
With respect to the output part the repeater is analogous to the trans-
mitter; therefore the standardization procedure ar:d the proceciure for
determining the quality indexes basically is the same as for the transmitter.
liowever, there are some peculiarities.
A distingu ishing feature is the normalization of the nonuniformity of the
frequency characteristic and the harmonic coefficient. Inasmuch as in the
repeater of the AM s3gnal there are no causes for variation of the non-
uniformity of the frequency characteristic and the harmonic coefficient
in the range of low modulating frequencies, the nonuniformity of the
frequency characteristic of the repeater is sufficiently normalized and
defined in the frequency spectrum of the AM signal, that is, for the DPU
[two-channel intermediate repeater] in the fp+6 kilohertz band, both for
resonance and band repeaters, and the harmonic coefficient can be
normalized beginning with 1000 hertz and more.
All of the signal/noise type ratios are normalized a~nd defined by the
relatively normalized suppressed carrier.
The norms for the quality indexes for the DPU were obtained beginning with
the actual possibilities of introducing minimum additional distortions
into the through channel. The normalized electrical characteristics of
the DPU are as follows: the rated output power and the output voltage ~f
the carrier; the maximum gain; the gain control limit; the input impedance
in the AM signal band. Inasmuch as the two-channel interme~iate repeater
can be used f or a signif icant interval of input voltage~, it is not the
rated input voltage that is normalized, but the maximum gain and the limits
of the gain control. Under actual operating conditions the output voltage
of each carrier frequency is defined by insuring sufficient voltages of
- the high-frequency signal in the entire segment of the line included
after the repeater (Fig 3.8).
- The specif ic norms for the quality indexes and the electrical characteristics
are presented in the corresponding sections of the description of the
given devices.
3.8. Introduction of Norms for Receivers
The receivers in the TPB system can be divided into two groups: individual
and group. The introduction of norms for each of these devices has its
own specif ic nature.
At the present time basically two types of receivers have become widespread:
the three-program speaker (GT) and the group receiver (GPTV). The
characteristic features of their standardization are investigated below.
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~ ' �l~,~ ~1) . . � � . ' �
= 319 ~ . '
~ . . .
. !p - ~ " .
~ ~rte
3}
~ ~ d -
- ~ � II?ica~~ ~ f~~n?
_ . ~ y~dn
yo~iru
Figure 3.8. Diagram of the carrier frequency voltage on the
distributing feeder line with two-channel
~ intermediate repeater
~ Key:
1. volts; 2. point of installing the two-channel intermediate repeater;
3. UO ad 3 4. JC~X; 5. 1cm
The introduction of norms for the three-program speaker is done in
accordance with All-Union State Standard 18286-72 "Three-Program Speakers.
Tech~ical Specifications." The group receivers are normalized with respect -
_ to technical conditions. Here the three-program speakers are normalized
as electroacaustic devices, and the group receivers, as electrical devices.
The three-program speaker is normalized with respect to acoustic and .
electrical indexes. The introduction norms f4r the low-frequency channel
of the three-program speaker corresponds basically to the All-Union State
- Standard 5961=66 for the single-prAgram subscriber speakers. The norms
- for the acoustic and electrical indexes of the three-program speaker on
reception of high-frequency signals have b~en established with respect to
classes I, II and III.
The acoustic indexes of the three-program speaker are determined by the
sound pressure, and they include the following: the rated frequency band,
nonuniformity of the frequency characteristic in this band; the average
sound pressure and tbe harmonic coefficient. These indexes have the same
def inition as ttie corresponding indexes of the radio receivers and the
subs~riber speakers. Here the normalized nQnuniformity of the frequency
characteristic of the average sound pressure must be satisf ied considering
distortions in the upper frequency range of modulation (Fig 3.5). The
harmonic coefficient is also normalized and def ined without considering
the distortions.
~
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The normalization of the quality indexes of the electrical channels of the
three-program speaker and the group receiver (GPTV) is carried out
identically except that for the three-program speaker the electrical
channel is normalized on the voice coil of the given speaker, and for the
group receiver, at its output for any real load. For the three-program
speaker of classes I and II, these quality indexes must satisfy the require-
ments of obtaining the corresponding quality classes for the through _
WB channel. For the three-program speaker of class II, the satisfaction -
of this condition is not mandatory. The nonuniformity of the frequency
characteristic with respect to the electric voltage in the rated frequency
band is also defined considering the distortions of modulating frequencies
- in the subscriber rosette of the three-program speaker or at the input of
the group receiver. Simultaneous satisfaction of the requirements of non-
uniformity of the frequency characteristic with respect to sound pressure
and electric voltage for the three-program speaker does not cause any
mutual difficulties and, moreover, the observation of the nonuniformity ~
with respect to the electric channel promotes obtaining of the given non~
uniformity with respect to the acoustic channel. Inasmuch as the normative
"standard" for nonuniformity of the frequency characteristic of the through
channel with respect to All-Union State Standard 11515-65 can have any
form within the limits of the given nonuniformiCi~s F1 and F2, it appears
possible to correct the frequency characteristic for the electric channel
correspondingly for satisfaction of its nonuniformity with respect to the
acoustic channel, which has significance for the edge, especi.ally the low
frequencies of the standardized range.
The standardization of the harmonic coeff icient of the electrical channel `
of the TPB receivers has several peculiarities by comparison with the
normalization of the radio broadcast receivers.
The harmonic coefficient of the radio broadcast receivers is normalized -
with respect to the sound pressure for a rated modulation coefficient and
- average sound pressure. In the presence of the regulatable carrier the
- normalized basic harmonic coefficient of the electric channel of the TPB
- receivers must be observed in the entire range of carrier regulation for
the corresponding modulation coefficients. This requirement pertains to
- the AM signal detector creating nonlinear distortions of the envelope for
small carrier voltages at its input. In the p.~esence of the low-frequency
- channels of the receivers of the two-cycle repeaters the harmonic
coefficient for output voltages equal to 0.1-0.5 of the rated must not _
exceed 0.5 af the basic one. The latter cond ition pertains to the GPTV -
[group receiver] and the GT [three-program speaker], classes I and II,
entering into the through channel. For the three-program speaker having
a high-frequency amplif ier, the standard with respect to Kr must be
observed for the given increa.se in the input signal.
Out of all of the types of interference the greatest complexity is off ered
by the normalization of the signal/intelligible crosstalk ratio. This f
ratio must be def ined for all types of interf erence when receiving AM ~
signals.
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The interfexence from the low-frequency signals of program I, the high-
frequc~ncy signals of the ad~acent high-frequency channel, and the aignals
I: ruin ll~~ rudio brouJca~~ yLaLlons are oI tl~ia type.
All of this interference in the TPB receivers is determined by the
characteristics of the input frequency selectors, thcir structural execution
and the presence of communications between the low-frequency amplif ier of
~ the receiver and the low-frequency program channel.
i
When normal~zing the existing TPB receivers with respect to the indicated
interference ther.e is no united terminology. The terms "mutual protection,"
"interferen�e protection" for the three-program speaker, and "crosstalk
interference" for the GPTV group receiver nre encountered. Therefore,
hereafter we shall use the term adopted in All-Union State Standard 11515-65:
signal/intelligible crosstalk ratio or, for short, the signal/noise ratio
with indication of the type of noise.
The signal/noise from the low-frequency channel ratio is normalized with
respect to the maximum voltage of the low-frequency jigna.l at the inpnt
of the receivers equal to 30 volts. For interference with the low-frequency
and high-frequency channels the signal/noise ratio is normalized on the
average interference frequency of 1000 hertz and upper interference fre-
quencies of 6000 hertz for the three-program speaker and 10000 hertz for
the group receiver with constant value of the input in~erference signal.
The adopted signal/intelligible crosstalk from the ad~acent high-frequency
signal ratio must be insured for the worst conditions of nuise protection
of the receivers, that is, for maximum voltage of the carrier of the
adjacent high-frequency channel of 3~volts and for a ratio of the voltages -
of the carriers of the adjacent and recPived high-frequency signals of
30:1 cor;.esponding to suppression of the useful signal carrier by 10 ti~es.
When defining the signal/noise ratio for the given type of interference
it is necessary to use joint inclusion of the signa.l and interference
- sources at the input of the receiver. -
The no�rmalizati~n of the signal/noise rati.o from the radio broadca.st
stations pursues th~ goal of insuring noiseproofness of the TPB receivers ~
with respect to this type of interference. In this case it is necessary
to consider the diff erent effect of it on the circuitry of the TPB
receivers. In order to determine the gi~�en intprference it is sufficient
to limit ourselves to the long wave radio broadcas~ range.
_ The volume of tY~e signal/intelligible crosstzlk ratio for all of the
indicated types of interf erence in the receiver is taken from a comparison
with the magnitud~ of the nonlinear crosstalk occurring in the line and
it is equal to 53 decibels at a frequency of 1000 hertz. ~
The introduction of norms for tha signal/background and signal/noise ratios
does not have signif icant peculiarities and is carried uut for the
- suppressed carrier or in practice in the absence of it. Actually, ~
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_ considering L-he noticeable excess of the background level of the noise level,
it is possible to limit ourselves to the normalization oC the signal/ _
(backgroun.d+noi3e) ratio or the signal/background ratio. Here, by the
- background voltage U~ we mean the value of ,
U~ ~Ubo U
oa + Uibo~ ( 3. 6)
where U50~ U100~ U150 are the harmonic voltages of the background with
frequencies of 50, 100 and 150 hertz respectively.
All of the above-presented signal/noise ratios are defined by the formula
- U~
~ , A~=201g , As,(2> (s.~)
. U,~,x ~3~
Key: 1. rated; 2. decibels; 3. interference '
where Urated is the rated output voltage of the electric channel; Uinterference
is the voltage of the corresponding interference.
The rated output power Prated is normalized for the rated load resistance
and the modulation frequency of 1000 hertz; the criterion for picking up
- the rated power is the satisfaction of the given harmonic coefficient.
The rated output voltage used when determining the signal/noise ratio is
as follows:
'L~~ox ~i~
(1) . (3. 8) -
O
Key: 1. rated
where Rrated is the rated load resistance. For the three-program speaker `
this resistance is equal ~o the resistance of the voice coil of the
speaker.
The sensitivity of the three-program speaker and the group receiver is
normalized for the rated output power and the input AM signal with modula-
tion frequency of 1000 hertz and modulation coefficient of 70%, and it is
determined separately with respect to the high-frequency channels. The -
variation in sensitivity of the three-program speaker is accomplished by
preset regulators. The limits of their control are normalized, beginning
with the possible difference between the maximum and minimum values of
the high-frequency signal voltages obtained on the subscriber rosettes
depending o,i the point of connection to the distributing line.
Inasmuch as the receivers are connected to the TPB distribution network,
_ it is necessary to normalize their input impedances for elimination of ,
their effect on the quality indexes of the channels and the electrical
characteristics of the line part of the TPB systems channel.
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The i~nput resistances are normalized in the band of received signals of the
given high-frequency channel and in the bands of the ad~acent high-frequency
- and low-frequency channels given by the selected quality class of the system.
When using the low-frequency repeater of the three-program speaker for
receiving low-frequency signals ("active version" of low-frequency
reception), the parameters of the channel are also normalized. The
normalization of the quality indexes is carried out with respect to the sound
pressure and with respect to the electric vo~.tage analogously to the investi-
gated method of norr~,zalizing the high-frequency channels. The norms of the
quality indexes of the active low-frequency channel can be established just
as for the high-frequency channel or higher, taking into account the higher
quality indexes of the low-frequency channel on the subscriber rosette.
In order to avoid the appearance of interference from the detection of
AM signal in thP amplifying channel, the signal/noise ratio from the high-
frequency channels is nortnalized for maximum input voltages of the high-
frequency signals. Among the electrical characteristics for the "active
version" of reception of the low-frequency signals, the sensitivity and
the input impedances are normalized for all signals. The sensitivity is
normalized with respect to the united rated output power of the electric
channel, and i.t is taken equal to the minimum admissible voltage of the
low-frequency signal at the subscribEr point, which permits compensation
and the attenuation of the low-frequency channel. Theinput impedance in
the frequency band of the low-frequency channel is normalized several
times (4 to 8 times) higher than the corresponding input impedance of the
_ signal-program speakers and the passive low-frequency channels of the
three-program speakers which permits the load of the low-frequency TPB
channel to be decreases. On the whole the normalization of the three-
program speaker with respect to the active low-frequency channel corresponds
to obtaining greater output power with lower input voltage and greater input _
' voltage with respect to the preserved passive channel.
The presence of the active low-frequency channel of the three-program
speaker makes it possible to reduce the norms that are difficult to satisfy
with respect to the passive channel, for example, with respect to the
average sound pressure.
The group receivers are normalized with respect to static and time operating
parameters of the automatic gain control. The static characteristics of
the automatic gain control are the control range with respectto input
and the limits of variation of the output voltage. The normalization of
- these characteristics is carried out jointly in the form of determination �
of the minimum range of variation of the output level for the given lim~its
of variation of the input level (Fig 3.9). The norm for the limits of
variation of the output level of the group receiver of 3 decibels is
_ taken from comparison with the admissible variations in level wfth respect _
to the low-frequency channel equal to 4 decibels. The norm for the
ragulation band with respect toinput is determined from calculating the
maximum fluctuations of the input level as a function of the weather con-
ditions. The range nf control with respect to the input Dinp and the
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limits of variation of the output level Dout are defined by the existing
formulas:
w us~t ~xe ~ A~~ ~ ( 3. 9)
D = 201g 1 ,
~:~ea(2)
' D - ZOI VeaxYaKC(3) B(7) (3.10)
~ ~`~6~ g u,~:
Key: 1. inp znax; 2. inp min; 3. out max; 4. out min; 5. DinP; 6. Dout'
7. decibels
Here the rated voltage is taken as�.the maximum output voltage. _
When putting the group receiver into operation it is necessary to establish
some mean initial output voltage Uout mean by the regulator in order to
insure the possibility of operation of the automatic gain control in
the direction of increasing and decreasing the input voltage. In practice -
Uout mean 26-27 volts is no less than the voltage at the subscriber point
with respect to the low-frequency channel, and the equality of the volume
of a11 three programs is not disturbed.
. - . .
U,~,~ 3Z------- ~ ~
t~ ~4 ~ - . I .
~ . �
~
1 ~ " i �
' -~-�,m� (5) ~.6)~v,rm~c~mr~7) -
Figure 3.9. Determina.tion of the control range of the automatic
gain control with respect to input
' Key:
1. Uout 4� Uout min
2� Uout max 5� Uinp min
3. Uout mean 6� Uinp max
7. UinP
The time characteristics of the automatic gain control are the response
time of the automatic gain control and the time of increasing the gain
of the receiver by a given amount. The response time of the automatic
gain control is determined by the time during which the output signal is -
distort~.~ (limited) on heating the AM signal to the receiver input with
. maximum input voltage and rated depth of modulation with the initial dis-
charged capacitor of the detector of the automatic gain control. The
time for increasing, the gain is determined by the time during which the
135 -
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output level af the signal increases by a given amount af ter the decrease
in input maximum voltage by several times.
As is assumed for the repeaters operating on a variable load, for the
grnup receiver, the increase in output voltage on dropping the load ie
normalized.
3.9. Introduction of Norms for High-Frequency Devices and Lines
The introduction of norms for t?igh-frequency devices and lines is done to
- provide for t~ansmission o~ high-frequency signal power with least losses
and observation of the quality indexes of the envelope of the AM signal
within the limits of the admissible values.
The transmission of the high-frequency signal power i$ determined by the
normalization of ~he transmission coeff icients of the high-frequency devices,
the attenuations of the lines and moduli of the input impedances of the
high-frequency devices and the lines on the carrier frequency.
. The reduction of the additional distortions of the quality :Lndexes to a
minimum is provided for by normalization of the transmissioa coefficients,
the attenuat3,on, the modulie of the input impedances and the phase angles
of the frequency bands of the AM signals.
The transmission coefficient of the high-frequency devices .is a value
~R = . ~ ~3. ii>
- ul
where U1, UZ are the~.input and output voltages of the given frequency
respectively.
For converiieace of the overall calculation of the line attenuation and the
attenuation of the high-frequency devices,~the attenuation of the high-
frequency devices is used ~
a= 201g 1 a A~� ~1~ ~ ~3.12~
K~
Key: 1. decibels
The transmission coefficient is normalized for equivalent load resistance. _
The modulus of the total input impedance Zinp and the hase angle ~ are
components of the complex input impedances zinP
Z~ e~~. For the high-
frequency devices Zinp and ~ are normalized for equ~iva.lent load resistances,
and for the line they are normalized for a real load.
The devices of the low-frequency channel used to transmit high-frequency
- signals, just as the subscriber transformer, or included parallel to the
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high-frequency channel through the blocking f ilters (ZF) , as the f eeder
transformer of the transformer substat~on and the KRF box and also the
~ single-program speakers, are not normalized with respect to the high-
frequency signal~. The average characteriatics of the subscriber transformers
~ ZT and aT and the single-program speakers are determined by measurements,
and they are used when calculating the attenuation of the distributing -
feeder lines and the subscriber network.
The necessity for normalizing the high-frequency devices and lines in the
frequency band of the AM signal is determined by the fact that with an
inc.rease in the modulating frequency the frequency band of the AM signal
expands, and the asymmetry of transmission of the lower f~-F and upper fp+F
transmission of the side frequencies of the AM signal appears. This
asymmetry is expressed in inequality of the transmission coefficients
and their phase angles for the frequencies f~-F and fp+F (Fig 3.10). Here
the value of the resultant vector of the AM signal UP (Fig 3.llb) varies
not according to a sinusoidal law, which leads to the appearance of non-
linear distortions of the envelope of the AM signal (Fig 3.12), and, -
consequently, distortion of the low-frequency signa.l at the output of the
rec~iver detector. Thus, the given nonlinear distortions of the envelope
of the AM signal are caused not by nonlinearity of the transmission -
channel, but its asy~etric frequency and phase characteristics in the
frequency band of the AM signal, which gives rise to the necessity for
r_ormalization of the values of K, a, Z, ~ in the frequency band of the
- AM signal for insuring the given Kr at the input of the receivers. The
practical noticeabili~y of the given nonlinear distortions occurs for the
modulating frequencies above 2000 hertz, which is one of the obstacles for
expanding the reproducible frequency band of the high-frequency channels
and improvement of their quality indexes. ~
� ~
, ,ti . .
. ~
, ~
y ~ -
f-f ~ f.~f .f
Figure 3.10, Asymmetric frequency-amplitude and frequency-
phase characteristics ~ _
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. al ' . ~ . - 'bj .
~ . . . -
~ . i . . X~
�'I~
~ ~
b', L~.? . f ~ � /S?tfs?
- ~ . ~Z~ I .t~~
. . : $ : ' . . - ` . ~Lo ~
. _ - _ . . y L+1~~ -
� . , . . ~1� t .
, . - . .
. ' I ' . ~ - :
. . . .
Figure 3.11. Vec~or diagram of the input and output AM signals: -
a) uri'distorted; b) distorted
U ' ~ . .
, .
. ' ~ ~ ~
?
~ ~ S i�~
~ ~
~
~ ~ ~ ~~lt, { ~ ~ ~1.
. ~ f i
, ,j t
.
~ ~ l ' .
~ ~
, . . ~ ~ . ~
, , .
Figure 3.12. One of the types of distortions of the envelope
of the AM signal for asymmetry of the side
- frequencies ~
A characteri~tic feature of the normalizativn of the feeder lines and the
devices with respect to the high-frequency channel is the necessity for
insuring matched operating positions of the feeder lines. The wave
impedance of the distributing feeder line, but not the pure line as in
wire communicattons but the real line loaded on the subscriber transformers,
appears in the role of the initial normalizing parameter. This equivalent
wave impedatrce Z~ve equiv determines the norms for the Zinp of all the
high-frequency devices installed on the distributing feeder lines and also
the total magnitude of the load resistance with respect to the high fre-
quency signals of the transformer substation for the stations with two-
- ele~ment network. The value of ZWave equiv is determined by the type of
wires, the density of the included subscriber transformers per km of
line S and their type.
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As !he performed studies and calculations have demonstrated, insurance
of ~Ite matched orerating conditions of the main and distributing feeder
lines can be connected with normalization of the admissible harmonic
coefficient occurring as a result of asymmetry of the side frequencies.
Thus, it appears possible to ~oin the energy and quality criteria of the
operating lines into one. Moreover, it is possible to estimate these two
indexes by using the total input impedance of the feeder line as the
initial paxameters zi~p=Zin ei~, that is, the parameter fixed at one point,
and not distributed along t~ie line.
In order to estimate the operating conditions of the lines it is possible
to introduce the indexes of the degree of matching with respect to input
impedance for the carriers and side frequencies:
- ~1) -
~oet~. = ss ~ ~ie~~, _ rl ...'r~se~~..~ ~s
.
. _ . . . - ~so ss:t . . . . s'x~ ~4~ .
. . ~ (z). . . : ~ (3). : . . (3.13)
Key: 1. wave; 2. inp 0; 3. inp 19 4. inp 2
where zWave is the total wave impedance of the line equal to zWave equiv~
zinp 0~ zinp 1~ Zinp 2 for the distributing feeder lines as the total input
~mpedances of the line respectively on the ca~rier, lower and upper side
freq~iencies.
In order to estimate the degree of deviation of the modulus and the phase
angle of theinput impedance from symmetric, the asymmetry coeff icients are '
introduced:
. : Q� 1 Zsxo _ Zsxo . Q _ 1 isao . Zezo` - I; -
. ~ _ ( . ~ s - -I- l
~ ~ Z . \Zaxt . Zsxi~ 2 Zesi Zaxs ! . .
- , ^ -+I~ ~ es _ - $o� .~3:1`~) .
. 2 . 2 . .
Beginning with the condition for the through channel Kr~S% on a modulation
- frequency of 4000 hertz, the maximum admissible Kr is defined for the line
part of the channel: .
Kr ~ Y5' - 43 = 3 0/ . - ~ ~ (3.15).
Correspondingl.y, the asymmetric coefficienta of the frequencies of fp�6 kilo-
hertz and the degree of matching with respect to the carrier frequency must
be the following: ,
Q~ < o,15; Qa s o, l~; e~ ~ i o�; e, < io�; 0,7 s n s i,5;
. ~po < l 5�. � . ~ . : ~ (3.16) ~ ;
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The calculation of the damping of the line part of the high frequency
channel is carried out beginning with the condition that the main and the
distributing feeder lines have been processed, and traveling wave conditions
with respect to high frequency signals are insured for them.
The total attenuation of the three-link network channel from the output of ~
the transmitter to the input of the receiver is defined as:
~vs = ~?nn ~ aMm + aovrn ~m � a= ~.a. AS. (3.17)
Key: 1. decibels ~1~
where a?�nn, ~~~tp, Qqy':n+ aP~ , as, aa6 are the attenuation of the trana-
mitter connection ~circuit, the main feeder line, the transformer substation
bypass, the distributing feeder line, the subscriber transformer and the
subscriber network respectively.
For the same two-link network channel the attenuation -
~v~ � avnn apm c~r a�~, A~ ~ ~ ($.1$) -
Key: 1. decibels
The maximum admissible attenuation of the n~twork aad is defined by the
rated output voltage of the transmitter carrier UO trans and the minitaum
admi:ssible voltage UO rec at the input of the three-program speaker:
aA~ = 201g U= = 201g i2o = 53,5 ~i. (3.19)
~1~. UoDp~g~ 0,25 ~4~ .
Key: 1. ad; 2. trans; 3. rec; 4. decibels
For any point of the TPB network the following condition must be satisfied:
a~ ~ aA�,. . ' ~ . . (3.20)
- The components of the total attenuation of the attenuation of the iadividual
devices and lines. The attenuations of the transformer substatian bypass
[OUTP] and Che AT [subscriber transformer] are determined~depending on the
load resistance or the number of subscriber points in accordance with the
graphs in Figures 2.15, 2.17 and 3.13.
The attenuation of the transmitter connection circuit for the three-element
network does not exceed 2 decibels, and for the two-element network, no
more than 10 decibels.
_ The attenuatior. of the main feeder line in general form is
14~
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. '
aM~l~ a d a~ - ~ . ~ (3.21) -
Key: 1. main f eeder; 2. insert
where ak is the attenuation of the overhead part of the lines; aBQB is the
attenuation of the cable insert.
The attenuation of the short cable inserts is not taken into account.
The attenuation of the distributing feeder line in general form
~ . . .
ap = ~ 1 + QB 0 a� o~r,, - (3.2z~
~1) ' . ~ ~a) . � ~r.=I ' ~2) - '
Key: 1. distributing feeder; 2. lead; 3. insert
where tx~ is the attenuation of the overhead section of the line; is
the equivalent attenuation per kilometer; aBl~B is the attenuation introduced
by the long cable inserts; E~an lead is the total attenuation introduced by
the lead; the attenuation introduced by one lead ~an is determined by the
point of connection of the lead (Fig 3.15 and 3.15).
_
4~
Q22 -
a20 -
- a,a . .
als ~ -
o,,y i
rAr�z �
o,iz �
o,~ ~
o,ae 2 ~ .
~e .
a,os
O,dV . ~~8~,~
120r 2
a0z ~
rAr-m3~� '
~ ZD 30 40 50 6C 70 BO N'mp~
Figure 3.13. Transmission coeff icient9 kT of the TAG-10 and
� TAG-25 subscriber transformer as a function of load
Key:
1. TAG-25; 2. kilohertz; 3. TAG-10; 4. NPoint
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_ . _ :'~A~
f (3).
M '
. ~�rZ~
� J .
. . Z~~~
t
~l
. ; . � X.NM
� ! Y J p S ~
f~lZOxlf~ : '
: ( 4~ ~3~ ,
. ' q Z~l. � .
. ( (2 . :
J
~ . t+iarl'll~ , .
~ t .
. ~ ) ~2
~ ~ ~
X~~ �
i Y � ~ 6
Figure 3.14. Attenuation introduced by the lead as a function
of the point of connection of it for a steel 13ne
(x is the distance from the beginning of the line)
Key:
1. lead 4� ~al~d, decibels
~ 2. wave
3. kilohertz
The attenuation of the subscriber networ~: aab is determined separately for
the building ~networks and the subscriber lines. Dependiug on .the number
of floors, the attenuation of the building networks does not exceed the
f ollowing: 2 decibels for 5 to 9 story buildings, 5 decibels for 12 to
19 story buildings.
For the subscriber lines it is recommended that the following damping be
- used� for a length of 0.3 km, aab=3 decibels; for a length of .0.3 to 0.6 km,
aab=5 decibels; for lines of more than 0.6 lan, aab~10 de~ibels. Here, by
the len~th of the subscriber line we ffiean the length of the line from the
subscriber transformer to the most rea~ote point plue .the:length of all the
branches included in the second half of the subscriber line. ~
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_ M t^ia~rp
`
,
. p�
d ~
~ 1 e-2t44
. 8 ~ .
,
, ' ~ 1 t J y .Sr~M~i.
,d~~6 � ~
' f -120~1y ' ~
� ~1~ 6 ~ .
y .
: ~ Zen,s"l~ � .
Z s~Zt~ ,
r d
'
` X,lo'AI
' 1 2 d y S :
Figure 3.15. Attenuation introduced by the.lead as a function
of the point of its inclusion for a bimetal line
Key:
l. ~al~d, decibels
2. kilohertz
3. lead
4. wave
When calculating the attenuations of the high frequency chanr.els it 3s
sufficient to begin with the greatest attenuation of one of the carrier
frequencies of 78 or 120 kilohertz.
The distortion of the attenuation increases on going away from the station
and approaching the subscriber points.
~ The presented radiation pattern of the carrier frequencies for the three- .
element network (Fig 3.16) clearly indicates the increase in the voltage
tolerance of the carrier frequencies on approaching the subscriber point.
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i �
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, : . f:(4) ' . .~6, : ' . $ , ' 9. .
- . . i %l~ IWMaA ~ ~l! ; ~dKM~ i ~7 ~ ~ ~A~fh~~-
~ t ~cr'�~a am~ IGr ' DI~:~�
~ yn ~r }
( , ~ . . i ~ ~1) . i ~ i y ~ .
- . _ � ~.i�
. ~ " t ~ ~
- " ~ 0, (11) . . x '
. ~ , � . ~e i
- � - . . . . . :(11 . " .
' , . . . . . : 16Y . ~ .
. , . � . . , 1
� ~ � . , ( .
_ . - . . : . , . . ~
~ ~ ' . . � ' ~
. ' � ~I ! '
. - .,j/Q
~77C IV.3t
Figure 3.16. Diagram of carrier voltages of high frequency
channels for the three-level systems cot~sidering
decay of high-frequency equipment and lines
Key:
1. UPTV transmitter
2. Transmitter connection circuit
3. Main~ teeder line
4. Transformer substation
5. UTP .
6. Dist~: ibuting f eeder line
7. Subscriber transformer
8. Subscriber network
9. Subscriber rosette
10. UO rated�120 volts
11. volts
~
144
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1
FOR OFFICIAL USE ONLY
CHAPTER 4. TRANSM7.TTERS ANA REPEATERS
4.1. General Information '
~ The transmitter of the TPB system is a set of two transmitters of AM signals
with carrier frequencies of 78 and 120 kilohertz designed to transmit two
broadcast ~:rograms by frequency multiplexing of the WB network. Thus, in
contrast to the radio broadcast transmitters operating on the emitting
antenna, the transmitters of the TPB system are loaded on the WB line, the
emission of which must be reduced to a minimum. The tiransmitters investi- -
gated later are designed for use in the systems for building the station
part of the channel in which the conversion of the low-frequency signal to
the AM signal and obta3;ning the required power of the high-frequency signals
at the input of the TPB network is concentrated at one station site (Fig 2.8,
2.10 and 2.12).
A significant characteristic of the transmitters of the TPB system, in
- contrast ta the radio broadcast transmitters of AM signals is regulation of
the carrier voltage with respect to the corresponding law with variation of
the broadcast signal level. The introduction of the indicated regulation
- leads to variation of the functional diagram of the transmitters. The dis-
tinction of the radio broadcast transmitters of AM signals is the introduction
of the frequency characteristic correction of the modulating frequencies
(raising it in the frequency range of 3000 to 6000 herez).
At the present time the UPTV-60 and UPTV-200 transmitters have been developed.
On the basis of the UPTV-200 transmitter, by increasing the output power of
the terminal stage, a transmitter UPTV-400 has been built. The rated output
powers of each transmitter af these transmitting installations on the carrier
frequency are 60, 200 and 400 watts respe~tively. The quality indexes of the
indicated transmitters are determined from the condition of obtaining quality
indexes of the entire through channel which are close to class II of All-Union
State Standard 11515-65. At the present time the PTPV-400 transmitter for
channels of quality class I with output power of 400 watts and the transmitter `
based on transistors for the rural TPB system with an output power of 40 watts
have been developed. .
145
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The indicated transmitters contain the basic devices for the shaping and
the amplification of the AM signal and also the feed sources, the devices
for monitoring, automation, control and protection.
The structural diagrarns of the UPTV-200 and the UPTV-400 tranemitters are
- identical and they diff er from the diagrams of the UPTV-60 transmitters by
the feed sources, the monitoring, automation and protection devices. The
functional diagrams of the basic channel for shaping and amplifying the AM
signal of all the indicated transmitters are identical; moreov~er, the trans-
mitters of each carri~r fre~uency of one type of transmitter are distinguished
only by the e~.ectrical data of the elements of the resonance circuits in the
high-frequency signal transmission channel.
Let us consider the functional diagram of the channel for shaping and amplify-
" ing the AM signal of the indicated transmitters (Fig 4.1). The system contains _
the amplifica.tion channel for the input low-frequency signal ~low-frequency
repeater), the high-frequency channel made up of the carrier frequency master
oscillator (ZG~, the adjustable carrier frequency repeater, the modulator
(M) and the modulated oscillation repeater (Z3MK) and also the chann,el for
' shaping the control signal (regulating device). Thus, in contrast to Lhe
radio broadcast AM transmitters, the given transmitters do not contain the
' frequency multiplier, powerful modulator for modulation of the output stage;
- the modulatian and regulation of the carrier level are performed in the
_ circuits with low signal levels. `
. ~ -'--(4 Cutnan 6 ~ 10 (11 12 (13)
BXb'D~ ~ic�numtna M ta~"� yM/f Bux~e
y y d! Ner.yr~~r,~.
.I/V tueyQ ~2) � mat, vnr,mumd~ f.na� I7MC~tN?~!
~ (1) 3 ~5) oeiyn
Nyt,uv,.
Pca nu~iy : niu�
Ho~
~ua p~cyyt MYCYtNd4 .
. rocrl~~ (9) , ' . _
~ ~ - . ~
. . . , . , _
� N~movarrt~ ~14) � , , - .
- ~ - numeyua - - . � �
Figure 4.1. Functional diagram of the shaping and amplification of
the AM signal of the TPB transmitters
Key:
1. Low-frequency signal input 8. Signal with regulatable carrier
2. Low-frequency repeater 9. Low-frequency signal
3. ReguYator 10. Modulator
4. ZG master oscillator 11. AM signal
5. Carrier frequency signal 12. Modulated oscillation repeater [UMK]
6. Carrier frequency repeater 13. AM signal output
7. Control signal 14. Power supply
- 146
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~
� FOR OFFICIAL USE ONLY -
The operating principle of the given system consists in the following. The -
carrier frequency obtained in the master oscillator goes to the controlled
high-frequency repeater and the control signal shaped in the regulator and
corresponding envelope of the modulating signal (broadcast signal) go
- together with it to the repeater. Under the effect of the control signal
the gain of the controlled high-frequency repeater changes, which leads to _
the adjustment of the carrier frequency level by the law of the envelope
of the modulating signal, that is, to primary modulation in practice not
noticeable when heard. Then, in the modulator, under the effect of the low-
frequency signal coming from the output of the lo~,rfrequency repeater,
_ secondary, basic amplitude modulation of the carrier takes place, as a result
of which the informatio.n of the broadcast signal is transmitted. The AM
signal shaped in this way is amplif ied by the stages of the modulated oscilla-
tion repeater.
This structure of the functional diagram of the basic channel for which at
the beginning total shaping of the AM signal with adjustable carrier is _
carried out and then amplification of it, is more expedient. The use of
anode modulation in the terminal stage would ~equire the creation of ano~her
powerful controllable rectifier in addition to the powerful 1ow-frequency
amplifier of the modulator, which would cause significant diff iculties. With
relatively low powers of the transmitters (on the order of hundreds of watts)
- the energy advantages of the anode modulation cease to be decisive. In the
i:ransmitters developed at the present time this principle of constructing -
the basic channel is retained. All of the indicated transmitters have quartz
stabilization of the carrier frequency of the master oscillator, which insures
stable reception of the AM signals in the presence of f~xed tuning of the
TPB receivers. With the exception of the diode modulator, all of the elements _
for amplif ication and conversion of the signals are executed from electron
tubes, which imposes additiona.l requirements with reapECt to protection
against high-voltage feed voltages.
In the existing systems for construction of the station part of the high-
frequency channel (Fig 2.12), the output power is determined by the received
maximum voltage of the carrier frequency of 120 volts and the load resistance.
For the ma.jority of cities the number of simultaneously connected main feeder
lines does not exceed 5-6, and the power of 200 watts is suff icient. For
a part of the reference repeater stations of such cities as Moscow and. ~
, Leningrad, with a large number of connected main feeder lines, a power of
200 watts turned out to be insuff icient, which also led to the necessity for
increasing the output power to 400 watts. The most widespread is the
UPTV-200 type transmitter; the UPTV-60 transmitter is in practice not wide-
spread. At the same time, for the TPB systems of many small cities a power
on the order of 40 watts is suff icient. -
_ When calculating the energy indexes of the iJMK in the rated rsgime (the
output power, the dispersion power, the voltage and current amplitude, and
so on), in spite of the regulation of the carrier level, all of the relations
, used for an ordinary AM signal are applicable. For the given maximum nor-
malized modulation coefficient m=0.7, the calculation relations are as follows:
147
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Maximum power. ~
- P~,~~ = P.~~~ m)~ ~ 2,9P.,~ (4.1) .
Key: 1. max; 2. rated
where Pg is the average carrier power in the absence of modulation for the
signal with rate~ carrier voltage;
The average power during the frequency period of the AM signal envelope
Pz = Ps (1 .^.s 1,2~P,. . . . (4.~
2~ . .
The maximum voltage and current amglitudes of the ~1M signal are as follows: -
UIIiKC~ - \i ~ m~ - 1 o7V ~ j ~ . . � . , � � , ~4.a7~
~ I~ (1-}- m) = 1.?Is, : ~ ~ . � ~ (4.4) _
Key : 1. max
where UH and IH are the rated voltage current amp~itudes of the carrier in
the absence of modulation.
For the transmitter with regulatable carrier when suppressing the carrier
voltage in the interval by 10 times the output power in the interval ,
PH min 0.01 PH, which leads to reduction of the dispersion power under
class B conditions.
Thus, the presence of the regulatable carrier significantly reduces the
average real dispersion power of the tubes and transistors when transmitting
- the broadcast signal. The operating conditions for the rated output power
of the carrier in the given case are maximal and correspond. to the maximum
broadcast signal of it. The actual average carrier level is appreciably less ~
than rated foY the broadcast signal. This fact can be especially used to
decrease the dimensions of the thermal leads of the modulated oscillation
repeater transmitters.
At t:~e present time the AM signal repeaters include only 'the two-channel
intermediate repeater (DPU) installed on the distributing feeder lines to
- insure the required high-frequency signal voltage aloag the entire length
of the feeder liae (Fig 3.8). The.DPU [two-channel intermediate repeater]
is made from transistors and is fed from the AC electric network.
4.2. Automatic Gain Control of the Carrier Frequency ~
In essence, with insignif icant variations in all three types of transmitters
the same circuit is used to shape the controlling signal and the controlled
carrier frequency repeater. Let us discuss the circuit for regulating the
148 .
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P'UK Ur~r 1l:lAL U5~ UNLY
carrler :in tl~e UP'rV-200 transmitter (and al;so in the UPTV-400) illustrated
in Fig 4.2. The low-frequency signal volta~e from the output of the
- tc~o-staga low-frequency amplifier goes through the cathode repeater
in the tube L2b, the transformer 111, to the double halfperiod detector
(in the tube 112, double diodes). In the RC-load of the detector (113-114),
the envelope of the modulating signal is isolated. Then the voltage of the
envelope is also filtered by the left diode of the tube 116 and transmitted
to the RC-circuit (115, 117). The DC voltage which is opposite in polarity
to the received erivelope voltage is introduced successively between the
lower point of the circuit and the common point of the entire circuit through
the 120 "carrier suppression" potentiometer. Both voltages are successively
applied to the antidynatron grid of the pentode 50. The variation of the
envelope voltage leads to variation of the bias voltage on the third grid,
which also causes variation of the amplitication coefficient of this pentode.
_ In Fig 4.3 the relation is presented for the relative variation of the carrier
voltage as a function of the bias on the third grid E~g indicating the simple
_ possibility of regulating the carrier by 20 decibels. The initial suppression
of the carrier in the interval is established by the potentiometer 120 and
according to Fig 4.3, consists in feeding the bias voltage on the order of
1.5 volts for suppression by 20 decibels. When feeding the rated input signal
the negative bias is compensated by the positive voltage at the output of the
circuit 115, 117, which leads to restoration of the rated carrier level. The
right diode of tube 116 included in parallel to the third grid of the pentode,
b~ocks it at positive potentials, which permits the formation of the required
dependence of the carrier level on *he modulating signal level, that is, the
extent of the upper section of the regulating curve with constant carrier
voltage (Fig 2.40). The required low-frequency signal voltage a t the input
of the controlling detector for creation of the given regulating curve is
established by the "control signal" potentiometer 30. The buildup time of
the controlling voltage of the RC circuit (115, 117) is basically determined
by the output impedance of the cathode repeater on the L2b tube (34) by the
transformation coefficient of the transformer 111, the internal impedances
of the diodes of the tube 112 and the left diode of the tube 116 and also the
capacitance of the capacitors 114, 115. This time correspondingly determines
the buildup time of the carrier at the output of the tube 50. The steepness
of the buildup of the carrier is determined only by the indicated elements in -
the case where the steepness of the buildup of the modulating signal signifi-
cantly exceeds the steepness of the charge of the capacitance 115. The
decay time of the controlling voltage on the circuit 115, 117 is determined
by the resistances 113, 117 and the capacitances 11G, 117. The decay time
of the controlling voltage determines the decay time of the carrier.
In the UPTV-200 and UPTV- 400 transmitters the buildup time of the carrier
t~ a value of 0.9 U~ rated is on the order of 6 milliseconds, and the decay
time of the carrier to ~7.2 U~ rated is approximately 200 milliseconds.
For further increase in noise suppression in the interval of the modulating
_ signal in 1967 another method of regulating the carrier frequency level was
- pr.oposed in which the existing smooth regulation of the carrier is maintained
within the limits of thP established dynamic range of the broadcast signal
149
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FOR OFFICIAL 17SE ONLY
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. FOR OFFICIAL USE ONLY
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I
FOR OFFICIAL USE ONLY
. ~ ;p~~~ _
~ ~ -18..
ZO
_ JO ,
-+l0 ~
30
F,.B -6 S J ? -1 ~'6~
Figure 4.3. Output level of the carrier frequency as a function
of the bias voltage E~ 3 on the third grid o� the
6Zh2P tube
of 40 decibels, and with the level below this range ~he carrier voltage is
sharply suppressed by another 30-40 decibels, which on the whole makes it
possible to obtain carrier suppression in the interval of 50--60 decibels
(Fig 2.41). The schematic of the device for additional suppression oF the ~
carrier for the UPTV-200 transmitter was developed in 1969. The initial
operating principle of the given device was investigated in Section 2.12 and
illustrated in Fig 2.43. The schematic diagram of the device is illustrated
in Fig 4.4.. The circuit elements which belong to the UPTV-200 transmitter
are denoted anly by the numbers in accordance with Fig 4.2; the circuit
elements of the device are designated in accordance with the type of element.
- The device consists of a two-stage amplif ier-limiter based on the L1 tube
(6N2P), a rectifier with respect to the voltage doubling circuit based on
semiconductor diodes D1 and D2 (D226D), the parametric stabilizer Rg, Eg
(D809), the DC amplifier based on the transistor T1 (MP37F~) and the switching
_ diode D5 (D226D). The device operates as follows. The amplifier-limiter of
the instantaneous values maintains the initial dynamic range of the broad-
cast signal at 40 decibels to several decibels at the input of the rectif ier. �
The parametric stabilizer reduces the limits of variation of the DC voltage
still more, reducing in practice the entire dynamic range of the broadcast
signal to one value of the ~C voltage on the D3 stabilitron. A voltage
determined by the broadcast signal and the DC voltage~.on the resistor R11 are
applied to the base of the transistor T1 in opposite polarity.
In the presence of the broadcast signal, the voltage of inverse golaxity on
the stabilitron D3 exceeds the voltage of direct polarity on the resistor R11
- as a result of which the transistor T1 is closed and the diode D5 does not
shunt the carrier frequency at the input of the pentode 66.
151 .
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152 -
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In the broadcast transmission interval the voltage on the stabilitron D3
decreases sharply, and the transistor opens under the effect of the direct
voltage, which causes transmission of the current through the diode D5 and
ln prrictlce Kliort. citcuiting of thc input of the tube 66 with r~apect to the
carrier frequency.
The device can be placed in the UPTV-200 master oscillator unit, and all of
the feed voltages are taken from its circuitry. The obtained total -
suppression of the carrier in the interval was 65-68 decibels; for the -
switching zone (Fig 2.42) it was 2-3 decibels. The performed operating tesCs
_ of the device in the MGRS [Moscow City Radio Wire Broadcasting Network] over
a period of several months in 1970 demonstrated its reliable operation and
absence of ac'ditional distortions of the AM signals.
4.3. UPTV-200 and UPTV-400 Transmitters
General Information
The UPTv-200 and UPZ~1-400 transmitters have to a great extent similar
structural diagrams and structural executions.
The UPTV-200 transmitter was developed by the Scientific Research Institute
for Radio of the Ministry of Communications in 1962, and at the present time
it is basic [16]. The UPTV-400 transmitter was built at the MGRS in 1963 on
the basis of the UPTV-200 by increasing the output power of the terminal
- stage to 400 watts.
The UPTV-200 and UPTV-400 transmitters have the following ~asic electrical
characteristics:
1. Carrier frequencies of 78 and 120 kilohertz.
2. Amplitude modulation. Rated modulation coefficient of 70�6.
3. Regulation of the carrier level of 20 decibels.
4. Rated carrier voltage of 120 volts.
5. Rated load resistance for the UPTV-200 transmitter of 72 ohms and for the
UPTV- 400 transmitter of 36 ohms.
- 6. Rated frequency band of 50-6000 hertz.
7. Admissible nonuniformity of the frequency characteristic within the
limits of the frequency band to 3 kilohertz is 2 decibels. On a frequency
of 6 kilohertz the increase in the frequency characteristic reaches +4 decibels.
_ 8. The harmonic coefficient with respect to the envelope for the rated
modulation level in the frequency band of 200-4000 hertz is no more than 2.5%,
and i:~ the 100-200 hertz band no more than 4%. ~
153
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9. The eignal/background ratio on frequencies of SO and 100 hertz is no
less than 60 decibele.
10. The rated input signal level for the broadcast transmission is 0 decibels
(0.775 volts).
The functional diagra:n o� the channel for sha.ping aad amplifying the AM signal
is presented in Fig 4.1 and it is investigated in Section 4.1. Let us co~
sider the structural diagram of the transmitters in accordance with their
_ structural execution (Fig 4.5).
. Nr n~N~A~ ~ ~ na~~n K~uH~
Ir~d ,~r ~2~ llMlt3 rn
~4~
. (1~ _ ~
_ r l1QHGl1~~5 /1aKeni~6 /layra(7) .
. . ~ . n~rmoyas a,u?epr,~~r~ a~ryemuyec
~ ?60~SS08 t0 ~roNmpcn
.
.
$ 9 ' . . .
/laxend /Icacn~ 1lq,~lr ~10) . ~ .
cmosunoraa numnyua .
a Nanpastis- a6ooB . � ~ � :
NUA ZZC � .
. ~ . s=~~' ~ ~
. . ~ � . . . ' _
. ti . . , . ~,~06(11) ~ . ' ' _ . : ~ ~ �
Figure 4.5. ~tructural diagram of the UPTV-200 and UPTV-400
transmitters in the panel execution
Key:
- 1. Low-frequency input 7. Acoustic monitoring panel
- 2. Master oscillator panel 8. Voltage stabilizer ~220 volt
3. Modulating oscillation repeater panel
panel 9. 2600 volt feed panel
4. To the TPB lines 10. To the modu~ating oacillation
5. 260/550 volt shade panel repea~er
- 6. Measurement panel 11. ,.220 volts
The atructural diagram of each transmitter consists of seven panels: the
modulating oscillation repeater panel (i,TrIIC); the master oscillator panel
_ (ZG); the measuring panel; the acoustic monitor panel; the 260/550 volt feed ~
pauel; the 2600 volt feed panel; the voltage stabilizer panel.
- The ZG and the iT1~IIZ panels are the channel for shaping and amplifyiag the
AM signal. The remaining panels perform the functions of ineasurement,
monitoring and feed of the basic channel for shaping and amplifying the
AM signal.
154
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' FOR OFFICIAL USE ONLY ,
ZG and UrIIC Panels
The total schematic diagram of the master oscillator and modulated oscillation
repeater panels ~f the UPTV-200 transmitter is presented in Fig 4.2. The -
low-frequency input signal goes through the level control (PY) 4, the
transformer 8, the "demodulation control" 11 to the two-stage low-frequency
amplifier executed from a double triode 15 (6M3P). The left triode of this
tube is included by the circuit with common cathode, and the right triode,
by the cathode repeater circuit. _
The control 4 is used to set the rated (0) low-frequency level in the I wind-
ing of the input transformer 8. The regulator 11 is used to set the rated
depth of modulation. In order to improve the noiseproofness of the AM signals
with respect to the low-frequency signals of program I, an increase in the
frequency characteristic in the u~per moduiating frequency range is formed
in the low-frequency amplifier by introducing frequency-dependent current
feedback realized by a series circuit of elements 18, 23 and 20. The given
circuit has resonance on approximately a frequency of 8 kilohertz. On fre-
quencies about 2 kilohertz the depth of the current feedb~ck decreases, as
a result of which an increase in the upper modulating frequencies is cre~ted.
Remodulatior. does norc occur on the upper frequencies as a result of diminished
level of these frequencies inti~e broadcast signal spectrum. In the receivers
the given 3ncrease is compensated by the corresponding trough. From the
low-frequency amplifier output the total level of the loT,~-frequency signal is
fed to the diode modulator, and Fart of the low-frequency signal from the
"controlling signal" regulator (30) is fed to the cathode repeater based on
the L2 tube (34). The shaping of the control signal by the elements 112-117, _
120 and the gain control of the tu~be 50 are investigated in Section 4.2. The -
generation of the carrier frequency is carried out on the L2 triode of the -
6M3P tube (34). The generatiQn frequency is stabilized by a vacuum quartz
operating by the parallel resonance scheme. -
Part of the carrier voltage is picked up from the anode circuit 33, 38, 40
of the master oscillator and is fed through the capacitor 41 to the first
grid of the pentode 50. For stabilization of the operating conditions of
~ the master oscillator and the contxolled high-frequency amplif ier the feed
voltage of their anode circuits is stabilized by the SG1P stabilitron (37).
From the anode circuit of the pentode 50 the carrier voltage is transformed
by means uf the high-frequency transformer 54 to the diode modulation _
circuit.
Thus, the diode 55 (D2Zh) is iinder the effect of two successfully applied
- carrier voltages and the low-frequency signal, which leads to obtaining the
AM signal in the circuit made up of the inductance 57 and the capacitor 61.
- The modulation is realized by varying the cutoff angle of the carrier
frequency current in the diode circuit. The cutoff angle always remains
normal, as a result of which proportionality is retained between the ampli-
tude of the modulating low-frequency signal and the amplitude of the f irst -
harmonic of the carrier on the circuit 57, 61.
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, This modulator corresponds well to the requirement of independence of the
amplitude of the envelope of the modulated oacillation with respect to the
amplitude of the carr ier required when using the carrier with regulatable
level. In addition, the diode modu:~ation insures very small nonlinear dis-
tortions even with a reduction in ehe carrier level while maintaining th~
deep modulation. In order to suppress the carrier frequency harmonics, the
AM signal is fed from the circuit 57, 61 through the low-frequency filter 63;
62 to the input of the first stage of the modulated oscillation amplif ier
based on the 6P15P tube (66). In order to establish the required output
voltage of the transmitter, the "high-frequency level" regulator is used (64)
at the input of the tube 66. The amplifier based on the 6P15P pentode
operates in the class A regime. Then the AM signal goes through the
sy~etric transformer 74 tuned to the high-frequencies to the preterminal
double-cyc~e stage based on the 6P15P tubes (80, 83) operating as the voltage
amplifier in the class A regimE. The cathode circuits of all the 6P15P tubes
(66, 80, 83) include the resistances 70, 84, 85 for measuring the currents
of these tubes. The diff erential relay 93 is included in the anode circuit
of the preterminal stage.
The preterminal stage is connected to the terminal stage by means of the
_ high-frequency transformer 96, two secondary windings of which form parallel ~
- ` circuits with the capacitors 97, 98. The output stage of the UMIC [modulated
oscillation amplifiexJ located on the UMIC panel is ezecuted in accordance _
with the doub].e-cycle circuit based on the GU-~1 tubes (11, 28, the number ~
- of the circuit elements of the UrIIC panel is separate). The GU-81 tubes
operate in the AB class regime without grid currents. The output transformer
37 is executed from a torus made up of four Alsi~er halfrings type VChK-22
(outside diameter 75 mm). It is necessary to note that the high voltage
transformer executed from the torus of relatively;small diameter requires
careful manufacture from the point of view of the electrotechnical
characteristics of the insulating materials of the inserts and the winding
wires.
The primary winding of the output transformer is tuned to resonance on the
carrier frequency by the capacitors 38 and 43. In order to exclude the
mutual effect of the transmitters on successive inclusion of them, two `
secondary windings of the output transformer are created. The series circuit
(39, 41, 50, 51) tuned to the carrier frequency of the adjacent transmitter
is included in parallel to each winding. This makes it possible in practice -
to exclude the power losses of this transmitter. The terminal and the pre-
terminal stages of the UNIK are encompassed by negative feedback with respect
to voltage with depth on the order of 18 decibels, which insures sufficiently
small output impedance of the transmitter (on the order of 7 ohms) and an
increase in voltage on dropping the load of no more than 1 decibel. The
negative feedback is f ed from the dividers 6, 7 and 31, 32 of the UMK panel
to the first grids of the 6P15P tubes (80, 83) in series through the -
secondary circuits of the transformer 74. The required bias voltage of the
terminal tubes is estatlished by the potentiometer 4 led to the face of the ~
UrIIC panel. In order to decrease the voltage variation of the anode feed -
of +2600 volts, a ballast resistance (45-49) is included in parallel to the
power supply. For monitorin~ the constant components of the anode currents
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of the GU-81 tubes, their cathode�eircuits include milliammeters 16 and 22
and a differential relay 14. In order to monitor the low-frequency and
high-frequency voltages in the master oscillator and modulated oscillation
amplifier panels [ZG and LTrIIC panels] there are control plugs.
In the plugs 6 and 31 of the ZG panel, the low~frequency voltagea are
monitored; in the plug 100 of the same panel, the high-frequency voltage i.s
monitored. In the plug 44 of the iTrIIC panel the output carrier voltage is
monitored.
The filament feed of all tubes of the ZG and U1~IIZ panels is realized from
special filament voltage transformers installed on these panels. The
stabYlized voltage of 220 volts is fed to the filament transformer of the
ZG panel.
The UPTV-400 transmitters are distinguished with respect to the IJNII~ only by
the schematic and structural execution of this panel. The f inal stage of
the UMK is made in accordance with the two-cycle circuit of 4 type GU-81
tubes (two tubes in each arm) operating in the class B regime. The
characteristic feature is the execution of the output high-frequency trans-
former. The transformer is executed from an armored core of eight pairs of
unitized II-type ferrite cores type F-600, which makes it possible to decrease
the transf~rmer dimensions and losses in the core. The variation of the
m~gnetic induction from 450 to 50 gauss causes variation of the resonance
frequency of the output circuit in the primary winding of the transformer
from 120 to 121 kilohertz, which is admissible with low Q-factor of the
circuit (Q=5). The output circuit is tuned by varying the air gap of the
- transformer, to prevent overheating the magnetic induction in its core
must not exceed 450 gauss. The calculated gap is 5 mm.
The output resistance of the transmitter is 4 ohms, and the variation of the
output voltage when dropping the load does not exceed 1.2 decibels.
_ Measuring Panel
The measuring panel is designed ~o measure all of the DC feed voltages, the
currents of the individual tubes of the ZG panel, the AC network voltage
and also for visual monitoring of the AM signal.
For measurements of the voltages and currents, one indicating instrument
is used which measures the current of the 6P15P tube (66) of the ZG panel,
the currents of the 6P15P tubes (80 and 83) of the ZG panel (each tube
- individually and their total current); the voltage of the 220 volt AC network,
the anode voltage of +2600 volts of the UMK panel, the grid voltage of the
tubes of +550 volts of the UMK panel, the bias voltage of the tubes of
-170 volts of the ITMK panel, the bias voltage of -23 volts for suppression
- of the carrier in the ZG panel, and the anode voltage of +260 volts of the
tubes of the ZG panel for various positions of the measurement switch.
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Visual monitoring is realized by the oscillograph using the SL038 tube. .
With a suff icient degree of accuracy for practice with respect to the
tube grid divisions it ia possible to determine the modulation coefficient _
and the dept~ of control of the carrier and also to estimate the maximum
depth of modulation in time of a real transmission. The monitoring AM signal
is fed to the tube from the output of the band filter of the acoustic monitar-
ing panel. The feed of the anode circuits of the tubes in the tube of the
measuring pa}~el is provided from the +550 volt power supply.
Acoustic Monitoring Panel
The acoustic monitoring panel monitors the fitness of the basic channel by
means of the "input-output" comparison circuit, acoustic monitoring, the �
creation of a bias voltage of -170 and -23 volts.
The "input-output" circuit compares the envelopes of the low-frequency
signals at the input and output of the transmitter. For this purpose the
output voltage of the AM signal is detected initially for isolation of the
low-�requency signal, and then the low-frequency signal obtained is detected
for isolation of the envelope of the low-frequency signal. The low-frequency
input signal is deteeted once for isolation of its envelope. The voltages
obtained f or the envelope of the low-frequency signal are f ed to the
individual windings of the polarized relay which responds and attenuates
an emergency signal for the relative variation of input and output levels
of the transmitter of +5 decibels. The polarized relay used with f ixed
extreme positions permits an emergency signal to be obtained even at trans-
mi~sion peak. In order to return the relay armature to the initial position,
a separate.button is used.
For acoustic monitoring, a low-frequency signal is used which is obtained
after detection of the AM signal for the "input-output" circuit. As the
sound reproducing device, the dynamic 1GD-18 speaker i3 used with an intake
power of 250 milliwatts. Its volume control is realized by a step regulator
with constant input impedance. The low-frequency signal obtained after
detection of the AM signal is also used to f eed the re*_urn munitoring to the
TsUS with a voltage of 5.5 volts. This low-frequency signal voltage is
picked up from a separate winding of the transformer.
The bias rectifier with a voltage of -170 volts is made by the bridge system
from the D7Zh type diodes. In order to smooth the pulsations, the LC-filter
is used. Part of the voltage equal to -23 volts stabilized by two reference
diodes of the D811 type is fed to the ZG panel for creation of the initial
bias on the 6Zh2P regulatable pentode and to the "input-output" circuit for
feeding the transistorized repeater. By means of another divider, a voltage
of -48 volts is selected for feeding the emergency bell and two relays in
the 260/550 volt f eed panel.
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260/SSO Volt Feed Panel
The 260/550 volt f eed panel is designed for crea.ting a feed voltage of +260 -
volts of the anode circuits of the ZG panel tubes and a feed voltage of
+550 volts of the second grid of the tubes of the modulated oscillation
repeater panel and also the tubes and the electron-beam tube of the measuring
panel. Two rectif iers with voltages of +260 and +550 volts are placed on the
panel.
_ The f eed rectifier at +260 volts is executed by the grid circuit from D7Zh
type diodes, two diodes in each arm For ~iltration of the pulsations the
LC-f ilter is used. A d ivider is connected to the f ilter output from which a
voltage of +4 volts is picked up for the emergency relay contacts.
The rectifier with a voltage of +550 volts feeds the second grids of the
- GU-81 tubes and the measuring panel tubes. The rectifier circuit is a bridge
circuit made of D7Zh type diodes, three diodes in each arm. The output of the
rectif ier has the LC-f ilter connected to it which is loaded on an additional
ballast resistance of 20 kilohms. A rectifier of +550 volts is f ed from the
ferroresonance stabilizer. The toggle switch for switching on the transmitter
and the switch for the type of control of the transmitter "local-remote," are
taken out to the face of the panel.
- ~600 Volt Feed Panel
The anode feed rectifier of the GU-81 tubes is designed for an intake current
~ of 0.5 amps, and it is made by the bridge circuit from silicon diodes of the
D205 type included in series, 12 each in an arm. The rectifier operates from
the LC-fil~er. In order to improve the stabilization of the rectified voltage,
a ballast resistance located on the modulated oscillation repeater panel
, which consumes a current of 90 milliamps is included in parallel to the load.
A rectifier of +'L600 volts of the UPTV-200 transmitters has significance differ-
ences. It is made Y,y the six-phase Larionov circuit from 54 D205 type silicon
diodes, nine in each arm. In the presenee of a th~ee-phase electric net~rork at
the station the application of this rectifier circuit is the most expedient.
The multiphase rectifier circuit insures low output impedance and the
necessity drops out for a ballast resistance. The execution of the smoothing
filter is simplified, the rectifier efficienc y is incrPases with the same
rectified power. The rectifier is designed for maximum intake current of
1.2 amps, the actual current in the maximum power regime does not exceed
0.6 amps, ~*hich makes it possible to get along without the radiators to the
diodes.
Voltage Stabilizing Panel
In this panel there is a 200-watt ferroresonance stabilizer of the SN-200 ~
type which feeds the +550 volt rectifier and the filament transformer of the
ZG panel.
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Control, Monitoring and Protection
Tlie UPTV-200 and UPTV-400 tranamittera are designed for local and remote
control. ~or remote cantrol, protection and monitoring of the transmitters,
automation elements are introduced into the circuitry of each tranamitter.
- The automation circuitry permits us to switch the transmitters on and off,
receive signa~s about the execution of the com~ands, realize m~~nitoring of
the operation of the transmitter and perform some protective functions. The
control of the set of transmitters can be realized either with the help of
a free panel of the UPI servounit (from the remote control ~~et for the WP-1
or UUP-2 amplifier substations) or direct current over the connecting line
for f eeding t1~e programs over the circuit made up of the "two wires to ground"
using t~e WA-1 panel. The f ilament feed and anode voltages are connected _
to the UMK [modulated oscillation repeater] panel and the measuxing panel
separately in time. On response of the first servorelay the feed voltage
is f ed to the bias rectifier; ~lie anode recrifier of +260 volts, the ferro-
' resonance stabilizer and the win3ing of the delayed relay which with a delay
of 18 seconds feeds a 1ow-frequency voltage from the input of the ZG panel to _
the "input-output" circuit. This delay is suff icient to exclude the false
response of the "input-output" circuit on random inclusion of the transmitter
_ with the previously fed modulating signai. The inclusion of the anode
rectifier of +2600 volts and tiie recti.fier of +550 volts is accomplished
with a delay of 2 seconds; after inclusion of the bias rectifier this delay
is realized by the relays included in the bias rectif ier circuit.
The automation system which realizes the monitoring of the correctness of =
operation of the transmitter includes the "input-output" com~arison circuit
which g~nerates the emergency signal with relative noncorrespondence of the
- input and output levels at +5 decibels. The polarized relay used in the
system receives emergency signals from all of the protective relays, includ- _
ing the differential relays installed in the two-cycle stages of the modulated
oscillation amplifier. In the transmitters there are soun.d and light signals
- abaut emergencies and failures. The sound signals usual~.y bell in case of
- lo~al control for all emergencies recorded by the polarized .alay of the -
acoustic monitoring panel, and the light signal indicates the presence of
feed voltages on the corresponding panels and also burning of the fuses in
the AC feed circuits of the +2600, +550 and +260 volt rectifiers. When -
opening up the rear doors of the transmitter the blocking picks up the high ~
- voltage feed voltages and dischar~es the capacitors of the +2600 valt recti-
f ier.
The connection of the feed voltage of the electric network, the low-frequencq _
_ signal, the remote control and monitori:ng devices and picking up high-frequency
voltages are accomplished by means of the term.inals installed on one plate ~
- of the inputs located below the transmitter, on the rear side.
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4.4. UPTV-60` Transmitter
The UPTV-60 transmitter was developed in 1960, and it is the first type of
tYan smitter used in the adopted TPB system.
The functional diagram of the channel for shaping and amplifying the AM
signal is the same as for the UPTV-200 and UPTV-400 transmitters and it was
investigated in .Section 4.1.
Structurally each transmitter will contain four panels of the modulated
oscillation repeaters, the ZG panel, the anode rectifier panel, the bias
rectifier panel ~..nd the voltage regulator.
- The functional diagram of the master oscillator panel is the sa~e as the
- UPTV-200 transmitter. Moreover, the schematic diagram of this panel differs
insignificantly from the ZG panel in the UPTV-200 transmitter.
In contrast to the UPTV-200 and tYie UPTV-400 transmitters, the output power
of the UPTV-60 transmitter is created by tbur UrIIC, 15 watts each. The output
of each amplif ier is designed for connection of one main feeder line for a
distributing f eeder line when providing a carrier frequency voltage at t:ne
input of the 95-volt line.
_ 'The output carrier voltage is set by the high-frequeney level regulator ~
included at the input of the f irst stage of the modulating oscillatiort
repeater. For monitoring the output voltage of the carrier, an electronic
- display based on the 6Ye5S type tube is used. The dark section of the display
, is closed for values of Uout=90 volts and m=70%.
A toggle switch permitting the feed of ths individual module of the UMK to
be disconnected is led out to the face panel of the UMK panel.
The acoustic monitoring panel contains a dynamic speaker and receiver. ,The
- output transformer of the low-frequency repeater of the receiv.er has a
separate winding for connection to the reverse monitoring line. The input
of the monitoring receiver can be connected to the output of any af the
four UNIK modules with the help of a switch.
'1'he modular construction of the transmitters during operation of each module
on a separate load complicates obtaining the inverse acoustic monitoring in
the case of remote control of the transmitter, for transmission of the ~
instructions to switch the return monitoring line to each module or the four
return monitoring lines is required. In order to overcome thi5 deficiency
it is possible to use addition of the powers of the individual modules on a
common load. Comparatively low carrier frequencies, a conttnon master
oscillator, a wide UNIIC transmission band and short lengths of the mounting
wires create the possibility of strict cophasal addition of the output signal
without power losses. For low resistance of the UMIC outputs, series inclusio:~
of them is possible (Fig 4.6).
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� y,~flf ( ~
~
MK ~
.~2~
yMll
K
~eF~~ (3)
Figure 4. 6. Schematic of the power addition of the tJl~ in the
UPTV-60
_ Key:
1. UNII~ [modulated oscillation repeater]
2. to the load -
3. Master oscillator
With this circuit diagram the unavoidable differences in the output voltages
and the distances do not cause additional power losses. In order to insure
` rated output voltage of 95 volts, a lead from the quarter of the turns of the _
secondary winc~ing is used. Here the output resistance of each UI~IIC module
decreases approximately to 4 ohms. It is possible to connect up to 8 feeder
lines with an output voltage of no less than 75 volts to the common output
of the transmitter with addition of the iTMK powers.
- The el~ctrical characteristics of the UPTV-60 transmitter, with the exception
of the output power, basically are the same as the UPTV-200 transmitter.
4.5. Connection of the Transmitters to the TPB Circuit
General Information
The investigated TPB transmitters are designed for installation of a centralized
network at the stations and alsu at the ref~erence repeater stations (OUS),
the repeater substations (UP) and the substation blocks (BP) for the de-
centralized network. In accordance with this definition, the transmitters
must have the possibility of the connection to the three-elPment, the two-
element and mixed WB circuits. Let us consider the circuitry for connectin~
r,he transmitters to the TPB network.
Connection to the Main Feeder Lines
The connectior~ of the UPTV-200 and the UPTV-400 transmitters ~o the main
fee~ier lines is made through the devices for connecting r_he UPi'-1 trans-
mitters (Fig 4.7) which are symmetric high-frequency transformers with tra~s-
formation coeff icient of n=1:1 and tuned in the primary windirig circuit to
carrier frequencies of 78 and 120 kilohertz. The secondary windings of the
high-frequency transformer of the transmitter connecting circuit are
162
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connected to each other through two series circuits tuned to the carrier
frequencies.
The two secondary windings taken from each output transformer of the two
transmitters and included in series form the ~oint output of the two trans-
mitters to which several main feeder linea are connected through their own
UPP-1 [transmitter connecting circuits). The secondary windings of the two
transmitters are connected to each other in the sequence such that the
currents from the ad~acent transmitter will flow in the secondary windings
- of one output transformer in opposite phase. The total load resistance
connected to the two UPTV-200 outputs must be no less than 72 ohms and no less
than 36 ohms for the UPTV-400. Here it is necessary insofar as possible to
distribute equally the load resistance between the two outputs of the trans-
mitters in order to de~crease the mutual effect of the transmitters.
The UPP-1 are installed in the output commutation phase (SVK) and they are =
- connected between the II winding;of the step-up meter tr~nsformer and the
linear protection elements (fuses and lightning arrestors).
When connecting the transmitters to the main f eeder .lines having cable insert
with the input with a capacity to 5600 picofarads i3entical for frequencies
of 78 and 120 kilohertz it is necessary to decrease the capacitance C3,
achieving tuning of the L1C3 circuit to a frequency of 120 kilohertz consider- _
{.ng the input capacitance of the cable insert. With a capacitance of the
_ cable insert of 5600 picofarads the capacitor C3 is com~letely disconnected.
_ The tuning of the L1C3C6 circuit to a frequency of 78 kilohertz is not r.equired,
for its tut_ing is maintained on connection of the capacitance C6=7500 pico-
farads to the invariant total capacitance of the c.apacitor C3 and the cable
- insert. With different input capacitance of the f eeder line for fr~quencies
of 78 and 120 kilohertz it is necessary to tune separately for each carrier
frequency. Initially, the tuning to a frequency of 120 kilohertz takes
place by variation of the capacitance C3, and then, the tuning to a frequency
of 78 kilohertz, by selection of the capacitance C6.
Connection to the Distributing Feeder Lines
For connection of the transmitters to the distributing feeder lines, two
versions can be used. In the f irst version, the distributing feeder.lines
are conneeted through the common UPP-3 device analogous to the UPP-1 device ,
(Fig 4.7), but having a transformation coefficient of n=3.16:1 and correspond-
ingly altered values of the elements of the secondary circuit L2, L3, L4,.
C1 and C2. The input impedance of all the feeder lines must be no less than
60 ohms (approximately 10 distributing feeder lines) on carrier frequencies
of 78 and 120 kilohertz. The output voltage of the carrier frequencies on
a common bus of the distributing feeder will be on the order of 30-40 volts.
The tuning of the UPP-3 to carrier frequency of 78 und 120 kilohertz will be
carried out analogously to the tuning of the UPP-1. Here the limiting
magnitude of the input capacitance of all the feedex� lines must not exceed
56a0 picofarads.
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. ~OZ~nn-J , ;Tqar~a~ P~ g~ ,
lni~ . (1~ , i T ~ ` ~ , ~(1~)
- - /
T~ . ,rv-t4,' ~ ~ 14 ~'3?c'~ '
I ~ : ' ~ L-' -
. ~ r ~ ~ _
~
� ~5~ - 4 ~ ~ . ~17 �rr-~ ~16)
a,~,,~fi.~ro ~ = ~
ey;~,~-o r~ (
~
j' � Np~ aiw.~zY
~ ' pj~ ~~~1~~
~ 1 ~ � . . I8 - Z~OIiYf f14~
' ( : . . \
~ . ~ ~ ~ , . ~ ~+e~?~~?.r~n~ ~19> . _
~ .
. i� ~ _.�_DA~ 1 ~ , r. . . � � . .
- eHr,~~o . . _(9) ~ ` . - : ' . ~ :
. �e~i'�"ro"t~e ( Z ) ~ . . . . . ~
- Figure 4.1. Connection of the transmitters to the main and the
distributing lines
Key:
1. From the regeater I of the 11. Common bus of the distributing
- low-frequency channel feeder
2. Transformer 12. Operation
3. UPP-1 13. Varistion
4. Main feeder 14. Limiter ~
5. Transmitter for the II program 15. RF-10 distributing feeder
6. autput transformer 16. RF-1 distributing feeder
7. Transmitter of the III program 17. R1~ _
8. I output 18. NRF
9. II output 19. Distributing feeder
10. UPP-3 transmitter connecting bay (STR)
circuit
In the second version in the absence of UPP-3, the connection of the
transmitters to the distributing f eeder lines can be made by using elements
of the structure for connecting the transformer substation (Fig 4.8).
The feeder lines are connected to the transmitter through the bypass (OUTP)
having the same transformation coeff icient as the UPP-3. Between the output
of the low-frequency repeater and the common bus of the distributing feeder,
blocking f ilters are included (ZFR). The compensation for the input
capacitance of the feeder lines is accomplished in this case on inclusion
of a seri~s circuit tuned to a frequency of 100 kilohertz parallel to the
_ output of the low-frequen~y repeater to the terminals 5-6. In order to
_ compensate for the capacitance of the lines it is necessary to decrease the
capacitances in the parallel ZFR circuits, achieving tuning of them to
frequencies of 78 and 120 kilohertz with input~capacitance of the lines.
This tuning is accomplished with respect to the maximum transmission
164
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FOR UFFICIAL USE ONLY
coefficient of the OUTP rahen feeding high-frequency signals to the OUTP
through the series resistance R=600 ohms.
1~ _
. E9) . '
, ~ ~ .t~/~7 ~e mz.a P~ ~
e ~10).
' ' ~~~~taa:;r. ' .
N ~
. . ~ l~
, . (Paf~raz
, . . ~4, - ~:4-:~y,-- 1
~ � mn-~ - - --=.:r
ya~~. 13
. . . ~-r �(14)
~1~ ~~f~Q q , .
~2~ t~r a~'-P i
r � A�~ Pa~amII '
- i j � NP? u.wtFtnGt 1
- ~ , (5) ~ 6 ~a~~rvuma~ 13 .
~ da rctuanQ ~ylp (6) , .
~ . ~u~~~ - ~rJ ~.Mdrvm.tsrsn ~�r~4+u~(L7)) ~
~ - ~ (17) � . ' �
~ 1~..___J . , . : , ~ .
i t . � ' ' , -
_ ( 2 tur.mPV ~ , . , � . . . . : .
l3~ ll~.z'~muc,v~y.
- Figure 4.8. Connection of transmitters to the distributing
feeder lines (Version II)
Key:
1, Transmitter for program II 10. RF-10 distributing feeder
2. Output transformer 11. Operation
3. Transmitter for program III 12. Pieasurement
4. UPP-1 transmitter connection 13. Limiter
circuit 14. RF'-1 distributing feeder
5. To the main or distribu.ting 15. Rlim
- feeders 16. IRF
6. OUTP [Transformer substation 17. Distributing feeder bay
bypass]. (STR)
7. ZFR
8. From the repeater I of the
low-frequency channel
- 9. Common bus of the distributing _
f eeders
Connection of the Transmitters to the Mixed Circuit
The con~ection of the transmitters to the mixed circuit made up of the main
and distributing f eeder lines can be made by the circuits in Fig 4.7 and 4.8.
For e~c~h type of wire network, its own version of connection of the trans-
mitters is used. Here it is necessary that the total load resistance
- reduced to the secondary windings of the output transformers of the trans-
mitters be no le~s ::han the rated and it be distributed uniformly between
two secondary winding;. In the presence of long distributing feeder lines
165
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; . - ~ : . ~ . � 'O
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166
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~
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167
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with atteruation of more than 20 decibels, the UPP-2 can be used with
~r:ti~t~L~~rmuL.[on coc~fflclc:nt n~1.73:1 and ruteJ load resietnnce of 200 ohme.
4.6. Two-Channel Intermediate Repeater (DPU)
The introduction of the TPB on the city networks demonstrated that there
are cases where on satisfaction of the norms for attenuation of the first
(low-frequency) channel, the requirement of insuring minimum admissible
level for the high-frequency programs of channels II and III is not satisfied. ~
,
This occurs on the distributing feeder lines having long leads and cable
inserts, and with long length.s of the basic directio~. In these cases, in
practice it is recommended that a distributing network be constructed, the
load be redistributed.between the distributing feeder lines, the structure
of the line be changed with a decrease in the number of leads, and their
length. .
However, tF:is procedure is not~always expedient because it is connected
with construction operations. The increase in voltage at the input of such '
feeder lines also is inexpedient as a result of the energy expressions which
disturb the effects during emergencies on the lines and overloads with -
respect to the input for the receivers.
A simpler solution can be the application of additional amplif ication of
the high-frequency signals in the channel by installing the repeater and
the distributing line circuit.
For qualitative and quantitative estimation of the set of possible cases,
let us use the previously calculated hypothetical versions of the lines
distinguished by the load density S, the number of leads and the materials
of the lines. The leads more than 300 meters long are taken into account.
The f t Tio ~,s ~da o~~~ '
~sos ~ Rsy~z~ ,7~ .~~r,s... nscs i ~
x~
Q6 , _
t
� � � . � � :
_~'_C+" _ . _ .
Xo ~ : ~ ' ~ . ~
' ~ . ~ . . .
- Cae ~ . ,
intermediate repeater [DPxJ]
175
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lT . . . . ~ . ' ~ ~ -
.f0' ~
ZB
26 ~
~v ~
22
g Cm~~r~/~�~' (2)
f6 ~um+ac Nop
B~
N ~3)
1y ~ra6~np Ka (4) ~
12
~ -
6 ~ .
. ~y B~ - 8~ -
2 .
,1 Z Z,B 3 � ~
Figure 4.12. Vo~coge diagram of the distributing line when
using the DPU
Key: -
1. Uf auxiliary
2. Steel-3; S, tr/km=5
3' ~max norm low--frequency 2� 6 kn'
4. Zinp ab tr-8 kilohms, N=2 couplers/km
4.7. Prospects for Improving Transmitters and Repeaters
- The prospects for ~improving the transmitters and repeaters of the high-
frequency channels of the TPB [triple-program wire broac~cast] system
~ consist in improving the quality and the operating indexes of these devices.
The quality indexes of the transmitters and the repeaters can be improved to
the norms required to insure quality class I of All-Union State Standard
- 11515-65 of the entire through high-frequency channel.
For this purpose gt the present time a transistar-tube transmitter has been
- developed with an output power of 400 watts. In order to decrease the
noticeability of the.nonlinear crosstalk from the low-frequency program in ~
the new transmitters it is proposed that the stati:c and time characteristics
_ of the carrier frequency level control be varied with respect to the existing
- control and that additional suppression oF the carrier frequency in the
_ -broadcast transmission interval be used.
The improvement of the quality and operating indexes of the transmitters and
the repeaters is connected with rebuilding the station part of the high-
frequency channels. When !nstalling the low-power AM signal shapers at the
referer.ce repeat~er stations and the mqdulator oscillation repeaters at the
transformer subetations (Fig 2.13), the problem of complete transistorization
of the given d%vices is solved. Here the reliability of the head unit for _
shaping the AM signal at the reference repeater stations is improved signifi-
cantly (the out~~ut power is decreased frc~. 200 and 4U0 watts to 1-2 watts), ~
~ 176
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the problems of satisfying the safety engineering requirements for the
transmitters remain only for the electrical network voltages, for all of the
anode voltagea of +2600 volts, +550 volts and +260 volts are excluded, and
the f eed voltages do not exceed 70 volts. This improvement of t'~e quality -
and operating indexes pertains to constructing t~he atation part of the channel
with the installation of the transmitters at the central station and the
repeaters of ti~e transformer substations (Fig 2.14).
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CHAPTER 5. RECEIVERS
5.1. General Information
Inasmuch as the transmission of additional programs is realized on high-
frequency and low level, a device must be installed at the end of the line
(at the subscriber) which converts and amplifies the signal. In the triple- -
_ program wire broadcast system two versions of the receivers are used:
individual, three-program loudspeakers (GT), and group, GPTV. In the first
- version the high-frequency signals are fed to the subscriber rosette. In the
second version, over the f eeder line to the group device which realizes
separation, detection and amplification of them; from the output of the GPTV,
the signals of each of the three programs are fed to the subscriber speakers
over indepe~lent pairs with a level of 30 volts. The receivers are the ele-
ment which determines successful introduction of system and must find demand
among the population, that is, they must be cheap, they must have high
reliability and good, varied external appearance. The application of the
transistors insures increased reliability and simplicity of str.uctural design
with low electric power intake.
The technical specifications for the receivers are selected beginning with
the given parameters of the TPB [three-program wire broadcast] system. The
sensitivity of the GT is selected eQual to 250 millivolts. It is obtained
as a result of a compromise between the requirements of maximum simplification
of the GT and also exclusion of the eff ect of induatrial interf erence and
interf erence from radio stations, on the one hand, and an effort to increase
the range of the system and absence of interference with wireless reception,
on the other hand.
An imQortant index of the receivers is the input impedance (Rinp); inasmuch
as thE :;T [tripl~e-program speakers] can be connected to the circuit in large -
numbers, they constitute a signif icant load for the network RT [distribution
points], and therefore their RinP must be high (on the order of se~reral
kilohms). The power on a sound coil of the GT is selected equal to 150 -
^~illiwatts, which coxresponds approximately to the power with respect to the
high-frequency channel.
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The Eirst version of the GPTV-1 group receiver had a sensitivity of
300 millivolts. When putting it into operation at the end of the long
feeder line the sensitivity did not insure stable reception of the high-
frequency programs. Therefore it is necessary to connect the GPTV to the
subscriber transformer through a bypass. In the GPTV-3 the sensitivity is
increased to 100 millivolts. The output power of each high-frequency channel
of the GPTV is selected equal to 25 watts by analogy with the power of the
GT so as to retain the developed configuration of the distribution network.
The excess power obtained as a result of low probability of connection of
all subscribers for one auxiliary program or all speakers at full volume is
useful as the reserve for the case of use of 2 to 3 points operating in the
apartment by the subscribers. The GPTV input is connected in parallel to the
subscriber network, the resistance of which at high frequency can vary from
SO to 200 ohms. In order that this not influence the characteristics of the
GPTV filters and, conseouency, the frequency characteristic, RinP is selected
equal to 400 ohms. The technical specifications of the receivers are presented
in Table 5.1.
As is obvious from Table 5.1, the GPTV type receivers have higher quality
indexes (the problem of maximum reduction of cost was not stated during their
development). The subscriber network of the three-pair wire of the GPTV is
more reliable than the single-pair wire network with high-frequency signals
where poor contacts at the branch points and connections are sources of cross-
talk. The number of transistors and radio parts used to build one GPTV is
15 to 20 times less than required to build the equivalent number of GT.
During the first years of development of the system there was orienta~ion
toward the development of attachments for the single-program speakers (Gr).
This solution arose from an effort to use the large number of Gr [single- ~
program speakers] available to the subscribers. This RT-61 type attachment
was produced at the Riga VEF plant. Since the subscribers basically had
quality class III Gr, it turned out to be impossible to realize the cl.~ss II
quality built into the attachment. The necessity arose for combining the
receiving-reneating part with class II Gr and making them in a single case.
~ Thus the Venta GT appe~red with higher sonnd quality which has found high
demand among the buyers. Later the improved GT were developed: "Riga," -
"Avrora," and "Mayak." In connection with the jmprovement of the processing
of the networks for receiving TPB programs in recent years, in nany cities
of the country it has become necessary to provide a large assortment of
receivers. The problem has again come up of developing attachment for the
Gr. The circuitry for such an adapter has been developed and is in the
_ experimental operational stage. The "Avrora" GT with somewhat simplified
high and low-frequency amplifiers was taken as the basis for the system.
Passive attachments are in the developmental stage which will permit the
owners of the receivers; tape recorders and television sets to receive three
programs without interference. They do not consume power and are simple to
service.
- 179
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The development of the receiving network will proceed in the direction
of creating new types of individual devices for various quality claeses, at
different pricES and with different external appearances.
Table 5.1 .
Standardized values _
Name of parameter GT GPTV
Sensitivity, millivolts 250 100
Output power, watts 0.15 25
Frequency band, hertz 100-6300 100-6340 -
liarmonic coefficient, T: ~
from 100 ta 200 hertz 7 6
above 200 hertz 4 3.6
Modulus of input impedance over the high-
frequency channels, ohms 2500 400 -
Background and noise level, decibe~.s -40 -55
Crosstalk attenuation between the high-frequency
channels, decibels -53 -60
Average sound gressure, newtons/m2 0.25 -
Noise protecti~n of the high-frequency channels: -
from the low-frequency g�rogram, decibels
at a frequency of 1000 h~rtz -53 -60 -
at a frequency of 6000 hertz -40 -
at a frequency of 10000 hertz - -50
Admissible overload of high-frt~quency channels
with respect to input level, decibels 10 10
Automatic gain control range witn respect to
input, decibels - 14
Response time of the automatic gair. control,
~ milliseconds 20
Increase in output level on disconnecting the load,
- decibels - 2.5
Limits of variation of the feed network voltage,
volts - 176-242
- The group devices were developed in three versions: GPTV-1 [19] developed
in 1962 had an output power of 25 watts; structurally it was made up of six
modules: a replaceable f ilter module (or the filters and the automatic gain
control system), the low-frequency amplifier module and feed module for one
channel and the same three modules for the other channel. This structural .
design is complex and expensive. The GPTV-1 was produced in two versions:
~ with automatic gain control and without it. Practice has shown that it is
necessary to build the receiver only with automatic gain control inasmuch as _
its cost increases significantly, and the operating reliability and range of
the TP B systea are increased. The GPTV-2 had an output power of 7 watts,
_ but simplification of the circuitry and the ~ceduction in its cost turned out
to be very small by comparison with the decrease in power; therefore the _
l-
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decision was made not to build it. The GPTV-3 which is built at the present
time is made with a modif ied circuit and structural design. The AGS circuitry,
filters and low-frequency amplifier have been simplified, the operatii:g reliabil-
~ ity has been improved as a result of using transistors with long service
life (P214 instead of P210 in the GPTV-1) and as a result of a reduction in
the number of parts; the structural de~ign has been simplifien: instead of
:ix modules there are three. The operating characteristics have been improved:
1. The sensitivity has been increased by four times, and the operation of
the automatic gain control, improved (it operates in practice without non-
linear distortions while insuring low voltage on the r~gulating diodes).
_ 2. The input impedance has been doubled. This makes it possible to install
the receiver on lon ger lines, and in combinati~n with increased sensitivity,
� it can be installed where the GT cannot operate.
3. The increase in gain of the receiver in an interval of 2 minutes increased
from 1.5 to 2 decibels. The high~discharge time constant leads to a reduction
= in the average transmission level with respect to the rated level. In the
given case the average level is closer to rated level. The range of the
- automatic gain control has been increased, which is more important for opera-
tion of the receiver. At the same time the dynamic range is not distorted,
for the distortions come only during a ~otal gain recovery time of the receiver
of less than 1 minute.
4. The rectifier with stabilizer has been made co~mmon to both high- frequency
channels. One stabilizer is cheaper and more economical. It has a higher
stabilization coefficient. The reliability increases, for the thermal condi-
tions of the transistors are equalized as a result of mo?-e uniform loading.
The total number of subscriber points serviced by one receiver is
H _ 25 watts = 140
- 0.25 watts 0.7 '
where 0.7 is the coeff icient of simultaneous inclusion of all points of the
given subscriber network. When using headsets (for example, in the hospital)
the number of subscribers connected to the GPTV can be increased to 400-500.
5.2. Riga Type GT
The Riga GT (Fig 5.1) has two band filters tuned to channels II and III
respectively, a detector, low-frequency amplifier with speaker at the output,
a three-position program switch and power pack.
In position. 1 of the switch IIa the. low-frequency program coming to the input
terminals of the GT is connected through the loudspeaker regu.'_ator R15
to.th~ transformer Tpl, the secondary winding of which has a loudspeaker
connected to it. In this case the AC n~twork is disconnected. In position 2
of the switch I[a of the RT, the network is connected to theinput of the
band f ilter tuned to a frequency of i8 kilohertz; simultaneously the filter
output is connected to the input ~f the detector; the output of the low-
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frequency amplifier is connected to the pr ~nary winding of the transformer
Tpl, and the power pack, to the AC network. In poaition 3 of the RT, the
- network is connected to the input of the band filter tuned to a frequency
of 120 kilohertz, and its output is connected to a detector, the output of
; the low-frec~uency umplifier is connected to the winding 1-4 of the Tpl
transformer, and the power pack is connected to the AC network.
_ ~ Alamrme~en ~1)
9a T
~ T All Sa .P~ P, rp
' 13�1/� ~ ,p tSO,t
~ R2 i~,
. ~ ~j ~ ~ 3 q ~ qf q T /113 ~ r� f~ $gZ
r ~
~C~,BL j ? . ~ T c"C,i~1:
~ ~s 6~~ ~ X ~n~ n~ '%rC~s
C~ . ~GOj ~1' M ~ ~ ,9 cn T 7.l
(i Rj 4 ~s ~r � A.. �?9~ A I.iU! /!r
~l~ ~ fd0 110 ux tn ~oB �ntiZr 'f7~ p~6 -
C~ ~ ` ~p, /1~
ltica , SO Ci ~ , ~ . ~ ~ ~ ~ - .
_ ~3~ ~ - . , '~2~ 19~i . ~
� ~ ,
Figure 5.1. Electric circuit diagram of the Riga type GT
Key:
1. Tape recorder ~
2. Electric network
3. Radio
The capacitor C1 blocks the path of the low-frequency program currents to
the preset regulators R1, Rz, whi~h served to equalize the initial levels o�
the high-frequency programs and prevent overloading of the detector. Their
shafts run to the face panel. Each band filter is made up of three loops;
for example, the filter of channel II is made up of ;he series L1C2 circuit
inductively connected to the parallel L2C4 circuit, and a third L3Cg circuit
connected by the capacitor C6 to the second circuit. The capacitor CS is
common to both channels. The shunting resistor R5 does not permit disconnec-
tion of the base circuit of the transistor T1 at the switching time and pre-
- vents it from breakdown. From the f ilter output the modulated signal goes
to the ingut of the emitter triode detecEor - the base-emitter 3unction of
_ the transistor T1. The detector has the least linear distortions when
installing a transistor with a value of S>,20. This stage has high thermal
stability, for the resistance to the direct current in the emitter circuit is
high. The resistors R5, R6 feed the initial bias to the base of T1. The
voltage on its collector is reduced using the R9R5 divider. The low-frequency
signal detected and ampl3fied by the same transistor from the load divid~d
into two parts (R~, R$) goes through the separating capacitor C10 to the input -
of the three-stage low-frequency amplifier operating in the class�A mode.
The resi:,:or Rg is simultaneously the volume control, which is aechanically
connected to the volume control R15 for the first channel. This coupling
.7 182
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eliminates the danger of short-circuiting of the output, which can occur on
movement of the regulator to its extreme position. In order to simplify
the commutation R15 is not disconnected from the primary winding T1 on
reception of the high-frequency channels. In this case it uses about 7~ of
the total output power in the maximum volume position.
The capacitor C9 filters the remains of the carrier frequency and also
increases the depth of the negative feedback for the higher sound frequency
harmonics. The feedback depth depends on the position of the regulator Rg,
which also increases the regulation limits. The first two stages of the
low-frequency amplifier are the emitter repeater based on the transistors T2,
- T3. When using the transistor with S>100 it is sufficient to have one stage.
The second stage of the low-frequency amplifier is made in accordance with
the transformer circuit with co~on emitter based on the transistor T4. The
_ low-frequency amplif ier mode is provided by the resistors R10, R11, R12 and
R14. The stability of the load with respect to direct current is insured as
a res~lt of connecting the resistor R17 to the emitter of the last sta~e.
The feedback with respect to AC voltage is fed to the input to the first
stage of the low-frequency amplifier. The feedback diminishes the nonlinear
distortions. The R16~13 circuit corrects the frequency characteristic for
high frequency and prevents receiver generation.
The electric power supply for the GT comes from the AC network. The rectifier -
is assembled in accordance with the double halfperiod circ�uit based on the
- diodes D1, D2 with a capacitive load of C15. The null potential point with '
respect to alternating current does not coincide with the positive end of the
rectifier. This made it possible to do away with two capacitors with a
capacitance of 200 microfarads each (C14, C15) and to decrease the cost of
the circuit. The filtration of the rectif ied v~ltage pulsations is accomplished
by the R1~C14 f ilter. The intake power in the network is 3.6 watts. In
order to connect the receiver to the relay network with ri voltage of 15 volts
it is necessary to resolder to Tpl (the wire running from the sliding contact
of the resistor R15 is unsoldered from the lead 1 and soldered to the lead 2).
The Riga GT [triple-program speaker] is made in a wooden case. On the front
there are controls for the preset regulators, the volume control and the
channel switch. On the back panel there are jacks for connecting a tape
recorder and two cords for connecting the receiver to the radio network and
the AC network.
5.3. Avrora Triple-Program Speakers [GT]
- The Avrora GT [triple-program speakerJ (Fig 5.2 and 5.3) is made in two -
versions: for operatic~l on the subscriber networks with voltages of 30 volts
and for Moscow, 15 volts. The basic parame~ers are the same as for the
- Riga GT [triple-program speaker], but as a result of introduction of the
high-frequency amplifier stage into the circuit, its sensitivity is increased.
The preset regulators are included here after the filter, which decreases
the variation of the input impedance of the GT for various positions of the
regulators. The program switch B1 has an additional "off" position. When
183
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FOR OFFICIAL USE ONLY '
a low frequency program is received the switch must be set to position 1.
The low-frequency voltage is fed to the primary winding of the output trans-
former TP1 through the fuses IIpl and IIp2 (which are included to keep the AC
network voltage out of the RT network and exclude ruining the GT if the radio
plug is erroneously plugged into the electric network) and the contracts 5,
6, 10 of the switch Blb' .
On reception of programs II and III the GT is connected to the radio network
by means of the switch Blb and to the feed network B1a. The band filter of
the second channel consists of the connected circuits L, C2L2C4; for the
third channel, L3C3L4C5. The high-frequency amplifier is assembled from
the transistor Tl; its collector circuit includes loops with tuning to the
high-frequency cFiannels which increase the selectivity of the receiver. The
diode detector is assembled from the D9V diode. The detected high frequency
signal goes through the volume control R,~a and the dividing capacitor C10
to the input of the low-frequency amplif#er, the first stage of which is
assembled from the transistors T2 and T3 included as a compositional transis-
tor. The connection to the terminal stage is direct. The low-frequency
amplifier is encompassed by negative feedback, the voltage of which is picked
up from a sep-rate winding 6-7 of the output transformer.
� - si~ . . 2 r~-_�-~
~ ~ (1) ~
~ I
: I - ~ s
o s ~ ~ ~ ~ ~,r,t~
e ~ n ~n -
s /
~ ~ ~ ~Nme ~ ~ e�w~~~ '�~uni R�y"' . I
! ` ! -
( , t'~ ~ ~ _ ~ ~R ~ T, ~aw
G . i u i eK I~ -~o ~
- ti~ ~ ~ ~ I
, n.e ,
i '
I ~ ~I,
~ y,~~ 4i M,~~c ~~r A ~ i~ `
~ p~ar ~s as ~
~
,~~4~,{~~! ~
~ ~3~ � _ .4l!
t'~~rwc'__ _
~ , .
Figure 5.2. Circuit diagram of the "Avrora" type GT.
Key: (1) volume (3) Program II level
(2) tape recorder (4) radio
The depth of this coupling depends r~n the position of the volume control,
which also increases the limits of its adjustment. The operating conditions
of the low-frequency amplifier are stabilized by the resistors R17, R18 and -
the DC feedback through the filter R14C12Rl 3 The pow~r pack is made up of
a power transformer, two-halfperiod rectif3er and II-filter.
184
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rux urrl~tt~, uaG ~rLx
[Photo not reproduced.]
Figure 5.3. External appearance of the Avrora GT [tripl~-program
speaker]
ihe Avrora receiver [35] is made in a wooden case weighing 2.9 kg. The
GT circuitry is mounted on a printed board fastened parallel to the face
plate in a case finished off with a plastic grating. This panel has the
- volume control and channel switch knobs. The knobs for the preset controls
are located on the back of the case (they are rarely used). On the back
there are also plugs for connecting the tape recorder, the network switch
for 127 or 220 volts with fuse and the leads of the cords for the radio net-
work and the AC network. ,
The "Mayak" GT (Fig 5.4) differs from the Avrora GT by changes in the input
circuits and the structural design.
[Photo not reproduced.]
Figure 5.4. Outside view of the Mayak GT [triple-program speaker]
185
FOR OFFICIAL USE ONLY
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- 5.4. GT with Low-frequency Channel Gain (Fig 5.5)
- It is known that the crosstalk from the low~frequency to the high-frequency
channels occurring in steel wire is reduced with a decrease in the low-
frequency current. The magnitude of the current depends on the load on the
line: the greater the load resistance, the less the current and the lesa
the crosstalk. Consequently, in order to decrease the interference it is
. , .r - ~ .
9 ~ (Z~ . ' . . ~ . .
- AXnt (3) j - _ = . -
B~ (b) (5) . ~ B~~ rPf(4~ ...`9, ~i 7~
r
~t ,,ys~~:~ n~:~e. ~ ~ ~'yti~'~
` ~::,~r:.~.,.~ y;:;~ o ~ ; ~Nnt ~
~ ~ ~ : (1~ ) .
~ � .
~ . (10) _ - .
. ~ Ba1np~K - .
PTcem~ (8) _ _ . . ~
. - ~ _ ~ . . . -
. ' . , . - - . 9l~.~E~~`(11) .
Figure 5.5. Structural diagram of the GT with low-frequency
channel gain
Key:
1. Control 7. Detector
2. Passive 8. R'T network
- 3. Active 9. Terminal low-frequency amplifier
4. Transformer 10. Rectifier -
5. Low-frequency preamplifier 11. Electrical network
6. High-freqsency part 12. Gr [speaker]
necessary to increase the input impedance of the GT connected to the
subscriber points, that is, to decrease the power fed to their input. Since _
~ the volume of the GT on the low-frequency channel must not be less than the
volume of an ordinary speaker, the decrease in power at the input must be
compensated for by amplifying the low-frequency signal, for which it is
impossible to use the amplifier available in the GT circuit which is used _
~o a~pl~fy the signals of programs II and III. The r.eceiver with amplifica-
tion with respect to the low-frequency channel has certain advantages in
addition to the decrease in crosstalk: the possibility of raising the low-
frequency characteristic appears; with simultaneous use of seveial plugs
installad in the apartment on fi.he low-frequency channel, the power intake
from the PV network in practice does not increase by comparison with the
- power intake by one ordinary speaker; the output power of the GT can be
- increased to 0.5-1 watt without increasing the network load; in the future
it will be possible to increase the number of subscribers connected to
the network without increasing the power af the station repeaters, The
~ 186
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possibility of improving the volume of the low-frequency channel both f or
liigher quality operation of the remflte subscriber points and for introduction
of stereophonic broadcasting requiring equal volume of both used channels,
is important. The signals from programs II and III go through the GT
exactly as in the ordinary GT without low-frequency amplification. The
78 and 120 kilohertz f ilters are installed at the receiver input. From the
output of the high-frequency f ilters the signal goes to the detector; the
detected signal goes to the low-frequency preamplifier. The input of the
terminal low-frequency amplifier is connected to the output of the low-frequency
preamplifier through the switch B1, which makes it possible to connect the
input of the terminal low-frequency amplif ier to the PV*network when listening
to the first program. The terminal amplif ier is loaded on the speaker which
can be connected directly to the network (without amplification) and it is
possible to hear the first program in the case of absence of voltage in the
feed electric network. As is obvious from Table 5.5, the GT with amplif ication
with respect to the low-frequency channel contains two additional switches
which provide for its operation with respect to the first program with or
without amplif ication of it. In ad~ition, the low-frequency amplif ier of this
receiver can be connected to the PV network only through the transformer.
The connection of the subscriber network to ~he input of the low-frequency
amplifier cannot be made without a transform~~r as a result of the high back-
ground level occurring in the output of the c~T.
These structural complications increase costs somewhat, and the introduction
- of an additional transformer into the circuit increases the copper consumption
for the wire broadcast needs. The problem of introducing this type of GT
has still not been solved.
5.5. GPTV-3 Group Device _
The GPTV is made up of two independent receivers distinguished from each other
by the filters and circuits in the high-frequency amplifier tuned to 78 and
120 kilohertz respectively and the common power pack. From the diagram of the
GPTV [18] presented in Fig 5.6 it is obvious that the receiver of one channel
is made up of the band filter, high-frequency amplifier, detector, low-
frequency amplifier and automatic gain control system. The schematic diagram
of the GPTV is presented in Fig 5.7. At the input the GPTV has a type K
filter, one element of which can provide for attenuation with respect to the
other high-frequency channel to 46 decibels. In this type of filter the
series and parallel branches are return two-terminal networks, that is,
Z1Z2=R2. This condition is satisfied when their resonance frequencies are
equal to w1=w2=w=7E kilohertz or L1C1=L2C2. In this case the selectivity
of the filter is improved. In the GPTV the filter is made up of one element.
_ Resistors are connected at ics input in order to decreas~e the effect of the
feeder line resistance on the frequency charactertstic of the filter. The
transformer L2 supp resses the cophasal interf erence operating with respect
to the "two wires-ground" circuit. The filter has an input impedance of
*wire broadcasting
187
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I
MUL BY
YR. DZYRDCH I K, S. A. ZRSLA~SK I Y
31 JANURRY 1980 B. N. F I LRTO~, R. SHERSHRKONR t FOUO ) 3 aF 4
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~
I
~
FOR OFFICIAL USE ONLY
. - lap. (2)
--------~�Ira6oytymaM (3)
" (4) !layarn'B~rrq ~ ~
~ -
~ .
1
t g)
Qune
p yBy ,Qtme yNy ~o~ON~HRIOM ( 3~
I
~ ~S~fu . ~6) ~7) . ~8) ' -
( pmpT ~ /!Py 10~ j .
' AuHU - - - --�-----J � � -
6noK N ce~rE
. numayus (12) ~ , ,
r---- 14
~uniinp yBy Qemen yHy ~ daoNeHma,~ 3)
~ ~2oKr ~ .
- � ~ (13) . ~ ~6) (7) ~8) I
.I . � ~ � ~ I
- - I APy 10~ ! ' � .
~ � /rUNdp 120I~PU~5~j .
� L------------------ -
Figure 5.6. Structural diagram of the GPTV-3 receiver
_ Key:
1. From the RT lines 11. Power pack
2. Program I 12. Network
_ 3. To the subscribers 13. Band filter 120 kilohertz
4. Channel 78 kilohertz 14. Program III
5. Band filter 78 kilohertz 15. Channel 120 kilohertz
6. High-frequency amplifier
7. Detector
8. Low~-freque:.~y amplifier
9. Program II
10. Automatic gain control
400 ohms (the average uupedance of the subscriber tsansformer on high
frequency).
The high-frequency amplifier with load in the form of a single two-stage
' circuit is based on the MP40 type transistors. It is used to amplify low
_ voltage of 5-10 millivolts on the regulating diodes of the automatic gain _
coztrol to a voltage sufficient for undistorted operation of the detector -
, and also to insure additional se?ectivity with respect to the adj~cent channel.
- The operating conditions o� the high-frequency amplif ier are stabil.ized by
including the resistor R9 in the emitter circuit of the transistor T2.
The input and output circuits are tuned ta the carrier frequencies by the
_ capacitors C5 and C10'
188
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The signal detector is two-cycle based on D9G type diodes. The current -
running thrnugh the load has a freqL~ency of 156 kilohertz, that is, the
current with a basic frequency of 78 kilohertz is absent in the load, which
facilitates filtration of the high-frequency component of the aignal. The
= condition of absence of nonlinear distortions i~i the detector is equality of ~
= the load resistances of the detector for direct and alternating currents,
~ rY?at is, observation of the condition RA~/RDC30.8. For this purposs th~.
load resistance of the detector is split into two parts: R11 and R12. Then
~ RBxRas 11 + 15�5,1 '
~ knep Rii -t- Rea -f' Ria _ 15-~-5,1 l~s Q,9e
( )
Rii Ri, 11-~- 5.1
Rnxr 2.
Key: 1. RAC~RDC
where RinP is the input impedance for the alternating current of the low-
frequency amplifier. The capacitance shunfi.ing the load of the detector is
selected equal to 620 picofarads, which cc~rresponds to a maximum transmission `
coef f icient of the detector and facilitates an increa in selectivity of the
receiver with respect to the other channel as a resulc pf using the properties
of inertialessness. The suppression of the interference at the detector output "
is proportional to twice the amplitude ratio of the signal and interf erence
carriers at the input of the detector:
� ~1)
rUc r~ = c~ cxrn
\ U - )8 \ Unax !ax (4 )
- r2) .
~ Key: 1. signa.l; 2. interference; 3. output; 4. input
Let us assume that signals of identical level arrive at the inputs of the
two channels. The int~erf erence of one of tnan, for example, II, is
1 measur~d in the interval of the useful signal when the carrier amplitude is
diminished by 20 decibels, that is, st the input of the channel the inter-
f erence exceeds the signal by 20 decibels. In the f ilter this interf erence -
is attenuated by 40 decibels and becomes lower than the signal level by
20 decibels; in the high-frequency amplif ier the interference is attenuated
by another 15 decibels. The detector gives suppression by 35+6=41 decibels,
that is, a~ the output of channel II the interf erence from channel III will
- be attenvated by 35+41=76 decibels. If the interference comes to the
channel input, for example, 3 times the signal level (by 10 decibels), then
it will be attenuated by 56 decibels in the receiver. The filter and the
circuits ~f the high-frequency a~plifier also provide for suppression of
~ the crosstal~C from the low-frequency channel t~ the high-frequency channel
by 60 decibels.
189
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,
FOR OFFICIAL USE ONLY
~ - - . .
~r:r~:7cvcXrrx 74~d'q d~
- I . . . s.ax ~
~l~
. � ~0 , ~ ~
I t4a ~
N, A, qexr ~s ~ c+' ~ Il'v.~ax ~T, i Q
I "if.~ TP,t T ~j91 .
, c, R,, . ~S ,~nvo
~.l ~ ~ wis~~ ~.~lr � ; ~~1~/r' i! u!X
( lr4 At ca i , ~ 'o . . -
C~ s P, ~ ~n
d' . 9 _
0
1Gn 2~70 ' . .
1 ~ ,
- . ~B Cp9~
` . . w_ ~ ~YY L11r .
K
.
.e.~ �
I 6~o~r ~umrrNrrp qp -
. . : ~ ~2~ masxso -
. IYS B~ ~1P~ T'~ .I{~ '
_ _ . = ~ . 'A a ~ .
. ~ ~ ~p~ ~ A - c G C ~ -
- - I 1A 11~dSr~ ~ t~~ I
. Aa ~~g p , ~ ~
- . ' ~ . - . . . . . : ' - ~
_ y _ I . . . : , ~ .
. ~ ~ . - -
Figure 5.7. Circuit diagram of the GPTV-3
~ey:
1. Amplification module 78 kilo'r~ertz
2. Power ;pack -
_ The first stage of the low~-frequency amplifier based on the MP40 type
_ transistor operates by the system with separated load and is used for
transition tothe two-cycle stage. The load resistance is in the collector
_ ci~;:uit and is divided into two parts: R14 and R16. The high internal
impedance offers the possibility of encompassing subsequent stages with
feedback. Since the input impedance of the next to the last stage is low
. as a result of the negative feedback, the first stage does not give voltage
amplification. The stabilization of the operating conditions of the
_ transistor T3 is realized by the resistors R15, R16' The coupling to the
190
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a�/~~ ~
~w.~~ Ar 6YY TB /7 ~ '
R~ ~ ~ ~r ~v~ ~r
� Rq I,VX ~rQ ` J: J l � ~
~ c : ; ~ ra
. ~n ~~~r~. i ~
ia S.., D , l A' I
~ T 3,0 B~s ~..y--,=r~
- , . d~ r~ ~ A1QU0 C~ ~ ~ ~ ~ ~S /A
� ' 4 5~,~ ~ i ~ 8
~r ~ t ~ .
R ( )
x~ R~ -r'-~. 4 ~'c
~ ~,3 1S0 Ts ,;pi.: ~ ~ t� ~ r
d( F'Pr ~ ~ w I
.y , 'a
_ ~
Ir~ ~ `
' , � ~yyK � ~ � i2; ~fB ' 1
~ . ~ ~
zJ0 . . ' . . -
~i ~ . ' . ~ I
~ .J
~
Ts
. ~ t I
~ . .
' '~X T n31~IQ T'
~ . ' I .
~
_ . - ~ ~
ro ~-~~lt . `
YRVJ.4 ~ 1~t5 ~
- ~ R Rn .
i'~ 5~ qtf 0~ t.~ -
� A~ ? si~ R
~ ~ ~~Pl ~ ~ ~X~
iw
a. - rP~? 3A N
y~~.''~ ~ 3)
~
3. Ta the channel 120 kilohertz
4. MP40
5. MP40A
next to the last stage is rheostat-capacitive. This two-cycle transformer
~ stage executed from the MP40a transistors gives voltage amplification from
100 millivolts to 10 volts. The t~rminal stage is m~de from P214V type
transistors in accordance with the circuitry with grounded emitter. It
operates in the class B mode. In order to eliminate the nonlinear diatortions
of the central cutoff type, especially noticeable in the case of low signals
and low air temperature, the initial bias is fed to the bases of the _
transistors T6-T9 trrough the resistors R24, R25 and the thermal resistances
which also stabilize the opGraLing conditions of the s.*.age on variation of _
191
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the ambient temperature. Eac'~ pair of parall,~l-connected transisters is
located on the radia~or, which insures normal operating conditions of the
receiver even under the conditions of short circuit load and high air tempera-
ture (+40�C). In addition, provision is made for two-stage protection of
the transistors from short circuiting using fuses. The output and the next
to the last stages are encompassed by parallel feedback as a result of which
the low-frequency amplif ier haa low internal impedance and operates well on -
variable load. On disconnect.ion of the load the output volr.age increases from
30 to 32 volts. The RC circuit which eliminates possible generation when
working with the disconnected or capacitive load is connected t~ the secondary ,
winding of the output transformer. Inasmuch as trie GPTV operates without
- constant servicing and operative level controJ. at its output is impossible, _
_ an automatic gain control is introduced into the circuit which is designed
for fluctuations of the high-frequency signal level within the limits to
- 14 decibels. Introduction of the automatic gain control offers the possibility
of installing the GPTV at the end of the long lines and insurance of stable
operation with a large number of subscribers. The fluctuations of the attenua-
tion in the lines occur slowly, over a period of several hours, for they are
basically determined by the meteorological conditions. The rapid jumps in
level are passible in the case of damage to the line, and fast response of
the automatic gain contrcl is required with an increase in the input level, _
but slow recovery over a period of several minutes is admissible with a
decrease in it. The response time of the automatic gain control is selected
equal to 20 milliseconds (on cc,nnection of the broadcast programs the non-
liriear distortions are undetectable to the ear), and the time for increasing
the gain by 2 decibels (after picking up the input signal) is 2 minutea.
The difficulty in building the automatic gain control consists in the fact
that the known procedure using carrier frequency fluctuations is unsuitable
in the case of 98M signals with variable carr3er, for it leads to compressiun -
of the dynamic transmi~sion band and tQ an increase in noticeability of the -
- crosstalk in the intervals. It is also impossible to use a pilot signal for
automatic gain control, for its frequency must differ fro~ the carrier
freq~sency by no less than 15 kilohertz so that the beats between the carrier
and the pilot signal are not noticeable. However, in t',is case tYie relative
difference between the freQuencies of the carrier and the pilot signals is
found to be large, and the attenuation in the signal for these frequencies `
can turn out to be different, that is, the variation in 4mplification as a
result ~f the effect of the auto~atic gain control can fail to coincide -
quantitatively with the actual requirement of the variation. In the GPTV
the automatic gain control is used with storage of the maximum carrier level.
Since the output ~oltage of the lourfrequency amplifi.er is proportional to
thE carrier level, a winding is wound on the autput transformer to see to
the operation of the automatic gain control. The selection of the regulator
for the automatic gain control is conditioned by the sufficient range of
control and comparatively low nonlinear distortions in the entire control
range with maximum admissible level of thE input signal (in order to h~ve
less amplification of the high-frequency amp].ifier). A regulator was
selected which operates by the potentiometric system and has low high-frequency
resistance so that shuntin~ of it by the input impedance of the high-frequency
192
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amplifier will not decrease the control range. The semiconductor diodes used
in the conduction region do not introduce distortians for a high-frequency
signal level up to 5-10 millivolts. The D226V type diodes are used in the _
circuit. They are connected in series with respect to direct current and
parallel with respect to low frequency. The control consists in variation
of the transmission coefficient with respect to the high-frequency divider
made up of the resistor R4 and the diodes D1, D2 with variation of the
magnitude of the direct current f low through these diodes.
_ The automatic gain control ~perates as follows: the low-frequency voltage
is detected by the diodes D5, D6, and the direct ~~urrent flowing through the ~
diodes D1 and D2 chariges their resistance with res,~ect to high frequency. _
The resistor R4 and the controlled resistance of the diodes form a divider
with automatically variable ratio with respect to high frequency. With an -
increase in voltage at the input, the direct current increases, and this
ratio decreases. The stabilizer voltage of 23 volts is used as the delay. -
The detector of the automatic gain contral has large dischar~e time constant ~
(several minutes), which keeps the amplification coeff iciei~t :n the trans-
mission intervals and the dynamic range invariant. This discharge time is
created by a capacitor C9 with a capacitance of 200 ~icrofarads and the
resistor R~ with a resistaiice of 2.7 megohms. The sensitivity of the receiver
in which the automatic gain control begins to operate is 10 millivolts.
- With an increase in the input level by 14 decibels, the output voltage varies
frum 23 to 33, that is, by 3 decibels. The automatic gain control does not
introduce noticeablc nonlinear distortions; the deficiency of it is an -
increase in noise after prolonged interruptions and a decrease in volume by -
2 to 3 minutes after the pulse interf erence.
The electric power supply of the GPTV is autonomous --from the AC network.
The f eed module is cou~on to both channels. The rectifier is double half-
period. It is equipped with a filter which starts with the choke, which is
better for operation on a variable load (at *_he filter output the DC voltage
varies to a less degree than for the f ilter beginning with the capacitance).
~ Inasmuch as the GPTV is fed from the household network, the voltage of which
can vary significantly, and it operates without servicing, it is impossible
to guarantee fail-safe operation of it without stabilization of the DC
_ voltage. The AC voltage stabilizer does not fit here, for it has a large
scattering field (which leads to a high background level of 50 hertz at the
receiver output) and also in con..ection with the fact that the terminal
stage of the low-freqiiency amplifier operates in the class B mode and is
a variable load for the rectif ier, the voltage at the output of the rectifier
_ does not rema~n constant. The operation of the stabilizer is based on the -
fact that the magnitude of the emitter current in the transistor does not
depend on the voltage var3.ation of the collector. If we connect the load
(the receivers) to the emitter circuit of the stabilizing transistor T13-T15'
the em~tter repeater circuit is obtained in which the voltage on the load
is almost equal to ihe voltage on the base of the transistor. It is
necessary to keep the voltage on the base constant. On variation of the
load, the emitter and base currents vary; therefore in order to obtain a
a 193
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FOR OFFICIAL USE ONLY "
DC voltage on the bases of the T13-Tl , two stages based on the transistors
T11-12 ~P214V) are included. The voI~age on the base of T11 is stabilized
by the "parallel stabitizer" circuit using the transistor T With an
increase in voltage at the input of the stabilizer, the vol~~ge increases
somewhat also at its output. Hexe the voltage on the base of T10, its
collector current and voltage drop on the resistor Rlp increase. The
voltage on the base of T11 decreases, and the voltage at the output of the
stabilizer decreases. Analogous processes take place with a decrease in
feed voltage and on variation of the load. On variation of the network
voltage from 176 to 242 volts and with simultaneous variation in the load -
current from 0 to 4 amps the voltage at the output of the atabilizer varies
_ by no ~ore than 4%. In order to increase the operating reliability of the
stabilizer the output stage is assembled from three parallel-connected
transistors of the P214V type with resistances in the emitters of 0.3 ohms
each which equalize their current. In addition, the transistors are located
on the radiators, which insures sufficient reserve with respect to the dissi-
pation power. The stabilizer has low internal impedance with respect to
alternating current; therefore the operation on both channels of the receiver
*aithout an increase in the crosstalk between them is possible. The power
intake by the GPTV from the network in the rest mode is 33 watts and in the _
rated power mode in both channels, 180 watts.
- Structurally the GPTV is executed in the form of a small bay in which there
are three modules: the receiver module for channels II and III and the power
pack. The bay is closed by a removable door to kiiich a lock is fastened.
The external appearance of the GPTV is presented in Fig 5.8. The GPTV is
_ m~unted on the stairwell wall of the upper story of the building as clos~
as possible to the subscriber transformer, or it is installed on a table in
tile specially assigiied facility. The receiver is connected to the TPV
[triple-program wire broadcast] network by the sch~me shown in Fig 5.9
(to the secondary winding of the subscriber transformer) or Fig 5.10 (to the
distributing feeder through the bypass increasing the magnitude and the
stability of the high-frequency program level if this level is below 50 milli-
volts). The outputs of all three channels are connected to the intermediate
terminal block instalied on the rear wall of the bay. The three-pair, intra-
building network is made of KRVPM-3x2x0.5 or KRVPS-3x2x0.6 cable which runs ~
from the GPTV to the subscriber switches through the KTVO splitter blocks. -
[Photo not reproduced.)
r^igure 5.8. External appearance of the GPTV-3
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� ~ ~ ~ (5)
(1) ~ ~2) � 8~a B r~
r-- -
~ . I 1 d 1 1'I ~
~
~4~ - - - -
a~ rnre
Figure 5.9. Connection at the GPTV through the OU sectional center `
Key:
1. Distributing feeder 4. GPTV
2. Subscriber transformer 5. Speaker
3. Sectional center a
, AT (3 ) 3X _ �
, ~r .
, bf
~ .
. l'l)T8 .$d
~ ~
, ~
Figure 5.10. Connection of the GPTV tothe subscriber transformer -
Key:
1. GPTV
2. Distributing feeder
_ 3. Subscriber transformer
The output level of 30 volts is established in each channel by the level
control on f eeding the low-frequency signal to the input with modulation
_ frequency of 100 hertz and depth of 70% on a load equivalent of 36 ohm~.
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CHAPTER 6. MEASURING DEVICES AND INSTRUMENTS
- 6.1. General Information
The proper operation and maintenance of the TPV [triple-program wire broad-
- casting] system requires the application of the corresponding measurement
equipment for tuning the transmitters and reGeivers, amplifiers, measuring
the electrical parameters of the low and high-frequency transmission chann~ls.
The TPV system has a number of peculiarities which complicates the application
' of the existing measuring equipment and which must be considered when develop-
ing new instrumen~s. These peculiaritics include the fcllowing:
Amplitude modulation with adjustable carrier level wict~in the limits of 10 to
100%;
A broad pass band with respeci to the carrier equal to +1~ kilohertz;
Rigid requirements on tlie harmonic coeff icient;
The presence of various channels (low and high frequency);
Signifi~ant voltage of the low-frequency channel sub~ect to measuremEnt (~o
300 volts);
Great difference in magnitudes of the voltages of the low and high-frequency -
channels to 1000 times. _
The stability of the signal level of programs II and III in the RT networks
is appreciably worse than the signal of program I; therefore the demand for
monitoring them increases. The measuring equ~pment for the TPV must have
smal~l nonlinear distortions, a wide modulating frequency band, small cross-
talk between channels, ad~ustment of the output voltage within broad limits,
syrtunetric input and output, relatively large input and small output resistances..
With respect to purpose the instruments can be divided into stationary and
portable.
- 196
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The stationary instruments make it Possible to centralize the measurements
at the TsUS, OUS and TP. Frequently they are built into the station
equipment, for example, into the SVK and STP bays. Portable instruments
have been designed for monitoring the networks and lines. They are produced
in large quantities, because the line service personnel need them.
~ The modulation attachment and the test signal pickup with high indexes of
standardized electrical parameters have been developed for the TPV.
The simplest measuring instruments are the lineman's display and the RTPV-2
pulse meter, by means of which it is possible to meascre the voltage in
each of three channels.
A complex resistance meter has been designed for introduction at the line -
development system measuring the resistances of the lines and sections
of them. A high quality monitoring receiver (KPU) is also used to check the -
high-frequency network of development units.
It is possible to measure the level diagram of the high-frequency programa
on the distributing f eedere by using the high-frequency VRG-3 measuring
oscillator [31]. A damage finder has been developed to find damage in the
~ radio relay lines. All these instruments are transistorized. They are
small in size and lightweight.
6.2. Modulation Attachment -
The modulation attachment (MP) (Fig 6.1 and 6.2) is a source of AM signals
of the carrier frequencies of 78 and 120 kilohertz, and it is needed to
check out the receivers, amplifiers and line devices. In addition, in
combination with the KPU the attachment can be used to check out the dis-
tortions of the shape of the AM signal envelope introduced by the passive
- network development units. In practice the attachment makes it possible to
~ make an entire set of ineasurements of the quality indexes and eYectrical
~ characteristics (with the exception of the time parameters) of all active
and passive devices :~n the system.
The MP circuit contains the low-frequency f ilter FNChl, the phase shifters
FV78 and FV120, modulator, the low-frequency filters FNCh2 and FNCh3, the
modulated oscillation amplifier iTMK, the circuits K78 and K120, the
symmetrizing transformer (ST), the monitoring detector, the channel switch,
the output voltage switch and regulator, and rectifier.
The attachment operates jointly with the osciliators: G3-33 is the source
of carrier frequencies and G3-35 is the modulating frequency source. In _
= the f irst case the voltage from the oscillator is fed to the high-frequency
input, and in the latter case, to the low-frequency input. The resistance _
of the high-frequency input is nonlinear and small in magnitude. In order
to decrease the voltage of the carrier frequency harmonics, the FNCh-1 low-
frequency filter is included at the modulator input. Although the circuit
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� _ 3 .
. ~ ( --1.
.
~ a6~~?~ ~ ~ ~ ( ~ s,r~r ~ (9 � _
� ( ! � sa+'v m R Ir ~
~ l ~�s '~a D �e~ uo ~r ~ e� ~12).
~ ~11~'0"'~ - '
(2) ~v4 ~ y ~ . ~~lg~
~I 1 ~da9 .
_ ~ y ~ . . . , .
~+apura~a~t (15) ~ ~ �
Figure 6.1. Modulation attachment
Key :
I. Low~frequency 8. Decibels -
' 2. Hig:~ frequency 9. UMK modulated oscillation amplifier
3. Frequency 10. Vo~tage
4. FNCh2 low-frequency f ilter 11. Manitoring detector
5. FNCh3 low-frequency filter 12. High frequency
6. Modu~atar 13. Low frequency
7. Regulator 14. FNChl lourfrequency filter
15. Rectifier
- [Photo not reproduced.] '
Figure 6.2. Outside view of th~ modulation attachment
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diagram of the modulator is more complicated than usual, it provides small _
nonlinear distortions with great depth of modulation. From the modulator
output the AM signal gces to the input of the LTMK, where the signal is
power-amplif ied. Since carrier frequency harmonics occur in the modulator,
the FNCh2 and FNCh3 low-frequency filters are included in the circuit to _
eliminate them.
In order to decrease the cross modulation in the UNIIC during testing of the
~ various TPV ~levices for noiseproofness, the K7F and K120 circuits are
- connected to the output of the UI~C. The symmetry of the output of the MP is
insured by the transformer ST. In order to check out the operating quality
of the attachment, that is, to measure the nonlinear and frequency distortions
' introduced by the modu'_.ator 3nd the UMK, the circuits include the monitoring
detector. Connecting a meter to measure the nonlinear distortion coeff icient
~ and a voltmeter to its output, it is possible to measure the frequency
characteristic of the MP and the harmonic coeff icient with respect to the
" env elope.
In order not to equip the portable device with a special power supply, the
UMK is powered by rectifying the. high-frequency voltage from the G3-33
generator output. At the output of the attacr.*.aent, a modulated voltage is
obtained with carrier frequencies of 78 and 120 kilohertz and a modulation
;:~pth oF m=70%. It is possible to regulate the magnitude of this voltage
- from 15 mv to 6 volts. The rated voltages are switched from 0.3 to 6 volts -
with an output power of 40 milliwatts.
The MP is a high-frequency device. The range of modulating frequencies
is from 50 hertz to 10 kilohertz with nonuniformity of 0.2 decibels. The
harmonic coefficient in the frequency band of 50 to 5U00 hertz is no more
than 0.2% (at the monitoring detector output). The ratec~. input voltage of
!8 and 120 kilohertz is 12 volts; the modulating frequency voltage is
11 volts.
The rated voltage at the output of the monitoring detector on an active
- load of 100 kilohms with parallel capacitance of no more than 300 pico-
farads is 0.775 volts. The input impedance for frequencies of 78 and 120
kilohertz is 30 ohms; for the modulating frequencies it is 600 ohms. The
crosstalk between the channels is 70 decibels.
6.3. Lineman's Indicator
The indicator is designed to measure alternating and direct voltages of
three channels an3 resistances of two direct currents. Its circuit diagram
is presented in Fig 6.3. -
The indicator is made up of two switches, two voltage dividers, f ilters,
- a rectifier and microammeter. There are five jacks at the indicator input.
One of them is common, and one of the wires of the line is connected to it.
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Depending on the measured parameter it is necessary to connect the second
wire to the jack: V~ for measuring AC voltages; V= for measuring DC voltages;
Rxl and Rx100 for measuring resistances.
The limit switch II1 of the scales for measuring the voltages has five
positions: from 0.5 to 1.5; 6, 30; 150 and 300 volts. The switch for the
type of operation IIZ also has five positions:
nch measurement of AC voltages;
78 measurement of the 78 kilohertz carrier voltage;
_ 120 measurement of the 120 kilohertz carrier voltage;
V= measurement af tne DC voltage;
St measurement of the resistances to direct current.
The first voltage divider I DH is connected to the AC circuit. It
switches from the 1.5 scale to the 6 volt scale. On switching to the 30 and
150 volt scales it remains in the 6 volt position, and the variation of the
scale limits is realized by the second divider II DH included in the
- DC circuit. On making the transition to the 300 volt scale the second divider
remains in the 150 volt position and again enters into the operation of the
I DH. This complication of the scale switches is intended to decrease the
error in readfng the instrument as a result of the effect of spurious
capacitances and the possible asymmetr;~ of the measured low-frequency voltage~
The II DH decreases the power of the rectified current to the magnitude
required for complete deflection of the instrument indicator, and it reduces
the effect of the spurious current to a minimum. In order that during
switching the filters not change the frequency characteristic, the resistance
of the I DH must be constant. This is insured by inclusion of resistors R1-R5
and R13. The second divider is made up of the resistors R22-R24; it insures _
constancy of the load rPSistance of the rectifier which is assembled on the
basis of the diode D. The capacitor C15 filters out the variable components
of the currents after detection.
The filter of the low-frequency channel is a 1I-type L1C1C2 element with
cutoff frequency of 15 kilohertz. The 78 kilohertz filter is made up of the
~ three-element band filter L2L3L4C4-Cg, and the 120 kilohertz filter, from
one element L5~6~12-~14� -
The AC voltages are me.zsured by the circuit in Fig 5.4. The scales of the
in3icator are calibrated in the effective values of the AC voltage. The
instrument error does not exceed 7%. When measuring the voltage of the _
high-frequency channels as a result of the crosstalk between them the
additional error does not exceed 3%. When measuring the low-frequency
voltages the error as a result of the crosstalk from high-frequency channels
is absent. When measuring the DC voltages the measurement limits are
200
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- FOR OFFICIAL USE ONLY
~ ~
' o,~, ~H
~ . . .
C
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201
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determined by the resistors R~-R10. In this case the meter has a high -
input impedance caused by high sensitivicy of the mi~roammeter.
In order to measure the resistance to the dirECt curr.ent the indicator has
a two-limiC oiimmeCer mude in accordance with the serie~t circuit with balance
null control. The pow~r suppl; of the indicator is the KBS-D-0.5 type dry
cell.
_ ~ ~i .
. . ;
g, ~ ~ Bs ~ f. '
. V / ~t~ ; ~ . M
~ . � . ~l~-
. . .
Figure 6.4. Circuit for measuring AC voltages MI �
Key:
' 1. IP iridicator -
- 6.4. Complex Resistance Meter (IKS)
When introducing the TPV [triple-program wire broadcasting] it is necessary
to carry out tedious high-frequency development of the RT networks in order
to create conditions close to the traveling wave conditions and insure an
input impedance with low reactivity, which var~es little in the frequency
bands from 72 to 84 and from 114 to 126 kilohertz.
The existing instruments do not permit measurements of the total resistances _
with unknown magnitude and sign of asymmetry on the required frequencies
with given error. Thus, for example, when making the measurement by the
MPP-300 bridge it is necessary to know in advance whether the resistance
- subject to measurement is symmetric, and if it is asymmetric it is necessary
to know the sign of the asymmetry.
The IKS instrument can be used to mea.sure the input impedances of lines and
secti~ns of lines, TP [transformer substations] and high-frequency devices
having any asymmetry with respect to ground. Its operating principle is
based on measuring AC voltage f ed to the input of the line with a magnitude
of current f lowing through the line known in advance (Fig 6.5). Within the
limits of one scale this current is always establ3shed at one and the same
value b~ regulating the measured voltage of the line input. In this case,
in order to discover the magnitude of the modulus of the input ~mpedance of
the line it is sufficient to measure the voltage at the input of this line,
and it is possible.to calibrate the voltmeter scale directly in ohms.
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In accoxdance with this operating principle, the str.uctural diagram of the
IKS depicted in Fig 6.6 has been developed. It includes the following:
the oscillator, the reactivity box, voltmeter and switching devices.
" A.
t
~ ~ ~ L
ZX
- Figure 6.5. Operating principle of the IKS [complex resistance
met er ]
Key:
1. generator
~ BlJXO~NO(1 ( 2 ~ � `
' , . . " " ~ ~paNC~~ae~a~,~n . ~
~1) QJ~,~o~ra~?ocnu~ ycunum.e~j e,-~� ~ ~ID
..~~.T~ . .
i
~ i 3) �r': 3 B, Z
~ q~ -
L~ _ A r:.
l 1..~-0c'
i 3 ,x, E Br~ 1 -
_ v ~
~ Om~yun A'a~ ~ ~
5 6 . M~tO.~uH (7)
~
Cin~7mue~~+� a;:c~xr~mr~ (4) . ( ) ( ) . ~ea~rmuCNOCmcu .
~ Figure 6.6. Complex resistance meter .
Key:
1. Wide band amplifier 5~ Reading
2. Output transformer 6. Calibration
3. Calibration 7. Reactivity box
4. Selective indicator
The generator consists of the master stage and the wide band amplifier
and is used for f eeding sinusoidal signals of given frequency and power to
the measuring circuit.
The generator can provide four fixed frequencies: 0.4, 3, 6 and 10 kilohertz;
it covers two bands: from 68 to 88 kilohertz and from 110 to 130 kilohertz
with smooth tuning. -
203
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~ The wide band amplifier (ShtJ) has a pass band from 300 hertz to 150 kilohertz
with a nonuniformity of 4 decibels.
At the output the amplif ier provides a power of 50 milliwatts on all operating
Frequencies on a load of any nature.
The gain cuntrol in the wide band amplifier (ShU) is used to calibrate the
instrument, that is, the magnitude of the current flowing through the line
oC determined magnitude selected when designing the instrument is established.
~rom the amplifier output the voltage goes to two output transformers: one
for low frequencies and the other for high frequencies; and from their
secondary windings it goes to the line, that is, the load of the amplifier
is the measured resistance of the lir.e, and when measuring the total
resistances the reactivity bo~ also. The calibration resistor Rsh
is connected in series in the line circuit. The current in the line is
established (the scale is calibrated) by measuring the voltage drop on this
resistance. In order to increase the precision, the range of ineasured
resistances from 20 ohms to 3 kilohms is broken down into four intervals: -
20-100, 100-300, 300-1000 and 1000-3000 ohms in the frequency band of
channels II and III. It is desirable that the power fed to the line input
during calibration would be identical on all intervals. Tk?erefore, the
circuit includes the switch B1_1 which realizes discrete measurement of the
voltage fed to the line input: the higher the input impedance, the higher
the fed voltage. However, since at all limits the voltage corresponding to
- the lower limit is measured, in order to eliminate the error in the measure-
ments the magnitude of the calibration resistance on variation of the mFasure-
ment limits also is varied by the switch B1_2. -
The shunt resistance is selected small in order to decrease the errors when
measuring the modulus of the r~actances so that in the least favorable case
- (when measuring the resistance moduli near 20-30 ohms) this erxor does not
exceed 10%.
~ The input of the ohmmeter is switched by means of B4 from the calibration -
resistor Rsh to the output of the generator through the voltage divider R1,
R2. Since the scale of the voltmeter is not calibrated in volts, it is more
correctly called an indicator. The selective indicator includes the band
f ilters, a wide band amplif ier, detector and the M265 type magnetoelectric
microammeter with a sensitivity of 200 microamps.
- The filters with an average frequency of 78 and 120 kilohertz pass only the .
f irst harmonic of the frequency on which the measurements are made, and -
the harmonics of this frequency are delayed which can occur both in the
generator itself and in the real line. The elimina.tion of these harmonics
increases the accuracy of the measurements. .
The anglesbetween the active-ard reactive components of the input impedanc~e
are measured by the compensation method: the reactanCe opposite with
respect to sign to the reactance of the line input is connected parallel
to the line input, and its magnitude is established so that these reactances
204
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are mutually compensated fo.r. Here the modulus of the input impedance of
the line reaches the maximum value an3 becomes purely active. The compensating _
reactivities are included in the composition of the IKS meter and are an
inductance and capacitance box. The inductance box contains five stagas:
"off," "0.75," "0.25," "0.75" and "0.025" millihenries, that is, it can
assume only discrete values. Therefore, for exact compensation of the i
capacitance of the line input, a variable-capacitance capacitor is connected
in parallel to the inductance.
Thus, after obtaining the compensation for the reactivity of the input
impedance of the line with respect to the scales of the boxes it is possible
to reckon the values of the capacitances or inductances required for compensa-
tion and calculate by them the compensated magnitude of the reactance and
the phase of the input impedance of the line. The basic instrument when
- iaeasuring the angle wi~.l be more than 15%.
The instrument is f ed from three of the KBS-0-0.5 type batteries during the
summer operation of th~ instrument and KBS-Kh-0.5 in the winter. The ~
rated feed voltage is 13.5 volts. In order to indicate the on condition and
to check the voltage of the battery, a M4283 type indicator is used.
In spite of some complexity of the process of ineasuring the complex value of
the input resistances of the line, the IKS greatly facilitates and accelerates
tiie processing of the lines, insuring good quality of the high frequency ,
channels.
6.5. High-FYequency Oscillator (VIG-3)
In order to record the level diagram on the distributing feeders and also
to measure the modulus and the angle of the input impedances of the feeders,
the VIG-3 type high-frequency measuring generator can be used. The oscillator
permits voltages of the carrier frequencies of 18 and 120 kilohertz to be fed
to the line simultaneously to pick up the level diagram of the channels or
- sections of the channel. It is connected to the distributing feeder gap
instead of the feeder protectors at the transformer substations.
In contrast to the IKS, the VI~3 feed is realized from the AC ne~work (the
intake power is no more than 25 watts), which limits the region of its
application.
The structural diagram of the VIG-3 is depicted in Fig 6.7. The instrument
is made up of the 78 and 120 kilohertz oscillators, a transformer designed
for connection to the line and therefore called a measuring transformer,
devices which measure the high-frequency voltage at the output of the line "
and the current in it and also a phasometer.
The feed unit is common to all of the modules of the circui~~, and it is a _
rectifier with stabilizer, at the output of which a DC voltage of 12.5 volts
is maintained.
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~ 1 ~ 31' ~NOI!(N. rtnsm ~H~. ~/vyuT~
7BM'q ycunu 7B~r!'q
- ~2) (3) (4) (5)
~na aNep. ~ude
numoH (6) mp p p (8)
.
3~ Afou~x. u~wn � ~
r~7i~-u yau~a ~ 120~rrq ~~'p z
a~M~14)
Figure 6.7. High-frequency VIG-3 oscillator
Key:
1. "/8 kiloherta master oscillator 8. F.eeder
2. Power amplif ier 9. 120 kiloliertz master oscillator
3. 78 kilohertz filter 10. Power amplifiPr
4. FNCh-4 low-frequency filter 11. 120 kilohertz filter. -
5. Transformer substation buses 12. ~-meter
6. Rec t if ied f eed 13 . Z-met er _
_ 7. Measuring transformer 14. Zmeas
The oscillators are identical with respect to circuitry and are distinguished
only by the magnitudes of the circuit capacitances and inductances. Each
oscillator is made up of a master oscillator, buf~er stage, terminal stage
power amplifier the output circuit of which includes a band filter for
the correspondiiig frequency filter. The oscillator can give a power of
1.2 watts on a resistance of 100 ohms.
Fig 6.3 shows the device by means of which the input impedance is measured,
_ that is, the voltage at the input of the line, the current through it and
the phase shift angle between the current and voltage.
A simple, convenient method of ineasuring the phase angle of the input
impedance of the line is used in this instrument. This procedure consists
in the fact that a voltage ~s fed to the pointing indicator through a ring
_ modulator which in the given case is a controlled rectif:ier. It is
assembled from four diodes D1-D4, the signal voltage sources Tpl, C1-C2,
R~-R2, the load resistances with the midpoint R3, R4 and the sources of
the controlling voltage Tp2, the pr;mary winding of which is connected to
the resistors R~-R1~. The amount of a voltage drop on them and, consequently,
on the windings of the transformer TP2 is directly proportional to tne
strength of the current running through the line. The secondary winding of
this transformer is connected between th~ midpoints of the load and the -
oscillator, the role of which is played by the resistors R1-R2. It is
obvious that in view of the sytmaetry of the circuitry this voltage will be
absent between the ends of the resistors Rg and R4. The signal voltage from
the Tpl through the capacitor C~ or C2 is f ed to R1, R2. Since the amount
of the capacitances is selected so that their resistance on frequEncies of
. 78 (C1) and 120 kilohertz (C2) is appreciably ~reater than the sum of the
206
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resi~~ances R1 and R2 with parallel-included R3, R4, the voltages on R, RZ will -
be shifted with respect to the voltage on the windings of the Tpl by 9~�.
'L'I~e pl~u~c meter oper~tes .tn the followin~; w~y. Let ua pr.opose thut 1nHtcnd
of the line the capacitor is connected, the magnitude of the impedance of
which corresponds with respect to modulus t4 the resiatance of the real line.
~ Then the current through the resistors R~-R1~ determined by the magnitude of
the cap~citance of the connected capacitor will be almost purely reactive,
and the voltage on these re~istors will be shifted by 90� with respect to
phase relative to the voltage on Tpl. This means that with the correctly
included windings of Tp2, there will be no phase shift vetween the signal _
voltage on R1, R2 and the controlling voltage on Tp2. Then the signs of
the voltage or on the upper end of R1 and the lef t end of the secondary
winding of TP2 will always compare. Then we assume that the current strength
through R1 and R2 from the controlling voltage is greater than from the
signal voltage. Then a DC voltage is formed on R3, R4 with "plus" on the
upper end of Rg. This occurs because if the voltage on the upper end of R1
has a plus sign, the controlling voltage opens the diodes D and D4. The
voltage from R1, R2 is fed through the diodes to R3, R4. I~ at another point
- in time the voltage on the upper end of R1 has a minus sign, then on the left
end of the secondary winding of TP2 there will be a voltagE with the same
sign, and the current from this winding will go through the diodes D2, D3,
opening them and closing the diodes Dl, D4. Since it is stipulated that this
current is greater than the signal current, the signal current passes through
the diode D3 (where these currents flow in opposite direction) without cutoff
and the voltage with the plus sign goes from the lower end of R2 to the upper
end of R3. The indicator j~2 connected to R3, R4 indicates the presence of
the DC voltage. Thus, if the current through the diodes created by the
controlling voltage is suff iciently large, the ring modulator operates as a
two-phase rectif ier.
It is easy to see that if an inductance is connected in place of the line _
and is not a capacitor, the size of the voltages on R1, RZ and the left end
- of the secondary winding of TP2 will not coincide, that is, they will be
180� out of phase. The plus sign will always be on the lower end of R4 in
this case, and the indicator pointer will be deflected on the opposite
direction in the same amount. _
It is obvious that the input impedance of the line is ~urely active, the ~
phase shift on the ring modulator between the signal voltage and the
controlling voltage will 90� (capacitors C1 and C2 are included in the
circuit for this purpose), and the constant component of the voltage on R3,
R4 resistances. The indicator pointer will remain at zero.
For convenience of ineasurement, the type of indicator ~~2 is selected so _
that it will be in the middle of the scale. In this case the total
deflection of the indicator pointer in one direction or another will
correspond to the phase shift between the voltage and current in the line
by +90 or -90� and indicate inductive or capacitive nature of the input
impedance of the line.
207
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. w ~ .
_ e- ~h v ~ ~
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~w ' i ~ ~ O 0 .
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FOR OrFICIAL USE ONLY
a
~
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FOR OFFICIAL USE ONLY
'1't?e measurement ol' the input impedance o~ the ltne is tnade by measuring the
current flowing through the line, with known and previously established
magnitude of the voltage at its input. Since when measuring the phase Zinp ~
of the input a pointing indicator is used with 0 in the middle of the scale,
in order to use the entire scale of the same in~licator to measure Zinp~
the meter circuitry is altered somewhat by compsrison with the usual version.
The difference in DC voltage is proportional to ~.Y~e magr.~tude of the current
_ in the line and the voltage at its input is fed t~ the indicator. The voltage
on the line is constant for all values of its input impedance, and the current
decreases with an increase in ZinP. Therefore the voltage diff erence to _
which the indicator reacts will be equal to zero for some value of Zinp. For
~maller values of ZinP the indicator will basically be affected by the voltage
obtained from the rectifier which is connected through TP2 to the resistances
included in series in the line circuit. With an increase in ZinP the current
in the line decreases, thQ voltage at the output of the rectifier connected
to Tp2 decreases, and then this rectifier is blocked by the voltage formed
on R5 on passage of the current from the second rectif ier connected to the
output of the generator through it.
For monitoring the voltage at the output of the line a voltmetex is
connected which is made up of a microammeter N1, diode bridge and resistor R24,
R25.
[Photo illegible]
Figure 6.9. Outside view of the VIG-3 oscillator
The accuracy of ineasuring the modulus of the resis~ance and phase angle is
no worse than 5%. This high accuracy required separation of the entire
measured range of resistances into two subranges: one from 20 to 100 ohms,
and another from 100 to 1000 ohms. The phase angle is measured within the
209
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limits from -90 to +90� in the entire range. 1'he outside of the instrumen~t
is shown in Fig 6.9.
6.6. Fault Detector (IPTV-1)
_ The detector is designed to determine the locations of short circuits in the
= 1ew and high frequency channels on the overhead and underground f eeder~and _
subscriber lines and also on house distribution cixcuits for monitoring the
' presence of high-frequency programs; in order to find the section of line
with damage causing an increase in xhe crosstalk between channels; in order to
determ.ine the path of damaged underground lines and the location of the
hidden wire in house networks. ~
The instrument makes ~t possible to find the location of short circuits in
the low-frequency channel of overhead lines from the ground, and in the
absence of the interfering effect of the electrical network current f ield on
the overhead lines running above the roofs of three to seven story buildings.
A short circuit beyond the limiting net resistance with respect to any ef the
three channels in the room wires using double lines, for example, TRVK, can
. be found with the search coil of the detector at a distance on the order of
, 5 to 10 cm from the wire, and up to the limiting resistance on the house
network stands at a distance of 50 cm or more. -
The operating principle of the instrument is based on the fact that the
electromagnetic field of the current of the RT network is picked up by the
- search coil, it is amplified and fed to a hea~set. The structural diagram
of the detector is shown in Fig 6.10. The search coil has three windings:
low frequency and two high frequency tnade in such a way that the inductive ~
coupling ~ccurs only between the high frequency windings. Depending on the
position of the channel switch either the low-frequency winding of the search
coil is connected to the amplif ier input Qr the output of the two-circuit
concentrated selection filter tuned to 78 and 120 kilohertz is connected.
On setting the switch to the low-frequency position all of the stages of the
detector operate in the amplification mode. When receiving high-frequency
signals and setting the switch to the 78 or 120 kilohertz position the last
stage performs the functions of a detector, and all the rest, the high-
frequency amplifier.
�I a.~ ~ '
j ~ ~~NV ~l~ . .
I
, ,1a D
~
~ ~ . r
~
~ ~
; Bxoa~~~ . ~
; ~.--o ~
. _
Figure 6.10. Fault detector IPTV-1
Key: 1-- low fre~uency; 2-- input -
210
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Tt~e input ~jacks are used to feed the programs of the high-frequency channels
to the input of the amplifier through the coupling winding of the search
coil. Tlie principle of determination of the short circuit location is based
on the Eact that the magnitude of the carrier in the wires at this point
clianges sharply. If to the left of the short circuit point the current ha~
' significant magnitude exceeding the opetating value of the current, then to
ttie right of this point the current in the line decreases in practice to 0.
When working with the detector this is manifested in the sharp change in
strength of the sound on advancement of the search coil along the line past
the short circuit point. The short r..ircuit on the line causes different
consequences for the sound frequency currents and the carriers of the high-
freqsency channels. On the sound :Erequencies the current increases by compar-
ison with the operating value over the entire section to the left of the
short circuit point. On the frequencies of the high-frequency channels in
the presence of a short circuit as a result of reflection of energy in this
segment, standing current and voltage waves occur before the short circuit
point. In some sections in the presence of a short circuit the current can
diminish by comparison with the operating value of the current at the same
time as in other sections it increases. However, on any channel there is
discontinuous variation of the current at the short circuit point, that is,
variation in volume of the sound in the detector headphone.
Tlle detector has the following qual.ity indexes: a sensitivity of 40 micro-
amps wi.tk~ inductive coupling through the search coil at rated output voltage; _
An output voltage of 1 volt developed in the :ieadphones with a resistance
- of 3000 to 4500 ohms;
. A reproducible frequency band with resr~ct to the high-frequency channels
_ of 300-3500 hertz for nonuniformity of 15 decibels;
Coeff icient of nonlinear distortions on the high-frequency channels of 7%. -
The detector has two sensitivity adjustments: step by 40 decibels and
continuous by 30 decibels. The instrument f eed is from 3 of the 1, 3FMTs-0.25
type elements.
When building over overhead and cable lines, house RT circuits and also ~
when detecting faults it is expedient to use the IPRL type detector which
- is made up of the IPRL-I �ault detector itself and the oscillator G. The
locat~.on of the break or short circuit is fixed by a sharp change in volume
of the sound in the headphones of the detector beyond the location of the
break or short circuit.
The detector detects the location of the following fault:
On pole subscriber lines at 15 and 30 volts with accuracy ef +10 meters
when it is at a distance of no more than 6 meters from the path of the line
and at an admissible noise level from the electric network;
211
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Pole and stand distributing feeders suspended at a height of. up to 20 metere
with prc~c~ston oF +20 meters when the detector is at a distance of no more
ll~aii l.t) mc~ter~ fr~~m thc p~i~h of the ].ine;
House wiring laid open or hidden. The precision in this case is +8 cm when _
_ the detector is at a distance of no more than 1 cm from the wall;
In secti4ns of underground f eeder lines laid using cable with nonmetallic
shielding with precision to 1 meter.
The qcality indexes of the detector are as follows: a voltage of 100 milli-
volts on the TON-2 headphones, fxequency band of 700 to 1400 hertz with
non~iniformity of 6 decibels, coefficisnt of nonlinear distortions of 10%
with an output volta~e of 0.5 volts; the detector has step adjustment of the
amplif ication 20 decibels deep and the continuous 18 decibels deep, and the
detector oscillator frequency is 1000 hextz.
6.7. ITPV-2 Type Triple-Program Wire Broadcast Pulse Meter
The portable ITPV-2 instrument [29] is designed to determine the quasimaximum
values of the voltages of broadcast programs on the wire broadcast networks.
' Ttie program can be heard on headphones. By using the instrument it is also
possible to measure the magnitudes of the sinusoidal voltages at frequencies
of 78 and 120 kilohertz and low fr equency in the range of 50 to 10000 hertz.
The structvral diagram of the instrument is presented in Fig 6.11. At the
input of tt~e W, two symmetrizing transformers are installed for low and
high frequencies with different transformation coefficients, which permits -
the signals of the three programs to be reduced approximately to the same
level at the input of the voltage divider (DH). Band f ilters ~78 and ~120
are included at its output for the cr rier frequencies (the low-frequency
filters pertain to the input circuit). From the f ilter output, and when
measuring low-frequencies �rom the output of the divid er the measured voltage
goes to the input of the wide band amplifier (ShU) which passes a 50-hertz
to 200 kilohertz band. The amplif ier ioad is two detectors. The first is
- the pulse meter detector (DI), and the second detects the AM oscillations
of programs II and III. From the output of the second detector the sound
_ monitoring detector (DZK~ and when listening to a low-frequency program
from the output of the wide band amplifier, the low-frequency voltage goes
to the low-frequency amplif ier which insures a level sufficient for normal
operation of the hea~phones (T). The detector of the pulse meter is loaded
_ on the measuring bridge (IM) with a microammeter, the scale of which is
calibrated in volts. In the absence of a signal the bridge is balanoed and
- the pointer of the instrument is at zero. When a signal arrives, the
balance is upset and the pointer is deflected proportionally to the maximum
value of the voltage.
_ 212
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_ FOR OFFICIAL USE ONLY
~.5~_~~~ ~ -
r-~--~---------r-- ~ T
~
- ~
~ ~~an ; 3~r p yHV .
1
_ ~
- drea B9 ,qy ~q m~B G'19 JjJI //,N
, (1) ~3~ 4) ll.,..._..J ~6~
~ 6
. - � . 9B (10)
Figure 6.11. ITP-2 pulse meter
I~ey : ~
1. Input 6. ShU
2. P1 7. Low-frequency amplifier
3. low frequency 3. DI _
4. DH g. IM
5. DZK 10. B, 9 volts
The limits of ineasuring the voltage of program I are as follows: 10, 30,
100 and 3.00 volts; the ttigh-frequency programs: 0.5, 1.5, S, 15 and 50 volts.
'The measurement error does not exceed +5% (on the 50 volt scale the error is
+7%). The input impedance of the instrument in the frequency band of 50 to
_ 10000 hertz is 12 kilohms; for the high-frequency channels with a pass band
ot every 10 kilohertz, 3 kilohms.
The crosstalk between the high-frequency channels is -36 decibels. Th~ noise
- protection of the high-frequency channel from the low-frequency signal is
70 decibels. The integration time when feeding the low-frequency signal to
the input is 30 milliseconds with 85% f idelity, and when f eeding the high-
frequency carriers modulated by a frequency of 1000 hertz to the input with
~ m=70% the integration time is 50 milliseconds with 80% f idelit~.
The power supply for the instrument is from a 9 volt battery;~the intake
current is 10 milliamps. In combination with the PZK-1 type sound monitoring
attachment which has an amplifier, speaker and battery, the ITPV-2 permits
loudspeaker sound monitoring of broadcast programs. The outside of the
instrument is shown in Fig 6.12.
6.8. Monitoring Receiver (KPU)
The KPU [mor~itoring receiver] is the highest quality instrument designed to
measure the qualitative and technical indexes of the low-frequency and high-
frequency channels of the system and permitting measurements of the normalized
parameters with respect to quality class I.
In order to perform all of the required measurements the instrument has two
operating modes: in one mode it performs the functions of the high-quality
monitoring receiver of AM signals, and in the other, it is a three-band, -
multilimit selectivP millivolt meter with symmetric input.
213 -
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[Photo illegibleJ
Figure 6.12. Outside of the ITPV-2 pulse meter
Eeginning with ehe problems of ineasuring all of the quality indexes the KPU
, contains the following assemblies: the amplifying channel of the receiver,
attenuator, low-frequency and high-frequency filters for various purposes
(including filters for separate measurement of background and noise), the
symmetrizing low-frequency and high-frequency devices, the amplifying channel -
of the voltmeter and the sound monitoring, the switching devices and power
supply.
In order to perform the set of ineasurements crosstal~c, noise, background,
frequency characteristics with respect to the envelope in the modulating
- frequency range and in the high-frequency and low-frequency cha~.inel bands
the following instruments and devices are required: symmetrizing transformers,
lineman's indicator, the Kazakhstan receiver, the GT Avrora, the tube volt-
meter, cathode repeater and filters for separate measurement of background
and noise.
Al1 of these devices are replaced by one KPU instrument, the structural
diagram of which is presented in Fig 6.13. The input circuits of the KPU
are made up of the SU-VCh high frequency and SU-NCh low frequency symmetrizers,
the AT1 attenuator and the PF78 and PF120 band filters,
The SU symmetrizers make it possible to obtain symmetrizing input of the
instrument and, in addition, the SU-VCh has additional selectivity with
respect to the signals of the low-frequency channel. In order to insure the
possibility of ineasuring voltages in a wide range from 0.25 to 300 volts,
an 8-step attenuator with attenua.tion in the limits from 0 to 80 decibels is
used.
214
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Each band f ilter has a noiseproofness of 60 decibels wbetween the high-
frequency channels. When measuring the low-frequency channel the required
noiseproofness (30 decibels) from the high-frequency channels is insured
by the FNChl low-frequency f ilter. When measuring the background level, the _
FNCh2 low-frequency filter is included which cuts off the frequencies above
200 hertz and has attenuation in the 200-1000 hertz band equal to 22 decibels. -
In order to measure the noise level, the high-frequency filter is included
in the circuit which cuts off frequencies below 200 hertz having attenuation
of 21 decibels in the frequency band of 50-100 hertz. -
The high-frequency amplifier is four stage. It is used to amplify the
signal to the amount suff icient for linear detection. As a result of the
application of negative feedback in the f irst two stages the high-frequency
amplifier has high input impedance required for norma.l operation of the
band filters.
The double halfperiod detector insures high linearity of loading the high-
frequency amplifier and improves the suppression of the remains of the carrier
frequencies and their harmonics.
" The low-frequency amplif ier is single-stage. Its load is the FNCh3 low-
frequency filter. The UNCh2 low-frequency amplif ier is three-stage with
~ommon amplification coeff icient of about 140. It amplifies the voltage to
- the rated output value of 0.775 volts. It has low output impedance and is _
loaded on the attenuator AT2 of the level indicator.
The voltmeter amplifier W is four-stage, wide-band. It has a total amplifi-
cation coeff icient of about 1000. The rectification circuit is a bridge ~
circuit. A microammeter for 100 microamps, type M265, is connected to one
of the diagonals of the bridge. Part of the voltage of the UV voltmeter
amplifier is fed to the monitoring amplifier UNChk which is made of 5
transistors and is loaded on the 1GV-1 speaker for listening to programs and
interf erence.
The power supply for the KPU can either be from KVS type batteries placed in
the instrument case or from the AC network. The power pack is made up of
the step-down power transformer, filter rec�3fier and voltage stabilizer.
The IP indicator monitors the inclusion of the instrument and the magnitude
. of the feed voltage. In order to include the instrument there is a flipflop
switch 8B1 Pitaniye [feed]; for switching power supplies there is a toggle
switch 8B2 Rod Pitaniya [type of feed]. The current intake by the instrument
when powered from the battery is 55 milliamps. The power intake from the
- AC network is 4 volt-amperes.
215
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~ r._..__~_~'____j-_~~~:..:...:~ - .
~ ~ ~ (lo)~
~ ,
~1) ~ i wru ~ �'95-u1 ya"V . .
_ `k.r. t 1 ~ ~~v 1 t' tl ' V 8 ~,i;
~ f~ ' I 1i l0 L
- '"'r""j; , ~o a ~?t~ p~a-73 6 ~ ~ .
~~l~ ~ t-8/B Yz~~ ~ .
y, _ ~ "
_ .1 � ~ ~
. 1 ,
A'UN0~1 ~ _ ' ~ .
(2) ` ~ ~ _ , .
, 9-~~, ~e~ti nn. . ~ ! 16 5-~ _ . -
S-e1 ~ ~ 9 I I , ~ ~ r0 .
o~ Is ~ s ~ 1 9~ ~
1~ I~ ~ y ~ ~ .
~ ~ 1
Pc~~~l ~e ~ . ~ ~ 1 j : . . ,
Od~nms~ f Yo ! ~8y j , 1 I .
~3 ~ ~ ~ansm~0 ~ 1 ~ j "
~ ' ~ ~ ~4~ ~-----+----+~---Z--~----~------ -
' - -
. . ~ .
. . ' _ . . ' i �
1 ~ ~ . ' ' . . ~ . , y .
~ /lam~i~e I~, Pcd ~um~n~ ~6~ - ~
. Z . . . .
~ ~l 6ao~r num~arua ~ ~ . . . .
~ . B-B1~ 'v~ ~~~16~ _ . .
~1 1 A
, cs~ . ~ : I~ . :
.
L--- B-Bl N11 . . . ~ .
- ' ~ . ' . . ~
Figure 6.13. I~Ieasuring rece~iver KPI3
Key:
1. Input
2. Channel
3. Type ~f operation
- 4. Filter~s ~
5. Power supply
~ 6. Type of feed
7. Power supply module
8. 220 volts
9. 135 volts
10. High-frequency amplifier
11. Calibration
216
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_ � � . 12 � 13
s~ry, D~ ee,x~~ (14)
~ i~' '
~ � ~ q
? . . . -
S?B
6 ~ ~ ~ t. E ~ �
' ,s : e' i;3 ' ? . N/l-1 : . . ~ � .
t i?~ A ~ .
, ~0~'15~ a B . ~ ~ ~ . . ' ' ~ . .
- ~ . . ~~~i
~ K, rpc~?xocmE (16) . - ~ . .
_ . % ~ . . , .
. ~~~r~... ~ ~J ~ .
i
~ ' ~x ~P .
' . _ ~i .s .
[Fi~ure 6.13]
12. Low-frequency filter
13. Low-frequency amplifier
14. Output
- 15. Calibration
16. Volume
- 217
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For separate ~xplanation of the operation of the instrument let us consider
two operating modes separately: 1-- Vol'tmetr [voltmeterJ and 2-- Priyemnoye
ustroystvo [receiver]. In the first operating mode the KPU makes it possible
to measure the eff ective values of the AC voltage of all channels from
10 millivolts to 300 volts in the frequency bands from 50 to 10000 hertz,
68-88 and 110-130 kilohertz; the effective values of the carrier voltages
of channels II and III in the presence of tone modulation or modulation by -
tiie broadcast signal with the carrier level ad~ustment included on the trans-
mitters; the modulus of the input impedance for frequencies of all channels.
In addition, in this mode the KPU permits the performance of the following:
separate measurement of the background and noise voltages of the low-frequency
channel to 75 decibels; measurement of the frequency characteristic in the
band of each channel, listening to the broadcast program of the low-frequency
channel.
The Ka.nal [channel] switch is used to select one of three channels. The
instrument has the following voltage scale: 30, 100 and 300 millivolts;
1, 3, 10, 30, 100 and 300 volts. The measurement error is no more than +6~;
the nonuniformity of the frequency characteristic is 2 decibels.
When measuring the voltages the low-frequency signal goes to the low-frequency
symmetrizers SU-NCh, from the output of which the voltage is fed through the
attenuator AT1, the groups 5-V1V of the type of operation switch, the FNChl
low-frequeno.y filter, the KK correction circuit, the S-V1V type of operation
switch group, the 2V1V channel switch group, the SVla and 5-Vlb groups to the
input of the W voltmeter amplifier and then to the rectification circuit of
the IP1 microammeter, type M265, calibrated in millivolts (volts).
When measuring the voltages of the high-frequency channels the signal goes
to the input of the SU-VCh device, then to the attenuator and to the correspond-
ing f ilter which insures the required selectivity. From the output of the
filter the measured voltage goes through the 5-Vla and 5-Vlb groups to the
UV and the instrument.
In the second operating mode the~instrument makes it possible to measure
the following quality indexes with respect to quality class I and II: the
frequency characteristic, inter.ference protection of the high-frequency
channels, background and noise voltage, and by means of the nonlinear distor-
tion meter, the harmonic coefficient. In this mode with a sensitivity of
the instrument of 25 millivolts the output voltage is 0.775v. The voltmeter
has 6 scales: from 0 to 3, 10, 30, 100, 300 and 1000 millivolts. Its basic
error is +6%. The nonuniformity of the frequency characteristic of the
instrument is 2 decibels, the harmonic coefficient is 0.5%. The noiseproof-
ness between thp high-frequency channels is 77 decibels, from the low-
frequency program 105 decibels, from the radio broadcast band on frequencies .
- above 180 kilohertz, 70 decibels.
218
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The signal to be measured goes by means of the 2-V1 channel switch "78"
or "120" to the input of the high-frequency sysumetrizer SU-VCh and then to
the AT1 attenuator and the PF 78 or PF120 band filter. Then the signal is
amplified using the WCh high-frequency amplifier, it is detected and again
amplified with respect to low frequency (UNChl). The setting of the required
sensitivity (calibration) is made by ad,justing AT1 (rough) and variation of
the amplification coeffScient UVCh (smoothly). Here the IP1 instrument is =
connected by means of the switch B2 to the output stage of the high-frequency
amplifier.
From the output of the UNChl low-frequency amplifier the signal goes through -
the FNCh3 low-frequency filter.s, the 5-V1 switch group and the FNChl low- _
frequency f ilter, the KK circuit, the 5-V1 group to the UNCh2 low-frequency
amplifier connected to the "output" terminals. The voltage at the output
of the KPU is measured by a built-in voltmeter which is made up of the
attenuator AT2, the K-circuits (K1 and K2), the rectifier B and the instru-
ment calibrated in decibels.
Depending on the type of ineasured parameter the "filters" switch is set to
the required position and the following measurements are made:
- 1. In the ShP position measurement of the harmonic coefficient of the
~ amplitude of the modulated oscillation of the high-frequency channels and
- pickup of the frequency cha.racteristics with respect to the envelope. In
' this case the KK is included and the pass band of the receiver is 50-10000
hertz. In order to measure the harmonic coefficient, the harmonic analyzer
or coefficient of nonlinear distortion meter is connected ta the output
terminals.
2. In the "background" position measurement of the background voltage of
the high-frequency channels. In this case the FNCh2 filter is included,
and the pass band is limited to frequencies of 50-100 hertz.
- 3. In the "noise" position measurement of the high-frequency channel
noise. In this case the FVCh high-frequency filter is included, and the
band is 400-10000 hertz.
4. In positions 1 and 2 kilohertz the measurement of the croSStalk in
each high-frequency channel. In this case the narrow band f ilters K1 and K2
are included respectively, and only the voltages at frequencies of 1 and
2 kilohertz are measured. The presence of noise interfering with the _
- measurement is determined by using the acoustic monitoring channel in the
"loud" position of the volume switch. The outside of the instrument is
shown in Fig 6.14.
, 219
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[Fhoto illegible]
Figure 6.14. Outside of the KPU
6.9. Channel Monitoring Device (UKT)
The UKT channel monitoring device is a portable instrument which can be used
for checking and tuning the channels of the TPV network, to check the
fitness of the GT at the subscribers and the GPTV. The 1000-hertz oscillator
in the UKT can be connected to the UPT~I-200 transmitter and it is possible
to check the correctness of the regulation in it of the suppression of the
carrier and depth of modulation. Rigid requirements are imposed on the
portable device with respect to weight and economy when fed from a battery.
Therefore the UKT circuit is appreciably simpler than, for example, the VIG-3
. oscillator, but the simplif ications are achieved at the expense of some loss
of precision and stability of the instrument.
The structural diagram of the UKT [35] is presented in Fi~ 6.15. The device
is made up of the master oscillator (ZG), the low-frequency 1000-hertz
oscillator (GNCh), the power amplifier (UM), multivibrator (MV), the meter
that measures the modulus of the input impedance on carrier frequencies, the
Z-meter, rectifier, and stabilizer of the DC f eed voltage. The oscillation
_ frequency of the master oscillator ZG (&8 or 120 kilohertz) can be switched
both manually and automatically using the MV multivibrator. The multivibrator
controls the relay which, in turn, connects (or disconnects) the capacitors -
to the oscillatory circuits of the ZG and UM. The frequency is switched
every 6 to 9 seconds. This time is entirely sufficient to measure the
level on the line using the lineman's indic~3tor.
The amplitude modulation of the carrier frequencies is realized directly in
the master oscillator itself without an additional modulator by feeding a _
voltage from the output of the GNCh low-frequency oscillator to the emitter
circuit of the transistor. The AM mode is used to check, without meas+iring
~ the quality indexes, f itness of the GT and GPTV. The voltage of the GNCh
220
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can be used also for other purposes. For example, on connecting its output
to the transmitter it is possible to check and adjust the depth of modulation,
the degree of suppression of the carrier. The modulus of the input impedance
of the feeders is measured in the usual way: a current or defined magnitude
(calibration) is fed to the line, and then the voltage drop on the Zinp line
is measured. The two-limit scale of the meter is calibrated directly 3n ohms
from 0 to 100 and from 100 to 1000 ohms. In the UKT, the M24 microammeter
for 100 microamps is used. The device is connected to the line in parallel,
but so tha~ the band-elimination filters ZFR separate the UKT from the low-
frequency station amplifiers.
~9) ~8
~ 3r y~ Da~xod oy
rt /1M
~5) ~6) ~7) ~
/'yy M6 Z-,~ '
_ e~,Xaa yy ~4~ . .
~208 B ~ t 188
' ~ 2 ~ BNtul~tua `l~ ~3 ~ _
ucmowyuK .
Figure 6.15. Device for monitoring channels -
Key:
1. Outside power supply 6. MV
2. 220 volts 7. Z-meter
3. 18 volts 8. High-frequency and AM output
4. Low-frequency output 9. UM power amplifier
5. GNCh 10. ZG master oscillator
The parameters of the device are as follows: the o.utput power on the carrier
frequencies on a resistance of 300 ohms is 1 watt; the voltage of the GNCh
is 2 volts, the hig~-frequency on a load of 1500 ohms is 2 volts. The
operating frequencies are as follows: 78 and 120 kilohertz with precision
of +1.5%, 1 kilohertz +20%. The continuous adjustment of the high-frequency
signal level is no less than 20 decibels. The measurements of the modulus
of the input impedance of the RF distributing feeder on carrier frequencies
are within the limits of 10-1000 ohms+l5%.
The instrument is powered from the AC, 220 volt network or 3 to 4 KBS
batteries with a voltage of no more than 18 volts.
6.10. Test Signal Pickup (G-78/120)
In order to tune the individual and group receivers and intermediate amplif iers,
- a special AM oscillator is required with higher quality indexes. The
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_ G-78/120 pickup is a source of AM signais made up of two independent
carrier frequency oscillators identical with respect to circuitry and a
common power pack. The structural diagram of the sensor is shown in Fig 6.16.
The amplitude modulation of the carrier frequencies can be realized either
by an external low-frequency oscillator or internal with modulation fre-
_ quencies of 1000 hertz and rated modulation depth of 70~. Each oscillator _
is made up of the master oscillator with quartz stabilization of the frequency
and a modulator executed by the circuitry of the two-cycle amplifying stage
with modulation in the emitter circuit. At the output the oscillator has -
a continuous amplification regulator which provides for regulation of the
output voltage within the limits oi 15 decibels and a step voltage regulation
switch for 0.1, 0.3, 1.0 and 3.0 volts (for the DPU). The power supply for
the pickup is from the 220 volt AC network. This volt~ge is rectified and
stabilized with respect to the DC voltage by a parametric stabilizer. As the
source of the low-frequency signals it is possible to use any sound frequency
oscillator with output impedance of 600 ohms. The basic parameters of the -
pickup are as follows: modulating frequency band 20 to 15000 hertz with non- -
uniformity on the higher frequency of 3 decibels, harmonic coefficient of
0.5% in the 20-6000 hertz band, background level 65 decibels, signal/noise
ratio with mutual connection of the outputs of the two oscillators to the
common load of 70 decibels, power intake from the network 3.5 watts, mass
of the instrument 2.5 kg. ~
- ~1~ ~B~ ~2~ Aloayn. Oy OscmD ~3~
' 4 ` .
~ B,v!~ir,/;~~JrN,~A d~t6/,CG~.9lJUA/ .
� w~~~�:;anuA Hv dxe9 (8)
_ ln~r~ Bod
AyuA rrcuw. ~rc-yux~6~ Gxn~ (8)
_ . ~4~ I~ayuta~r~5~ : ~
l20KPy Mods,n. OqOe~roD~10)
~ ~ ' . ' ---ir.;~' .
. t
- ~ ~ � ~ � ~(i yum~Qa G~Rb (12)
. ~ .
.
Figure 6.16. Test signal pickup
Key:
1. Low-frequency oscillator 78 kilohertz 8. Low-frequency input
2. Modulator 9. Low-frequency oscillator
3. High-frequency output 120 kilohertz '
4. Internal modulation 10. High-frequency output
5. Carrier 11. Power supply
6. External modulation 12. Electrical network
7. 1 kilohertz oscillator
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6.11. Measurement Panel of the Distributing Feeder k~ame (PI-STR)
The measurement panel is built into the STR-5 distributir~g feeder frame
installed on tr~3nsformer subgtations for remote control and monitoring of
tl~e operaClon c,f tl~e trnnHf.ormer aubstationa af large citie9 with triple-
" program wire broadcasting. The measurement panel provides for the following:
measurement of the signal level of all three programs, measurement of the
modulus of the input impedance of each feeder (to 10) on the signal frequencies
of the three programs, measurement of the quasipeak value ef the envelope
of the modulated signal of the second and third programs.
All of the measurements are performed without interrupting broadcasting over
the distributing feeders. The levels are measured simultaneously with
respect to three programs. This is achieved as a result of daing away with
- the pointing indicators and using a cathode ray tube as the indicator.
Another characteristic ot the PI-STR panel is the fact that thE modulus of
the input impedance of the feeder is measured not by using special oscillators,
but on the broadcast transmission currents of the low-frequency programs and
the carrier frequen.cies of the second and third programs. The structural
diagram of the panel when measuring the program levels is presented in Fig 6.17.
The voltage from the STR-5 buses goes to the input device which insures the
possibility of connecting three filters to the buses: low frequency trans-
mitting the signal of I and two band filters at 78 and 120 kilohertz. The
voltage from the output of the filters goes through the preset regulators to
the integrators (IU). Their purpose is to insure measurement of the level
- by the procedure established by MRTU-1029-66 specif ications. According to
_ this procedure the integration ti.me (the minimum sigtnl duration, the level
of which is reckoned with 90%+10% fidelity) is equal to 10 milliseconds,
and the capacitive discharge time is from 3 to 4 seconds. The integrator
- satisfies these requirements. It includes two amplif ication stages (emitter
repeaters), detector and integrating circuit. All th�ree devices are identical.
- From the output of the integrator the voltage goes through an electron switch
to the vertical deflection amplif ier (WO) but only in the case where the
switch is not closed. The switches are controlled by an electronic commutator
and pass the signal from the IU [integrator] alternately. The switching speed
is 100 times per second (twice the electrical network voltage frequency).
The UVO [vertical deflection amplifier] amplifies the signals arriving from
any IU and transmit them to the vertical deflection plates of the cathode ray
_ tube beam. With respect to horizontal the beam is deflected by pulses
obtained from the same electronic commutator which controls the switches.
The deflection (scanning) is realized so that if the first program switch is
opened, the bea.m is not deflected, but remains on the left side of the screen.
When the second switch is opened (the f irst one is blocked), the beam deflect~
jumpwise to the middle of the screen, and on blocking the third switch, farther -
than the middle. In addition to the pulses, an AC voltage (from the network)
is fed to the horizontal deflection plates, deflecting the beam so that
instead of points from the beam on the screen dashes 5 to 10 mm long appear.
This facilitates reading and increases the service life of the cathode ray
tube. A transparent mask is fitted to the cathode ray tube screen with three
223
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scales plotted on it calibrated in effective volts. By these scales and
~ tl~e m~ximum beam deflection the program levele on the STR-5 buaea are reckon,ed.
Wlien the electronic switches operate the transient processes influencing the
degree of deflection of the beam occur. These spurious beam deflections can
be per~eived by an observer as a variation in the signal voltage. However,
even if the observer, knowing the origin of this interference, doea not ,
notice them, they still complicate proper reading of the level with reapect
to the beam position. In order to facilitate reading, the beam is ext~n-
guished during the switching time of the measured channels. In order to
extinguish the beam pulses are fed to the modulator of the cathode ray tube.
These pulses are obtained ~in the electronic commutator. The integrators,
electronic switches and commutator are made of transistors, and the vertical
deflection amplifier ls made from the 6N2P tube (the magnitude of the voltage
required for the beam deflection reaches 200 volts, and industry still does
not produce the corresponding transistor).
~3) . ~
trr~l Nyl ~n, Rp 9A'1'~14)
~r ~R
4 : ~ ~ : ~r;J ' s Hy~l lfn, y80 _
Fr, , j
, ~1~ ~ ~13)
~11:1 ~ f!'/~ /f/I~ .
o .
. ��~12~ ,~/!Z/l~lpD.NH611L . . _
. aoM,~y~ramop
`
Figure 6.17. Structural diagram when measuring program levels -
Key :
1. STR-5 buses 11. Switch 3
2. Input unit 12. Electronic commutator _
3. Low-frequency f ilter 13. WO [vertical deflection amplifier]
4. Band filter 78 kilohertz 14. Cathode ray tube
5. Band filter 120 kilohertz
6. Integrator I
7. Integrator II
8. Integrator III -
9. Switch 1 ~
10. Switch 2 _
The structural diagram of the PI-STR when measuring the quasipeak values of
the envelope of the modulated signal is presented in Fig 6.18. In contrast ~
to measuring the signal levels, the measurement of the level of the
envelope is made not simultaneously with respect to two (II and III) programs,
but in turn. The program is selected manually by the switch B. The
electronic commutator does not operate in this case, and the magnitude of
the corresponding DC voltage deflecting the beam horizontally is established
by the variation in position of the switch B. The high-frequency voltage \
from the STR-5 buses goes through the input de�~ice, the 78 and 120 kilohertz
filters and the switch B to the input of the amplitude detector. At the
224
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output of the detector a low-frequency voltage is obtained, that is, the
same envelope, the voltage of which must be measured. Then the low-frequency
volt~igc i~ fed to the integrator, And from its output thew puleating
voltage is fed to the vertical deflection amplifier and then to the deflect-
ing plates.
" , . _ - ,
(2)
�'-'d R~ ~ B ~4~ 5) ~b) '~7) R .
Z ~J Hy se9 /Y
~~ae �
Rs ,p . .
, ~1~ ~3~ - . , .
Figure 6.18. Structural diagram of ineasuring the envelope level
Key:
1. Input device 5. Detector
2. F-78 band f ilter 6. Integrator
3. F-120 band filter 7. Vertical deflection amplifier
4. Switch
. - r0~ 1 1 B B,x,: ~ Br
. ~ ~f ~
- B~ 1 ' 1 ~i .C" t I/ , ~ 1'r ' -0~ N ~ (lo)
� i ? ~ ~~'3 ll.r. d; ~r~ 7::. ~ ,rA,
. ~ i ; ~ ~ i 12~
~ . yv9
, ~ rOt t 1 I B>r';: IR A;]~ -
~ Ama G ~ g''- � ~~.b,~,' ~ . . ~l, ~1
E, 11. ll~ I ~ Z,s~ , ~,.;�i~ i~p~
a ~ rr7.'.'~ ~ I~ 1
1
�:c~
z- ~ ~ ~3i ~ i ~ ~ d i ~
~1~ � m ~r~ ~r'!~'' ~ ?-i-----J--i-----J
~ ~ 'y-~P i~5)
~3~ t s ~0~,. ~,V,-:
. f , L_~ ~
nua N
. , . ~6~
Figure 6.19. Structural diagram of monitoring the constancy of
the input resistance modules of the feeder lines
Key:
1. Measuring f eeder 10. Integrator
2. Measuring transformer 11. Switch
3. Resistance box 12. WO vertical deflection -
4. Att amplifier -
5. From the shaper
6. Electronic commutator
7. PFNCh low-frequency band filter
8. 78 kilohertz band f ilter
9. 120 kilohertz band f iler
225
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The modulus of the input impedance of the feeders is measured by the structural
diagram in Fig 6.19. In this caee the voltage goes to the feeder from the
buses of the transformer substation through the measuring transformer and
the resistor R1. A circuit made up of the resistor R2 and the resistance
box is connected in parallel to the autput of the measuring transformer.
The magnitude of the'resistance R2 is 20 times that of R1. If the resistance
is set on the resistance box so that the drops on both resistors will be
identical, this means that the resistance of the box is 20 times greater than
the input impedance of the feeder. Thus, in order to measure the modulus of
the input impedance it is necessary, awitching the resistances of the box, to
equalize the voltage drops on R1 and R2 and reckon ZinP of the feeder by the
box scales (a difference of 20 times is considered during calibration).
The voltages are measured on the resistors just as the program levels are
- measured. The voltage is~fed through the switches and the transformer to the
filters which pass the currents of the program, on the frequency of which the
measurements are made. On the programs II and III, measurement is made an
carrier frequencies, and on program I, in the frequency band of 400 to 800
hertz. Although the operating rules require performance of the measurements
of Zinp only on a frequency of 400 hertz, if the filter band of program I is
made very narrow, the voltage at the filter output will be small, and the
greater part of the time it will not exist at all, for the voltage components
with a frequency of 4-0 hertz in the spectrum of the broadcast program occur
rarely. Therefore in order to facilitate the measurements the filter band is
made relatively wide.
From the f ilter output the voltage goes to the integrator, and then through
the electronic switch and the vertical deflection amplifier, to the cathode
ray tube plates. The electronic commutator alternately includes the switches
and simultaneously shifts the beam horizontally. In this case two strips -
will be obvious on the screen of the eathode ray tube which move vertically
in accordance with the broadcast transmission level. Turning the switch of
the resistance box, it is necessary to set it to the position in which both
strips will be at the same height, and then read the modulus of the input ~
resistance of the feeder by the box scale.
The PI-STR is a highly accurate instrument; its error in the mode of -
simultaneous monitoring of the dynamic levels of all three programs does not
- exceed +10%, and the additional error as a result of the presence of the
voltage of additional programs does not exceed +4%. The values of the moduli
of the input resistances can be measured with an accuracy of +10% in the
range from 160 to 1000 ohms and with an accuracy of +10 ohms in the range
from 30 to 100 ohms.
The structural design of the PI-STR provides for the installation of the
panel on the STR-5 frame without any adjustments. If the modules for monitor-
ing the programs, measuring the input impedance and the pulse meter are -
installed in advance on the frame, it is necessary to remove them and
install the PI-STR panel in their place. The panel f eed is from the STR-5
feed module, but since the cathode ray tube and the transistorized stages
226
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require additional rated values of the stabilized voltage, an additional
feed module is installed on the PI-STR.
6.12. Problems of Introducing Meters
The above-enumerated instruments do not completely correspond at the present
time to the operating needs. One of the main peculiarities of the triple-
program wire broadcasting is the use of a variable carrier. This factor
gives rise to signif icant difficulties in measuring the voltage distribution
on tlie wire broadcast networks. The instruments used quite precisely measure
the voltage if the carrier is tone modulated, that is, when the carrier
remains constant. The tone line measurement can be made when the TPV net-
works in the given region have only just been created. However, when the
network has already begun to operate, it is inadmissible to carry out the
current tone measurements for entirely understandable causes (preventive,
operational or operative). It is possible to say the same thing about the
measurements when searching for damage and determining the degree of influence
on the voltage distribution along the f eeder of the newly connected leads.
The readings of the voltmeters the lineman's indicator and RTPV-2
essentially depend on the nature of the broadcast transmission (voice, music),
and they can lead to invalid conclusions. This leads to the necessity for
making individual measurements. The creation of an instrument, the readings
of w!Zich will not depend on the level and nature of the broadcast program
appears to be difficult. Therefore it is more expedient periodically to
change the operating conditions of the transmitter: to convert it for some
. time to operating conditions with nonregulatable carrier. Then during this
time the carrier will be constant, and by the readings of the instrument
reacting to the existing voltages it is possible quite precisely to d etermine
the transmissian coeff icient of the various elements and the level distribu-
tion on the network. The disconnection of the carrier regulation, however,
is connected with an increase by 20 decibels of the crosstalk interference
on ttie high-frequency channels from program I which can turn out to be
noticeable for the subscribers. The noticeability of the crosstalk can be
reduced to the minimum by reducing the time during which the~transmitter con-
ditions change. It is obvious that this variation must be of a periodic
(pulse) nature. The pulse duration, the buildup and decay fronts, the
repetition periodic ity are to be determined by theoreticaly and experimental
work. . It is also necessary to develop and install the corresponding auto-
matic devices in the transmitters that have already been produced and newly
developed.
There is a theoretical possibility of determining the transmission coefficient
of the lines and the devices by measuring not the maximum values of the
signal, but the residue of the carrier frequency voltage in the intervals
(it does not depend on the level of the broadcast programs). This measurement
procedure does not require introduction of an automatic device into the ;
transmitter, periodic disconnection of the regulatianof the carrier, and
it does not lead to .an increas~ in the crosstalk interference.
227 '
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i
~
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At the present time the problems connected with the development of the AM
signal generator to measure the high quality indexes of the individual
channels and the TPV devices have been basically solved. There is a necessit,y
for oscillators vf three types:
a) High quality (standard) oscillatorsfor checking the KPU;
b) Oscillators required to organize the production of the receivers and
amplif iers; -
- Oscillators designed to check out the fitness and simple repair of the
receivers and the DPU at the point of their installation. These instruments
have been developed.
The first type includes the modulated attachment, the second type includes
the generator and the test signal sensor and the third type, the device for
monitoring the UKT channels.
The KPU monitoring d evice which permits measurement of the quality indexes
of the transmitter and subscriber point channel will sati~fy the operating
needs.
In order to measure the complex resistances of the lines and lthe devices,
the PI-STR, IKS, VIG-3 and UKT instruments are used. The PI-STR and the .
VIG-3 instruments are stati4nary. A deficiency of them is the fact that
they mea~ure the input impedances only on the carrier frequencies. There
is a necessity for developing a stationary instrument which will permit _
measurement of the r esistance in the entire frequency band of the high-
frequency channels, which will permit more exact and complete estimation
of the quality of processing the TPV networks. A similar goal is being
fulfilled by the IKS instrument, but the measurement of th~ resistances
with this help is inconvenient, and errors are possible in the recalculations.
The measurement of the resistances by the VIG-3 instrument is much more
convenient and more precise. It is expedient to develop a new instrument
in which the advantages of the both instruments will be combined. The
operative measurements that do not require high precision when processing
the lines, when searching for and eliminating failures on the networks are
realized by the portable UKT instrument. -
The manufactured IPTV-1 fault finder, although basically satisfying the
operating needs, still has a deficiency: when finding short circuit points
using the search coil, the sensitivity increases with an increase in
frequency. This complicates the search for the short circuit points. It
is necessary to develop an instrument which will be free of this def iciency.
In addition, usually the lineman carries the IPTV-1 instrumen~ and the
lineman's indicator with him when searching for the damaged points. It is
expedient to combine the functions of a detector and an indicator in the
new instrument.
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CHAPTER 7. HIGH-FREQUENCY PROCESSING OF THE LINE PART OF A CHANNEL
~ AND HIGH-FREQUENCY LINE DEVICES
7.1. High-Frequency Processing of Lines
In ord er to create traveling wave conditions in the lines for high-frequency
signals and match the individual channel elements (MF [main feeder]-TP
[transformer substationJ, overhead wires and cable, and so on), it is
necessary to carry out high-frequency processing of the lines and channel
devices from the transmitting station to the subscriber units. It reduces
to inclusion of the devices which provide for transmission of all three
programs without nonlinear and frequency distortions and with sufficient
level at various points of the lines, and which lower the mutual effect
between the channels. The quality of processing the lines using high-frequency
devices depends on the parameters of the devices themselves and the precision
of matching the various sections of the channel. This quality can be
determined by measuring the distribution~of the voltage levels and the
harmonic coefficient on the higher modulating frequencies along the line.
This type of operation is diff icult; therefore it is nossible to determine
with sufficient accuracy the degree of ~atching, measuring the input impedance
of the line in the frequency band of each channel, and with respect to the
input resistance, the nonlinear distortions. The theoretical calculations
and practical measurements have demonstrated that if the modulus of the input
impedance on frequencies that are +4 kilohertz away from the carrier differs
from the modulus of the input impedance on the carrier itself by no more than
1.4 times, the phase angle will not exceed 15�, then the harmonic coefficient
will be no more than 3%. When these conditions are not satisfied, the match-
ing must be carried out more exactly.
In order to process the distributing and main feeders with leads and cable
inserts, passive devices are used which are basically made up of LC-elements.
The short f eeder leads kl~d 2. ohma
Here n is the number of distributing feeders at the given transformer sub-
station (excluding the feeder for the outdoor public address system FUZ,
which must be processed by a band-elimination filter). When measuring the
input impedance of the transformer substation from the high-voltage side the
- lead-in of the ma in feeder is first disconnected from the overhead wires
(Fig 8.14). All of the distributing feeders must be connected to cotnmon
buses. If the transformer substation has reserve feed with respect to all
programs, the measurement is repeated twice: once with the lead-in and the
UPTP of the feeder A(basic), another time with the input and UPTP of the
- Feeder B(reserve). When measuring the basic complex, the contactor of
cell B of the STP scale must be in the nonoperating position ar~3 the door
of this cell is open. The IKS instrument together with the ZX terminals
, connected to it by two identical inductance coil L1 and L2, the connection
point of which is grounded, are connected to wires running to the UPTP
input (in cell A of the STP bay). The IKS housing must be grounded. Then
_ the armature of the contactor in cell A is mechanically fixed in the pulled
position, the door of this cell is closed and measurements are taken. When
measuring the complex B the procedure is analogous. Tr.e induction coils
are designed to protect the operator and the instrument in the case of
random contact of the wires of the distributing f eeder and the electrical
network wires. Their resistance to currents of ineasuring frequencies of
the IKS is several kilohms and has no influence on the measurement result.
These coils are made locally using a ferrite core of the NM-2B30 type with
magnetic permeability M=2000, 75 turns and an inductance of no less than
9 millihenries.
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~
The moduli of the total input impedances of the main feeders on frequencies
of 78 and 120 kilohertz are measures of the input terminals of the UPP
through which the given line is fed. The transmitters and other UPP are
disconnected from the terminals. The terminal 7 is grounded by the require-
ments of safety engineering. During the measure~ents on a frequency of
78 kilohertz the IKS is connected to the terminals 3-7 of the UPP; the
terminals 4-7 are connected by jumper. For measurements on a frequency of
120 kilohertz the instrument is connected to terminals 4-7, and terminals 3-7 .
are closed.
The moduli of the input impedancea of the pairs of 3-pair house networks are
measured on a frequency of 400 hertz. The input of the measured pair is
disconnected from the correspQnding terminals of the GPTV and are connECted
- to the ZX terminals of the IKS instrument.
8.7. Electrical Measurements of Quality Indexes of High-Frequency Channels
and Parts of Them
On the parts of the "transmitter input and actual transmitter load (UPP.input)"
channel and the "transmitter input and transformer substation (common buses
of the STR)" channels the frequency characteristics, the harmonic coefficieut _
with respect to the envelope and the magnitude of the crosstalk interference
from the adjacent transmitter are measured.
On the "transmitter input and subscriber radio point of a single pair house
network" channel the frequency characteristics, the harmonic coefficient,
the magnitude of the crosstalk interference from the low-frequency channel
and from the adjacent high-frequency channel are measurad. The measurements
must be taken with respect to every high-frequency channel at two subscriber
- points of each transformer substation fed from different distributing
f eeders. During per iodic measurements the numbe~ of subscriber points
subject to measurement is selected from the calculation of H=N/2000, where
N is the total number of subscribers f ed from the given OUS, including the
single program radio point. The points fed from different transformer si=~�-
stations are selected for the measurement.
Or~ the "transmitter input and subscriber radio point of the three-pair house
network" channel the amplitude characteristics, frequency characteristics,
harmonic coeff icient, background and noise voltages and magnitude of cross-
talk interference from the adjacent high-frequency channel are measured.
The measurements are performed raith respect to each high-frequency channel
at one subscriber point of the three-pair house network �ed by the GPTV.
During periodic measurements, one radio point each out of M three-pair
networks of each Oi?S is selected for measurements, where M=m/5; m equals
the number of GP"iV in the given OUS.
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The part of the high-frequency channel "transmitter input and actual load"
is measured by the circuit in Fig 8.15. The remaining parts of the high-
frequency channels beginning with the transmitter input are measured by the
same circuit, but the KPU and the nonlinear distortion meter, depending on
which channel is measured, are connected to.th.e output of the transformer sub-
_ sta~ion or to the subscriber point.
~ ~
r-- 9 -To l , ' ' - - ~
. ~ -
,
� ~ ~ n~:ram- ~A'!-3 S?1~ ~4) . '
, ry ~
. ~ ~
~1~ ~ . ~ ~ Xi?-u Srllil ~5~
~ � Ri ~ ~
I ~
1 ~ ry!=Z71- _ � . :
~ y, .
R ~~o-I1 . . .
. . ~ + - -4-~ ~ i . . IPy ~
- q
. ~ NA3l Il;l.~l
- . . . ~ s
V . . j ' .
, _ � ' ps ~ .
~ ~6) 90i � . ~
Figure 8.15. Circuit for measuring the parts of the
high-frequency channel
Key:
1. Oscillator 6. E01 oscillograph
2. 78 kilohertz transmitter 7. KPU
3. 120 kilohertz transmi.tter 8. NNM
4. to the lst UPP 9. E02 oscillograph
5. to the 2d UPP
The parameters of the resistors R4, R5, R6 in the given circuit correspond
to the parameters of the resistors R3, R4, R5 of the circuit in Fig 8.1.
The indexes are measured at the inputs of the first and second groups of
UPP connected to the corresponding outputs of thE transmitter. The UPP
groups are replaced using the II2 switch. When measuring the remaining high-
frequency sections of thp channel the depth of ~adulation and the carrier
frequency voltage are monitored using the E01 oscillograph and the V2
voltmeter at the output of the UPP group to which the ma in feeder feeding
the transformer substation and the distributing network where the measure- _
ments are taken is connected.
The duration of the sendings of the measuring signal in the sound frequency
spectrum must be minimal. The checking is done by feeding the signal with
a frequency of 50-100 hertz and with a level of 30 decibels below rated -
to the input of the transmitter. The presence of the signal at its
. connection point is checked using the KPU.
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'I'li~~ ~~:~~~L.LLuLur l:r.~~c~u~~n~.y Lun.Lng and t~clting ot thc rc~quirc~J ~evr.lt~ ol
measuring signals must be carried out when loading the osciilator for the
resistor with a resistance equal to the rated input impedance of ~he trans-
mitter, that is, for position 2 of the switch II1. In order to obtain a
stable value of the output voltage of the oscillator in the frequency band
when connecting it to the input of the transmitter (position 1 or 3 of the
=~j switch II1) the output impedance of this oscillator must be an order less than
the input impedance of the transmitter.
When measuring the sections of the channel it is necessary f ixst to measure
the background and noise level, the crosstalk and then the frequency
c:~aracteristic and the harmonic coeff i~ient. _
= Before the measure~ents the sensitivity of the KPU instrumenfi is calibrated
by the carrier level in the interval. This replaces feeding a signal with
a frequency of 1000 hertz to the input of the transmitter to establish the
rated level at the measurement point. For measuring the background and
noise levels the signal source is disconnected from the input of the trans- -
- mitter of the tested channel and together with it a resistor is connected in
the screen with the resistance equal to the modulus of the output impedance
- of the signal source. When taking the readings of the KPU in decibels the _
calculation formula for calculating the signal/background and signal/noise
ratio has the form: D=20-(x+y), where D is the signal/background and
signal/noise ratio, decibels; 20 is the depth of ad~ustment of the carrier,
decibels; x is the value of the reading with respect to the output attenuator,
. decibels; y is the instrument readings, decibels.
When measuring the crosstalk interference level, the mea.suring signal with a
frequency of 1000 hertz, rated level and duration of 5-10 seconds is fed to
the input of the influencing channel. Here the output voltage of the
_ terminal modules of the equipment is monitored, and if the high-frequency
channel is influencing, then also the modulation depth is monitored. If
- the low-frequency channel is influencing, then trie low-frequency signal with
rated level is fed only to ~he transformer substation on the lines of which
the measurements are taken. All of the distributing f eeders of this sub-
station must be connected. On the two-element network the measuring signal
is fed only to the distributing feeder on which the measurements are taken.
The crosstalk interference le~Tel measurements are taken with the "noise"
position of the filter switc:h in the KPU. If the interference level exceeds
by less than 6 decibels the noise level and if it is belew the noise level,
, then the measurement is taken in the 1 and 2 kilohertz positions. In this
' case the level of the crosstalk interference is determined by the formula
A~ = 20 201g
.
. ~ Y~l~ .
U1 and U2 are the crosstalk interference voltages, volts, on frequencies of
1 and 2 kilohertz.
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~
- FOR OFFICIAL USE ONLY ~
Wi~~~i~ m~~;isuring the inter~crcnce level in the "noise" position and taking
tize readings of the KPU instrument in decibels the interference level is
determined by the formula A.~=20 -(x+y), decibels.
_ In ur~l~~r ~u nu~~iriur~� lli~~ I~r~�~~u~~n~~y ~~lirirricl~,rlr~l I~�~ ;t vult~i�c~ ul 0.2~i vul.lr+ -
!s Ced lo the input of the transmitter on a frequency of 110, 160, 1000, _
3000, 4000 and 6000 hertz. Initially a measuring signal is fed with a fre-
quency of 1000 hertz for 10 to 15 seconds. The input attenuator and
calibration regulator K are used to set the pointer of the KPU instrument
- to the -4 decibel position, with a position of the output attenuator at
- 0 decibels and the "measurement" position of the calibration switch. Then
the instrument is read successively on all frequencies.
The harmonic coeff icient is measured on frequencies of 2000 and 4000 hertz
for the rated output voltage of the transmitter and modulation depth M="70%
and signal duration of no more than 60 s~ :onds. Measurements are taken in
_ the "noise" position of the ~agulator b} KPU using the nonlinear dis-
tortion meter. ~
When measuring the quality indexes of the channel with the group receiver,
initially the harmonic coefficient is measured, then the background voltage, -
- the noise of the crosstalk interference and then the frequency characteristic.
The Itcirmonic coeff icient is measured on a frequency of 1000 hertz with rated
volt;i}.;e at the transmitter output. For the meas;~rements it is possible to
use Clie nonlinear distortion meter of the S6-1 type connected by the symmetric
input tc the house network. The voltage of the measuring signal can b~
monitored by the KPU in the "voltmeter" mode.
Before the measurements of the background, the noise of the crosstalk inter-
- ference and the frequency characteristic it is necessary to ~eed a preset
signal to the input of the transmitte~,c with rated frequency level of 1000
hertz to maintain a value of the amplif ication coefficient of the GPTV -
having automatic gain control. Directly af ter f eeding the preset signal
- the KPU instrument is used to take measurements in the "voltmeter" mode with
the channel switch position at low frequency. The duration of the preset
si~nal is 3 to 5 seconds. The background and noise voltages can be read
for 20 seconds; otherwise the amplification coefficient of the GPTV varies
and distorts the measurement result. The signalr,,ackgzuund and signal/noise
ratios are determined by the i:ormula
~j - 201g~~~~2~
~ cm) ~ (1)
Key: l. background (noise); 2. preset signal _
where Uy is the preset signal voltage measured by the KPU; Ubackground and
Unaise are the background and .~oise voltages measured by the KPU in the
corresponding positions of the filter switch.
r
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Inp~2~ ~
~np~3~ .
~ . -
. -
)!I V ' .
Figure 8.16. Circuit diagram of the measuring instrument
connection to the three-pair GPTV network
I:ey: 1. KPU; 2. program II; 3. program III
In order to measure the crosstalk incerference from the signals of the
adjacent high-frequency channel, the preset signal lasting 1 second is fed
to the input of the transmitter subjected to the effect. By using the
switch II1 a measuring signal lasting 8 seconds is fed directly to the input
of the transmitter of the influencing channel. By using the KPU in the
"voltmeter" mode the interference voltage Ui.~ is measured, ana any voltmeter
- with symmetric input or a lineman's indicator is used to measure the voltage
U2 of the influencing signal on the same pair of the three-pair network which
belongs to the influencing channel. Then the points of connecting the KPU
_ and the voltmeter to the three-pair network change places (see Fig 8.16) and
by using the switch II~, the measuring signal is fed to the input of the
transmitter to which the preset signal was fed. The KPU is used to measure
the interference voltage U2.~ (for 8 seconds), and the voltmeter is used to
measure the voltage of the influencing signal Ui. The signal/crosstalk ratio
in the two high-frequency channels is defined by the formulas:
U,
A,~ = 201g u
a. Ab~ 201g , ASl~
(1>
Key: 1. decibels -
The time diagrams of the voltages at the outputs of the transmitters (in the
measurement process) are presented in Fig 8.17.
In order to measure the crosstalk interference from the low-frequency signals
the preset signal lasting 1 second is sent to the input of the transmitter
subjected to the effect; then the measuring signa.l is f ed for 3 to 5 seconds.
_ The interference voltage is measured ~ising the KPU. The same method is used
to measure the interference in the second high-frequency channel. The
sign,al/interference ratio is determined by the above-indicated formulas.
When measuring the interference voltage in the "noise" position the inter-
ference voltage is read d3.re.ctly by the instrument scale. If the measurements
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P'UK UP'P'll:lAL US~: UNLY
qB /lepe9ttmv~r ~g ~rr~ (u.o~c ~2o~r~q) . ~
i?8 ~3) ~1) ~ '
. g ' � ~,e .
O f . � 9 - lT . . . . .
. . . . . . . , , ~
. - qB. Ilepe~~tmvu~r ~Ktwl~Rrt ~axfr~ ~2j ~ ~ _
ta~o . . _ . .
~t . . . .
e , ~ � ; ~ . . ~7 t~e (4>
Figure 8.17. Time diagrams of the voltages at the
output of the transmitters ~
Key:
1. 78 kilohertz (or 120 kilohertz) transmitter '
2. 120 kilohertz (or 78 kilohertz) transmitrer
3. U, volts
4. t, seconds -
are taken in the positions 1 and 2 kilohertz, the magnitude of the i.~;.er-
ference voltage is defined by the formula
UA = ~/~U~ UZ~ .
� (1~'. , . . : . .
Key: l. interference, low frequency
where U1 and U2 are the voltages of the crosstalk (in volts) on frequencies
of 1 and 2 kilohertz.
The preset signa~ lasting 1 second is fed to the input of the transmitter
to measure the frequency charact^ristic, then after 15 seconds, during
which the level is measured, th~~ ueasuring signal with a frequency of
1000 hertz and a level of 0.25 volts lasting 5 seconds is fed. The time
diagram of the voltages at the input of the transmitter in the measurement
process for one measuring frequency is represented in Fig 8.18. Using thF
KPU in the "voltmeter" mode and in the low-frequency position the signal
level is measured. The measurements are repeated on frequencies of 110 and
6000 hertz with feed of the preset signal at the rated level before each
sending of the measuring signal. -
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(1) U8
yinm~ro0a~n+d (3) . ~
q cttrrru .
. -
~eg
m~dnr~i ~4~
~ ~
. ~ ~ I8 t! t,C ~2~
Figure 8.18. Time diagram of the voltages at the input of the
transmitter
Key:
1. U, volts 3. Preset signal
� 2. t, seconds 4. Measuring signal
~ 276
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~
FOR OFFI~IAL USE ONLY
APPENDIX 1. QUALITY INDEXES OF THE HIGH-FREQUENCX CHANNELS (FROM THE
DRAFT OF OST "CHANNELS OF THE THREE-PROGRAM WIRE BROADCAST
HIGH-FREQUENCY SYSTEMS. BASIC PARAMETERS")
Table II 1.1. Quality Indexes of the Through Channel
Names of indexes Norms
Reproducible frequency band, hertz 100-6000
Nonuniformity of the frequency characteristic, in accordance with
decibels, no more than Fig 3:4
Harmonic coefficient, no mcre than, on frequencies
of :
above 100 to 200 hertz g/q
above 200 to 2000 hertz 4/2
above 2000 to 4000 hertz 5/2, 5
- Signal/background ratio, decibels, no less than 40
Signal/noise ratio, decibels, no less than 55
Signal/intelligible crosstalk ratio, decibels, no 50
less than
Notes: ~
1. The indexes of the through channel are normalized with the three-program
speaker corresponding to class II of the through channel.
2. The unaltered value of the nonuniformity of the frequency characteristic
~S2 can be shifted within the limits of ~S1 (Fig 3.4).
3. The norms for the harmonic coefficient indicated in the numerator must
be withstood for the rated signal level at the end of the through channel,
and in the denominator for all levels reduced with respect to rated from
6 to 20 decibels, for channels with devices having two-cycle low-frequency
stages.
4. Signal/background ratio; signal/noise ratio; sjgnal/intelligible cross-
talk ratio are normalized in the interval.
- S. Signal/background ratio is given for the channel with three-program -
speaker corresponding to class II of the through channel. For the channel
with group receivers the norm in decibels is na less than 50.
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Table II1.2. Quality Indexes o~ the Operating Channel and Parts 1
of It
Norms for the quality indexes of
the operating channel and parts of i~
Numr o f 1 ndexer~
a~ v~~ a~ ~ I a? ~�a o
~ .c s~ .c w
a~~i a~i " ii w~ o w o o " u ~ 00
J~ W+~ O H rl W 1.~ .G F+ W iJ .G W i.~ -
0 7+ o�~ o~+ o~+ ~ a? a~+ o Y+ ~ o a~
I f3 E~3 s.i W e0 p G1 Q N 7
ai aA a.~ m~ ao a~ a~ m u~+ ~ aL a~ ao C1 G~ ~-I
~~a~~n ~ama~a~co ~~m,~a?
a~o a~d,~ co.c a~a m N n~ acaa,.~ u
q ~ ~ ~ ~ w ~ ~ w ~ o .c a ~ N ~ d a?
H J.~ H i~ O i~ M H iJ W 1�1 d-~ QJ N J~ ~ N id
Reproducible frequency 100-6000 - 100-6000 100-6000
band, hertz
Nonuniformity of the fre- In accord- - In accordance In accord-
quency characteristic, ance with with ance with
decibels, no more than Fig 3.6 Fig 3.5 Fig 3.4
Harmonic coeff icient, Z,
_ no more than, at frequencies:
more than 100 to 200 hertz 4.0/2.0 - - 8.0/4.0
more than 200 to 2000 hertz 2.5/1.3 - - 4.0/2.0
more than 2000 to 4000 hertz 2.5/1.3 2.8/1.4 4.0/2.0 5.0/2.5 _
Signal/background ratio,
, decibels, no less than 60 - - 50
Signal/noise ratio, -
decibels, no less than 60 - - 55
Signal/intelligible cross-
talk ratio, decibels,
no less than:
from the low-frequQncy 60 55 53 50
channel
from the high-frequency 60 - 57 50
channel
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APPENDIX 2. EQUIVALENT PARAMETERS OF THE DISTRIBUTING FEEDER LINES
Table II2.1. Equivalent Parameters of the Bimetal (BSM) Circuit
with Wire Diameter of 3 mm
Load subscriber transformer TAG-10
, . liapas~ }ra �acrore 78 KJt~ $ Tlapax~rpH aa aacra:e t~0 xCu
S~ Zea ~3) ~ ~ za+ ~3) ~ ~9
'rP/+~
_ ~1) p~ yron AB/~at pap/xi~ uo Os~ roa '
~ 4~~6 5 6 7 ~5 ) ns/
6~ D~
- b~ 633 2�20' 0.76 1~59 602 -0�36' 0,45 2~54
~10 6~l5 4�; S' 1,~0 1,~5 5~fi -1�l2' 0~65 2~57
~5 656 7�24' 1~50 1,52 588 -1�42' 0~86 2~51
~ 20 . 664 9�s8' 2.50 1~49 576 -1�42' 1.Q~ 2~64
~ 25 670 13�12' 3~1 1,45 568 -2�18' 1~25 2~68
. 30 672 16� 3~? 1~43 556 -"~4' 1~43 2~71
35 6T1 18�54' 4,40 1,41 544 - -3�24' 1~61 2~74
~ 6~,5 ?1�48' 5.0 1,39 53~# --3�24' 1,8 2,78
~ -t9) ~'PY~-a6axe~xe ~rpaec.~opnsa~rog~ TAI'-25 '
, 5~ 658 14~4' . 3.? 1,44 624 4� 1~65� 2~4? -
10 633 29�12' ?.5 1~37 623 8� 3,10 2,44
!5 53? 33'~S' 10~8 1,40 622 11�~' 4,5 2~43
2a 472 ~5�1S' .13.? 1.46 . 612 15�3~' 6.0 2,43
25 41? 48�5fi' 16,2 1,5~ 559 18�18' Z~4 2~44
~ 30 378 51� i8;4_ 1.62 583 21�48'_ 8~7 2~45
Key : ~ . . . _ ~ .
l. S, tr/lan
2. Parameter on a frequency of 78 kilohertz
3. zBe
4. Modulus, ohms 8. Parameters on a frequency of
S. Angle 120 kilohertz
6. Decibels/lan 9. Load subscriber transformer
7. Rad/km TAG-25
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Table II2.2. Equivalent Parameters of a Steel Network with
Wire Diameter of 3 mm
Load subscriber transformers TAG-10
~_(2~Iapaxerp~ es sa:rorax 76 xI1a s) iiapattcrps aa ranra:e 12u xl~t
g~ Zss~3) " as za~ ~3 as ~ -
~P/~
(1) `~m'r Csyro~ 1q~/xx p(~)y ~4) ~SJ A~ ~ ,
(b
5~ 820 --6�10' 3,5 I,SS 762 -6�40' 3,8 3,d?
10 23T~ -3'35' 4,! 1.91 ?50 -6� 4~2 3,10
15 ~ 850 -4�43' 4~8 t;8~ 740 -5�30' 4,5 3,13
20 860 2� 5~5 1,80 7:~ -5� 4,8 3,1T ~
Z5 86S 5� 6,3 1.T5 719 -4�40' S.0 3.21
3~ 8S7 7�40' ?~1 l.72 ?10 -4'10'- b.4 3.25 �
. 35 862 10'30' l.67 700~ -3�Z5' 5.6 � 3,39
~i0 855 l4�20' 8.7 D.62 6SD -3�2b' 5,g 3.33
. - ( ) ~'PY3~a-aboee~~rcec~te 'rPaxc~wPn~a~roPd TAI'-25 . . .
5 g60 7�35' 7,0 1.T2 ?87- -3�15' 5,21 2~93
IO ?~0 23�10' 11.7 1,58 ?81 0�5U' ?y0 2,a9
. la 675 ~2�t0' 16.0 1.56 ??5 4�50' .8~75 2~85
20 594 37�45' 19.T 1.59 -?60 8�25' 10.~ 2.84
25 550 40�30' 23,2 1.64 ?42 12� ~ 12.3 2.84
30 . 515 42�~0' 26,6 1.70 ?20 1~� 14.1 ~.i~ ~ -
Key : . . - . � ' ' . . . ~ . : . �
1. S, tr/lan
2. Parameters on a frequency of 78 kilohertz
3. zBe
4. Modulus, ohms
5. Angle
6. Decibels/km
7. Rad/km
8. Param+eters on a frequency of 120 kilohertz
9. Load subscriber transformer TAG-25
280 -
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APPENDIX 3. MAXIMUM ADMISSTBLE LOADS OF A STORY (IN POINTS) OF TH~
STAIRCASE WIRING LINES
Table II3.1
LIHGio tORP1t H8 BTa.~E. rtOpx:
~CQ~f~h~C K.C~aOa Jna:slst 7~lCTgttQ~
- ~2~ Ao8 apo~oJ~t. IIPs Am~a rc~~pre:pao;t npoec~~sa. K
. Ib 90
jt~r.csa ~
r:ecrs$apo3 ~3) Aa?~a a~P~aaxoR ~ryoao~xa. x -
nDoao~s~ ~ n c~
~ o
~ 0 4~ �~t 4)�~ 0 4)a ~4)
(.1) - ^ o ,,e " �
o ~4~� A %1 o d /1 A
. ~ n~o~oA nTBhc�zx i,2 ~s~
(GjAO 1S 6 6 6 6 - 6 6 6 4
> 15 Ao 2? 6 5 4 2 6 2 2 -
> 27 s 36 6 4 3 2 4 - - ~
>36 ~ 48 4 2 2 - 2 - -
~ > 48 a 60 2 - - - - - - -
: (4) ~ .
. : . . IlpoBOA IIByi{.2~5 ~6~ .
. ~
~t4)Ao15~ 6 6 6 6 6~ 6 6 ,6
>15Ao2T~ 6 6 6 4 6 ~ 3 a
>27 ~ vS 6 6 5 3 5 3 3 ~
>36 ~ 48 ~ 6 4 ~ 3 ~ 2 3 2 2
>4g , 60 3 ~ 2 2 - 2 - - -
~ ~ . T1poPOA I1B-1~5 (PSL3�2X1~5i (7)" ~ ' ~
~ > 15 ~AO Z? 6 . 6 6 b 6 . 6 6 4
>Z7 s 36 6 6 6 6 6 6 6 3
> 36 s 48 6 6 6 6, 6 6 8 3
~ >48 ~ 60 5 ; b 5 b b 4 3 2
~
>6fl s 80 4 4 4 3. 3 2 2 -
Key: - ~
Length of the staircase wiring line, meters
z. No of points in a story connected to one staircase wiring line;
with a length of the residence line, meters
3. Length of attic wiring, meters 6. PVZh-2,5 wire
4. to 7. PV-1,5 (PPV-2x1,5) wire
5. PTVZh-2x1,2 wire
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- APPIIIDIX 4. CALCULATION OF THE INDUCTANCE AND CAPACITANCE OF THE
RESIDENCE CIRCUIT Lre3, ~res ~ THE REACTANCES
X~ AND XL ON CARRIER FREQUENCIES OF 78 AND 120 KILOHERTZ
Table JI4.1
fp=78 kilohertz fp=120 kilohertz
1
1
Lres - 4170 C , millihenries Lres = 1750 ~~picofaradsJ' ~illihenries
[picofarads] _
1 1
~res = 4170 , picofarads C1e3 = 1750 L , picofarads
L[millihenries] [mil.lihenries]
XL = 0.49 LjmillihenriesJ~ kilohms XL = 0.75 L~millihenries]~ kilohms
1
X~ = 1.95�103 ~ , kilohms X~ = 1.33�103 1 kilohms
[picofarads] ~[picofarads]
282
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I
MUL BY
YA. DZYRDCH I K, S. R. ZRSLR~SK I Y
31 JRNURRY i980 B. N. F I LRTO~, R. ~J. SHER~HAKO~A C FOUO ) 4 OF 4
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COPYRIGHT: Izdatel'stvo "Svyaz'," i974 ~
10845
CSO: 8344/0265 - -
~86
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